Analog Devices AD652 c Datasheet
Monolithic Synchronous
FEATURES
Full-scale frequency (up to 2 MHz) set by external system
clock
Extremely low linearity error (0.005% max at 1 MHz FS,
0.02% max at 2 MHz FS)
No critical external components required
Accurate 5 V reference voltage
Low drift (25 ppm/°C max)
Dual- or single-supply operation
Voltage or current input
MIL-STD-883 compliant versions available
PRODUCT DESCRIPTION
The AD652 synchronous voltage-to-frequency converter
(SVFC) is a powerful building block for precision analog-todigital conversion, offering typical nonlinearity of 0.002%
(0.005% maximum) at a 100 kHz output frequency. The inherent monotonicity of the transfer function and wide range of
clock frequencies allow the conversion time and resolution to
be optimized for specific applications.
The AD652 uses a variation of the charge-balancing technique
to perform the conversion function. The AD652 uses an
external clock to define the full-scale output frequency, rather
than relying on the stability of an external capacitor. The result
is a more stable, more linear transfer function, with significant
application benefits in both single- and multichannel systems.
Gain drift is minimized using a precision low drift reference
and low TC, on-chip, thin-film scaling resistors. Furthermore,
initial gain error is reduced to less than 0.5% by the use of laserwafer-trimming.
The analog and digital sections of the AD652 have been
designed to allow operation from a single-ended power source,
simplifying its use with isolated power supplies.
FUNCTIONAL BLOCK DIAGRAM
R
IN
V
IN
INTEGRATOR
HL
C
INT
COMPARATOR
5V
Voltage-to-Frequency Converter
AD652
The AD652 is available in five performance grades. The 20-lead
PLCC-packaged JP and KP grades are specified for operation
over the 0°C to +70°C commercial temperature range. The
16-lead CERDIP-packaged AQ and BQ grades are specified for
operation over the −40°C to +85°C industrial temperature
range. The AD652SQ is available for operation over the full
−55°C to +125°C extended temperature range.
PRODUCT HIGHLIGHTS
1. The use of an external clock to set the full-scale frequency
allows the AD652 to achieve linearity and stability far
superior to other monolithic VFCs. By using the same clock
to drive the AD652 and set the counting period (through a
suitable divider), conversion accuracy is maintained
independent of variations in clock frequency.
2. The AD652 synchronous VFC requires only one external
component (a noncritical integrator capacitor) for
operation.
3. The AD652 includes a buffered, accurate 5 V reference.
4. The AD652’s clock input is TTL and CMOS compatible and
can also be driven by sources referred to the negative power
supply. The flexible open-collector output stage provides
sufficient current sinking capability for TTL and CMOS
logic, as well as for optical couplers and pulse transformers.
A capacitor-programmable one-shot is provided for selection of optimum output pulse width for power reduction.
5. The AD652 can also be configured for use as a synchronous
F/V converter for isolated analog signal transmission.
6. The AD652 is available in versions compliant with
MILSTD-883. Refer to the Analog Devices Military
Products Databook or current AD652/883B data sheet for
detailed specifications.
CLOCK IN
D FLOP LATCH
CKQDG
AND
Q
D
Q
ONE
SHOT
C
OS
1mA
–V
S
Rev. C
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
Figure 1.
00798-001
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
Fax: 781.326.8703 © 2004 Analog Devices, Inc. All rights reserved.
www.analog.com
AD652
TABLE OF CONTENTS
Specifications..................................................................................... 3
Absolute Maximum Ratings............................................................ 5
ESD Caution.................................................................................. 5
Definitions of Specifications....................................................... 5
Theory of Operation ........................................................................ 6
Overrange...................................................................................... 8
SVFC Connection for Dual Supply, Positive Input Voltages .. 9
SVFC Connections for Negative Input Voltages ...................... 9
SVFC Connection for Bipolar Input Voltages ........................ 10
PLCC Connections..................................................................... 11
Gain and Offset Calibration...................................................... 11
Gain Performance ......................................................................12
Reference Noise .......................................................................... 12
Digital Interfacing Considerations........................................... 12
Component Selection ................................................................ 12
Digital Ground............................................................................ 13
Single-Supply Operation........................................................... 14
Frequency-to-Voltage Converter ............................................. 15
Decoupling and Grounding...................................................... 16
Frequency Output Multiplier.................................................... 17
Single-Line Multiplexed Data Transmission .......................... 18
Isolated Front End...................................................................... 22
A-to-D Conversion .................................................................... 22
Delta Modulator......................................................................... 23
Bridge Transducer Interface...................................................... 24
Outline Dimensions....................................................................... 25
Ordering Guide............................................................................... 26
REVISION HISTORY
5/04—Data Sheet Changed from Rev. B to Rev. C
Updated Format..............................................................Universal
Changes to Gain and Offset Calibration section.................... 11
Updated Outline Dimensions................................................... 25
Changes to Ordering Guide...................................................... 26
2/00—Data Sheet Changed from Rev. A to Rev. B
Rev. C | Page 2 of 28
AD652
SPECIFICATIONS
Typical @ TA = 25°C, VS = ±15 V, unless otherwise noted. Specifications in boldface are 100% tested at final test and are used to measure
outgoing quality levels.
Table 1.
AD652JP/AQ/SQ AD652KP/BQ
Parameter Min Typ Max Min Typ Max Unit
VOLTAGE-TO-FREQUENCY MODE
Gain Error
f
= 200 kHz ±0.5 ±1 ±0.25 ±0.5 %
CLOCK
f
= 1 MHz ±0.5
CLOCK
f
= 4 MHz ±0.5
CLOCK
±1
±1.5
Gain Temperature Coefficient
f
= 200 kHz ±25 ±50 ±15 ±25 ppm/°C
CLOCK
f
= 1 MHz ±25
CLOCK
±10
f
= 4 MHz ±25
CLOCK
Power Supply Rejection Ratio 0.001
±50
±50
±75
0.01
Linearity Error
f
= 200 kHz ±0.002 ±0.02 ±0.002 ±0.005 %
CLOCK
f
= 1 MHz ±0.002
CLOCK
f
= 2 MHz ±0.01 ±0.02 ±0.002 ±0.005 %
CLOCK
f
= 4 MHz ±0.02
CLOCK
Offset (Transfer Function, RTI) ± 1
Offset Temperature Coefficient ±10
±0.02
±0.05
±3
±50
Response Time One Period of New Output Frequency Plus One Clock Period.
FREQUENCY-TO-VOLTAGE MODE
Gain Error, fIN = 100 kHz FS ±0.5 ±1 ±0.25 ±0.5 %
Linearity Error, fIN = 100 kHz FS ±0.002 ±0.02 ±0.002 ±0.01 %
INPUT RESISTORS
CERDIP (Figure 2)(0 to 10 V FS Range) 19.8 20 20.2 19.8 20 20.2 kΩ
PLCC (Figure 3)
Pin 8 to Pin 7 9.9 10 10.1 9.9 10 10.1 kΩ
Pin 7 to Pin 5 (0 V to 5 V FS Range) 9.9 10 10.1 9.9 10 10.1 kΩ
Pin 8 to Pin 5 (0 V to 10 V FS Range) 19.8 20 20.2 19.8 20 20.2 kΩ
Pin 9 to Pin 5 (0 V to 8 V FS Range) 15.8 16 16.2 15.8 16 16.2 kΩ
Pin 10 to Pin 5 (Auxiliary Input) 19.8 20 20.2 19.8 20 20.2 kΩ
Temperature Coefficient (All) ±50
±100
INTEGRATOR OP AMP
Input Bias Current
Inverting Input (Pin 5) ±5
Noninverting Input (Pin 6) 20
Input Offset Current 20
±20
50
70
Input Offset Current Drift 1 3 1 2 nA/°C
Input Offset Voltage ±1
±3
Input Offset Voltage Drift ±10 ±25 ±10 ±15 µV/°C
Open-Loop Gain 86 86 dB
Common-Mode Input Range –VS + 5 +VS – 5 –VS + 5 +VS – 5 V
CMRR 80 80 dB
Bandwidth 14 95 14 95 MHz
Output Voltage Range
−1
− 4) −1
(+V
S
(Referred to Pin 6, R1 > = 5 kΩ)
±0.25
±0.25
±15
±10
±15
0.001
±0.002
±0.01
±1
±10
±50
±5
20
20
±1
±0.5
±0.75
±25
±30
±50
0.01
±0.005
±0.02
±2
±25
±100
±20
50
70
±2
(+VS − 4)
%
%
ppm/°C
ppm/°C
ppm/°C
%/V
%
%
mV
µV/°C
ppm/°C
nA
nA
nA
mV
V
1
Rev. C | Page 3 of 28
AD652
AD652JP/AQ/SQ AD652KP/BQ
Parameter Min Typ Max Min Typ Max Unit
COMPARATOR
Input Bias Current 0.5 5 0.5 5 µA
Common-Mode Voltage −VS + 4 + VS − 4 −VS + 4 +VS − 4 V
CLOCK INPUT
Maximum Frequency
4
Threshold Voltage (Referred to Pin 12) 1.2 1.2 V
T
to T
MIN
MAX
0.8
Input Current
(−VS < V
< +VS) 5
CLK
Voltage Range −VS +V
Rise Time 2 2 µs
OUTPUT STAGE
VOL (I
= 10 mA)
OUT
I
OL
VOL < 0.8 V
VOL < 0.4 V, T
MIN
to T
MAX
IOH (Off Leakage) 0.01
Delay Time, Positive Clock Edge to Output Pulse
Fall Time (Load = 500 pF and I
= 5 mA) 100 100 ns
SINK
150
Output Capacitance 5 5 pF
OUTPUT ONE-SHOT
Pulse Width, t
COS = 300 pF
OS
1
COS = 1000 pF 4 5 6 4 5 6 µs
REFERENCE OUTPUT
Voltage
4.950
Drift
Output Current
Source T
MIN
to T
MAX
10
Sink 100 500 100 500 µA
Power Supply Rejection
Supply Range = ±12.5 V to ±17.5 V 0.015 0.015 %/V
Output Impedance (Sourcing Current) 0.3
POWER SUPPLY
Rated Voltage ±15 ±15 V
Operating Range
Dual Supply ±6 ±15 ±18 ±6 ±15 ±18 V
Single Supply (−VS = 0) +12 +36 +12 +36 V
Quiescent Current ±11
Digital Common −VS +VS − 4 –V
Analog Common −V
S
TEMPERATURE RANGE
Specified Performance
JP, KP Grade 0 +70 0 +70 °C
AQ, BQ Grade −40 +85 −40 +85 °C
SQ Grade −55 +125 °C
1
Referred to internal V
. In PLCC package, tested on 10 V input range only.
REF
5
2.0 0.8
20
S
0.4
15
8
10
200
1.5
5.0
250 150
2
5.050 4.975
100
2
±15
+V
S
4
5
−V
S
0.01
1 1.5
10
0.3
±11
S
−V
S
5 MHz
2.0
20
+V
0.4
15
8
10
200
250
2
5.0
5.025
50
mA
2
±15
+VS − 4 V
+V
V
µA
S
V
V
mA
mA
µA
ns
µs
V
ppm/°C
Ω
mA
S
V
Rev. C | Page 4 of 28
AD652
ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter Ratings
Total Supply Voltage +VS to −V
Maximum Input Voltage (Figure 6) 36 V
Maximum Output Current
(Open Collector Output)
Amplifier Short-Circuit to Ground Indefinite
Storage Temperature Range: CERDIP −65°C to +150°C
Storage Temperature Range: PLCC −65°C to +150°C
S
36 V
50 mA
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on
the human body and test equipment and can discharge without detection. Although this product features
proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy
electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance
degradation or loss of functionality.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
DEFINITIONS OF SPECIFICATIONS
Gain Error
The gain of a voltage-to-frequency converter is the scale factor
setting that provides the nominal conversion relationship, e.g.,
1 MHz full scale. The gain error is the difference in slope
between the actual and ideal transfer functions for the V-F
converter.
Linearity Error
The linearity error of a V-F is the deviation of the actual
transfer function from a straight line passing through the
endpoints of the transfer function.
Gain Temperature Coefficient
The gain temperature coefficient is the rate of change in fullscale frequency as a function of the temperature from +25°C to
or T
T
MIN
MAX
.
Table 3. Pin Configurations
Pin No. Q-16 Package P-20A Package
1 +V
2 TRIM +V
3 TRIM NC
4 OP AMP OUT OP AMP OUT
5 OP AMP “−“ OP AMP “−“
6 OP AMP “+” OP AMP “+”
7 10 VOLT INPUT 5 VOLT INPUT
8 −V
9 C
10 CLOCK INPUT OPTIONAL 10 V INPUT
11 FREQ OUT −V
12 DIGITAL GND C
13 ANALOG GND CLOCK INPUT
14 COMP “−“ FREQ OUT
15 COMP “+” DIGITAL GND
16 COMP REF ANALOG GND
17 COMP “−“
18 COMP “+”
19 NC
20 COMP REF
S
S
OS
NC
S
10 VOLT INPUT
8 VOLT INPUT
S
OS
Rev. C | Page 5 of 28
AD652
T
THEORY OF OPERATION
A synchronous VFC is similar to other voltage-to-frequency
converters in that an integrator is used to perform a chargebalance of the input signal with an internal reference current.
However, rather than using a one-shot as the primary timing
element, which requires a high quality and low drift capacitor, a
synchronous voltage-to-frequency converter (SVFC) uses an
external clock. This allows the designer to determine the system
stability and drift based upon the external clock selected. A
crystal oscillator may also be used if desired.
The SVFC architecture provides other system advantages
besides low drift. If the output frequency is measured by
counting pulses gated to a signal that is derived from the clock,
the clock stability is unimportant and the device simply
performs as a voltage-controlled frequency divider, producing a
high resolution A/D. If a large number of inputs must be
monitored simultaneously in a system, the controlled timing
relationship between the frequency output pulses and the usersupplied clock greatly simplifies this signal acquisition. Also, if
the clock signal is provided by a VFC, the output frequency of
the SVFC is proportional to the product of the two input
voltages. Therefore, multiplication and A-to-D conversion on
two signals are performed simultaneously.
AD652
SYNCHRONOUS
+V
TRIM
TRIM
OP AMP OUT
OP AMP "–"
OP AMP "+"
10 VOLT INPUT
–V
VOLTAGE-TO-
FREQUENCY
1
S
CONVERTER
2
3
4
5
6
20kΩ
7
1mA
8
S
Figure 2. CERDIP Pin Configuration
5V
REFERENCE
ONE
SHOT
QCK
D
AND
Q
"D"
FLOP
COMP REF
16
COMP "+"
15
14
COMP "–"
13
ANALOG GND
DIGITAL GND
12
FREQ OUT
11
10
CLOCK INPUT
9
C
OS
00798-002
S
OP AMP OU
OP AMP "–"
OP AMP "+"
5V INPUT
10V INPUT
NC3+V
AD652
SYNCHRONOUS
VOLTAGE-TO-FREQUENCY
4
5
6
7
8
CONVERTER
10kΩ
10kΩ
16kΩ
9
8V INPUT
2
1mA
4kΩ
10
10V INPUT
OPTIONAL
NC1COMP REF20NC
5V
REFERENCE
"D"
Q
FLOP
D
AND
Q
CK
ONE
SHOT
11
12
S
OS
–V
C
19
18
17
16
15
14
13
NC = NO CONNECT
INPUT
CLOCK
COMP "+"
COMP "–"
ANALOG GND
DIGITAL GND
FREQ OUT
Figure 3. PLCC Pin Configuration
Figure 4 shows the typical up-and-down ramp integrator output
of a charge-balance VFC. After the integrator output has
crossed the comparator threshold and the output of the AND
gate has gone high, nothing happens until a negative edge of the
clock comes along to transfer the information to the output of
the D FLOP. At this point, the clock level is low, so the latch does
not change state. When the clock returns high, the latch output
goes high and drives the switch to reset the integrator; at the
same time, the latch drives the AND gate to a low output state.
On the very next negative edge of the clock, the low output state
of the AND gate is transferred to the output of the D FLOP.
When the clock returns high, the latch output goes low and
drives the switch back into the Integrate mode. At the same
time, the latch drives the AND gate to a mode where it
truthfully relays the information presented to it by the
comparator.
00798-003
The pinouts of the AD652 SVFC are shown in Figure 2 and
Figure 3. A block diagram of the device configured as an SVFC,
along with various system waveforms, is shown in Figure 4.
Rev. C | Page 6 of 28
Because the reset pulses applied to the integrator are exactly one
clock period long, the only place where drift can occur is in a
variation of the symmetry of the switching speed with
temperature.
Since each reset pulse is identical, the AD652 SVFC produces a
very linear voltage-to-frequency transfer relation. Also, because
all reset pulses are gated by the clock, there are no problems
with dielectric absorption causing the duration of a reset pulse
to be influenced by the length of time since the last reset.
AD652
R
CLOCK IN
D FLOP LATCH
CKQDG
AND
ONE
Q
D
SHOT
Q
t
OS
C
OS
00798-004
V
IN
R
IN
1mA
INTEGRATOR
COMPARATOR
C
INT
INTEGRATOR
HL
–V
S
OUTPUT
CLOCK
OUT
AND
OUT
D FLOP
OUT
LATCH
OUT
FREQ
OUT
COMPARATOR
5V
THRESHOLD
t
OS
Figure 4. Block Diagram and System Waveforms
Figure 4 shows that the period between output pulses is
constrained to be an exact multiple of the clock period.
Consider an input current of exactly one quarter the value of
the reference current. In order to achieve a charge balance, the
output frequency equals the clock frequency divided by four:
one clock period for reset and three clock periods of integrate.
This is shown in Figure 5. If the input current is increased by a
very small amount, the output frequency should also increase
by a very small amount. Initially, however, no output change is
observed for a very small increase in the input current. The
output frequency continues to run at one quarter of the clock,
delivering an average of 250 µA to the summing junction. Since
the input current is slightly larger than this, charge accumulates
in the integrator and the sawtooth signal starts to drift downward. As the integrator sawtooth drifts down, the comparator
threshold is crossed earlier and earlier in each successive cycle,
until finally, a whole cycle is lost. When the cycle is lost, the
integrate phase lasts for two periods of the clock instead of the
usual three periods. Thus, among a long string of divide-byfours, an occasional divide-by-three occurs; the average of the
output frequency is very close to one quarter of the clock, but
the instantaneous frequency can be very different.
INTEGRATO
OUT
THRESHOLD
CLOCK
Figure 5. Integrator Output for I
= 250 µA
IN
Because of this, it is very difficult to observe the waveform on
an oscilloscope. During all of this time, the signal at the output
of the integrator is a sawtooth wave with an envelope that is also
a sawtooth. See Figure 6.
200µs/BOX
C
INT
100µs/BOX
FREQ OUT
10µs/BOX
CLOCK IN
10µs/BOX
00798-006
Figure 6. Integrator Output for I
Slightly Greater than 250 µs
IN
00798-005
Rev. C | Page 7 of 28
AD652
Another way to view this is that the output is a frequency of
approximately one-quarter of the clock that has been phase
modulated. A constant frequency can be thought of as
accumulating phase linearly with time at a rate equal to 2πf
radians per second. Therefore, the average output frequency,
which is slightly in excess of a quarter of the clock, requires
phase accumulation at a certain rate. However, since the SVFC
is running at exactly one-quarter of the clock, it does not
accumulate enough phase (see Figure 7). When the difference
between the required phase (average frequency) and the actual
phase equals 2π, a step-in phase is taken where the deficit is
made up instantaneously. The output frequency is then a steady
carrier that has been phase modulated by a sawtooth signal (see
Figure 7). The period of the sawtooth phase modulation is the
time required to accumulate a 2π difference in phase between
the required average frequency and one quarter of the clock
frequency. The sawtooth phase modulation amplitude is 2π.
PHASE
2
π
2
π
EXPECTED
PHASE
ACTUAL PHASE
The result of this synchronism is that the rate at which data may
be extracted from the series bit stream produced by the SVFC is
limited. The output pulses are typically counted during a fixed
gate interval and the result is interpreted as an average
frequency. The resolution of such a measurement is determined
by the clock frequency and the gate time. For example, if the
clock frequency is 4 MHz and the gate time is 4.096 ms, a
maximum count of 8,192 is produced by a full-scale frequency
of 2 MHz. Thus, the resolution is 13 bits.
OVERRANGE
Since each reset pulse is only one clock period in length, the
full-scale output frequency is equal to one-half the clock
frequency. At full scale, the current steering switch spends half
of the time on the summing junction; thus, an input current of
0.5 mA can be balanced. In the case of an overrange, the output
of the integrator op amp drifts in the negative direction and the
output of the comparator remains high. The logic circuits
simply settle into a divide-by-two of the clock state.
TIME
φ
MOD (t)
2
π
V
(t) = COS (2
OUT
CARRIER FREQUENCY
Figure 7. Phase Modulation
π×f
AVE
AVERAGE
×
t +φMOD (t))
TIME
PHASE
MODULATION
00798-007
Rev. C | Page 8 of 28
AD652
V
C
SVFC CONNECTION FOR DUAL SUPPLY, POSITIVE INPUT VOLTAGES
Figure 8 shows the AD652 connection scheme for the
traditional dual supply, positive input mode of operation. The
range is from ±6 V to ±18 V. When +VS is lower than 9.0 V,
±V
S
As shown in Figure 8, three additional connections are required
The first connection is to short Pin 13 to Pin 8 (Analog Ground
) and add a pull-up resistor to +VS (as shown in
to −V
S
Figure 21). The pull-up resistor is determined by the following
equation:
V
V52 −
S
R
PULLUP
=
These connections ensure proper operation of the 5 V reference.
Tie Pin 16 to Pin 6 (as shown in Figure 21) to ensure that the
integrator output ramps down far enough to trip the
comparator.
The CERDIP-packaged AD652 accepts either a 0 V to 10 V or
0 mA to 0.5 mA full-scale input signal. The temperature drift of
µA500
+
S
the AD652 is specified for a 0 V to 10 V input range using the
internal 20 kΩ resistor. If a current input is used, the gain drift is
degraded by a maximum of 100 ppm/°C (the TC of the 20 kΩ
resistor). If an external resistor is connected to Pin 5 to establish
a different input voltage range, drift is induced to the extent that
the external resistor’s TC differs from the TC of the internal
resistor. The external resistor used to establish a different input
voltage range should be selected to provide a full-scale current
of 0.5 mA (i.e., 10 kΩ for 0 V to 5 V).
SVFC CONNECTIONS FOR NEGATIVE INPUT VOLTAGES
Voltages that are negative with respect to ground may be used
as the input to the AD652 SVFC. In this case, Pin 7 is grounded
and the input voltage is applied to Pin 6 (see Figure 9). In this
mode, the input voltage can go as low as 4 V above −V
configuration, the input is a high impedance, and only the
20 nA (typical) input bias current of the op amp must be
supplied by the input signal. This is contrasted with the more
usual positive input voltage configuration, which has a 20 kΩ
input impedance and requires 0.5 mA from the signal source.
. In this
S
AD652
SYNCHRONOUS
VOLTAGE-TO-
FREQUENCY
1
CONVERTER
2
3
INT
–
V
+
4
5
6
IN
–V
20kΩ
7
1mA
8
S
5V
REFERENCE
ONE
SHOT
QCK
D
AND
Q
"D"
FLOP
16
15
14
13
ANALOG
GND
12
R
L
11
10
9
5V
CLOCK
+V
S
Figure 8. Standard V/F Connection for Positive Input Voltage with Dual Supply
+V
S
AD652
SYNCHRONOUS
VOLTAGE-TO-
FREQUENCY
1
CONVERTER
2
3
C
INT
–
V
IN
+
4
5
6
20kΩ
7
1mA
8
–V
S
5V
REFERENCE
ONE
SHOT
QCK
D
AND
Q
"D"
FLOP
16
15
14
13
ANALOG
GND
12
R
L
11
10
9
5V
CLOCK
+V
S
Figure 9. Negative Voltage Input
DIGITAL
GND
FREQ
OUT
DIGITAL
GND
FREQ
OUT
00798-008
00798-009
Rev. C | Page 9 of 28
Loading...