INTEGRATED CIRCUITS
DATA SHEET
TEA1620P
STARplugTM
Preliminary specification |
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2003 June 18 |
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File under Integrated Circuits, IC11 |
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Philips Semiconductors |
Preliminary specification |
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STARplugTM |
TEA1620P |
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FEATURES
∙Designed for general purpose supplies up to 50 W
∙Integrated power switch:
– TEA1620: 48 Ω; 650 V
∙Operates from universal AC mains supplies (80 to 276 V)
∙Adjustable frequency for flexible design
∙RC oscillator for load insensitive regulation loop constant
∙Valley switching for minimum switch-on loss
∙Frequency reduction at low power output makes low standby power possible (<100 mW)
∙Adjustable overcurrent protection
∙Under voltage protection
∙Temperature protection
∙Short circuit winding protection
∙Simple application with both primary and secondary (opto) feedback
∙Available in 8-pin DIP package.
GENERAL DESCRIPTION
The TEA1620P is a Switched Mode Power
Supply (SMPS) controller IC that operates directly from the rectified universal mains. It is implemented in the high voltage EZ-HV SOI process, combined with a low voltage BICMOS process. The device includes a high voltage power switch and a circuit for start-up directly from the rectified mains voltage.
A dedicated circuit for valley switching is built in, which makes a very efficient slim-line electronic powerplug concept possible.
In its most basic version of application, the TEA1620P acts as a voltage source. Here, no additional secondary electronics are required. A combined voltage and current source can be realized with minimum costs for external components. Implementation of the TEA1620P renders an efficient and low cost power supply system.
APPLICATIONS
Typical application areas for the STARplugTM are:
∙Chargers
∙Adapters
∙STB (Set Top Box)
∙DVD
∙CD(R)
∙TV/monitor standby supplies
∙PC peripherals
∙PC Silverbox standby SMPS
∙Microcontroller supplies in home applications and small portable equipment, etc.
2003 June 18 |
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Philips Semiconductors |
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Preliminary specification |
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STARplugTM |
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TEA1620P |
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QUICK REFERENCE DATA |
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SYMBOL |
PARAMETER |
CONDITIONS |
MIN. |
TYP. |
MAX. |
UNIT |
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Vdrain(max) |
maximum voltage at the DRAIN |
Tj > 0 °C |
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− |
650 |
V |
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pin |
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RDS(on) |
drain-source on-state resistance |
Tj = 25 °C; Isource = −0.06 A |
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48 |
55.2 |
Ω |
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of TEA1620 |
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Tj = 100 °C; Isource = −0.06 A |
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68 |
78.2 |
Ω |
VCC(max) |
maximum supply voltage |
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− |
− |
40 |
V |
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fosc |
frequency range of oscillator |
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10 |
− |
200 |
kHz |
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Idrain |
supply current drawn from DRAIN |
no auxiliary supply |
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0.5 |
− |
mA |
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pin |
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Tamb |
ambient temperature |
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−20 |
− |
+85 |
°C |
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ORDERING INFORMATION |
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TYPE |
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PACKAGE |
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NUMBER |
NAME |
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DESCRIPTION |
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VERSION |
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TEA1620P |
DIP8 |
plastic dual in-line package; 8 leads (300 mil) |
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SOT97-1 |
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2003 June 18 |
3 |
Philips Semiconductors |
Preliminary specification |
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STARplugTM |
TEA1620P |
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BLOCK DIAGRAM |
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VCC |
1 |
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SUPPLY |
8 |
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DRAIN |
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TEA15 x |
VALLEY |
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TEA1620P |
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2 |
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LOGIC |
7 |
GND |
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n.c. |
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100 mV |
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PWM |
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stop |
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6 |
RC |
3 |
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THERMAL |
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OSCILLATOR |
SOURCE |
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low freq |
SHUTDOWN |
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PROTECTION |
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LOGIC |
blank |
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F |
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POWER-UP |
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RESET |
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1.8 |
U |
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overcurrent |
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2.5 V |
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0.5 V |
REG |
4 |
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5 |
10x |
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AUX |
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short circuit winding |
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0.75 V |
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MGT419 |
Fig.1 Block diagram.
2003 June 18 |
4 |
Philips Semiconductors |
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Preliminary specification |
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STARplugTM |
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TEA1620P |
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PINNING |
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SYMBOL |
PIN |
DESCRIPTION |
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TEA1620P |
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VCC |
1 |
supply voltage |
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GND |
2 |
ground |
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RC |
3 |
frequency setting |
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REG |
4 |
regulation input |
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AUX |
5 |
input for voltage from auxiliary winding for timing |
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(demagnetization) |
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SOURCE |
6 |
source of internal MOS switch |
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n.c. |
7 |
not connected |
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DRAIN |
8 |
drain of internal MOS switch; input for start-up current |
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and valley sensing |
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handbook, halfpage
VCC |
1 |
8 |
DRAIN |
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GND |
2 |
7 |
n.c. |
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52xP |
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RC |
3 |
TEA1620P |
SOURCE |
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6 |
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REG |
4 |
5 |
AUX |
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MGT420 |
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Fig.2 Pin configuration of TEA1620P.
2003 June 18 |
5 |
Philips Semiconductors |
Preliminary specification |
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STARplugTM |
TEA1620P |
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FUNCTIONAL DESCRIPTION
The TEA1620P is the heart of a compact flyback converter, with the IC placed at the primary side. The auxiliary winding of the transformer can be used for indirect feedback to control the isolated output. This additional winding also powers the IC. A more accurate control of the output voltage and/or current can be implemented with an additional secondary sensing circuit and optocoupler feedback.
The TEA1620P uses voltage mode control. The frequency is determined by the maximum transformer demagnetizing time and the time of the oscillator. In the first case, the converter operates in the Self Oscillating Power Supply (SOPS) mode. In the latter case, it operates at a constant frequency, which can be adjusted with external components RRC and CRC. This mode is called Pulse Width Modulation (PWM). Furthermore, a primary stroke is started only in a valley of the secondary ringing. This valley switching principle minimizes capacitive switch-on losses.
Start-up and under voltage lock-out
Initially, the IC is self supplying from the rectified mains voltage. The IC starts switching as soon as the voltage on
pin VCC passes the VCC(start) level. The supply is taken over by the auxiliary winding of the transformer as soon as
VCC is high enough and the supply from the line is stopped for high efficiency operation.
As soon as the voltage on pin VCC drops below the
VCC(stop) level, the IC stops switching and restarts from the rectified mains voltage.
Oscillator
The frequency of the oscillator is set by the external resistor and capacitor on pin RC. The external capacitor is
charged rapidly to the VRC(max) level and, starting from a new primary stroke, it discharges to the VRC(min) level. Because the discharge is exponential, the relative
sensitivity of the duty factor to the regulation voltage at low duty factor is almost equal to the sensitivity at high duty factors. This results in a more constant gain over the duty factor range compared to PWM systems with a linear sawtooth oscillator. Stable operation at low duty factors is easily realized. For high efficiency, the frequency is reduced as soon as the duty factor drops below a certain value. This is accomplished by increasing the oscillator charge time.
Duty factor control
The duty factor is controlled by the internal regulation voltage and the oscillator signal on pin RC. The internal
regulation voltage is equal to the external regulation voltage (minus 2.5 V) multiplied by the gain of the error amplifier (typical 20 dB (10 ×)).
Valley switching
A new cycle is started when the primary switch is switched on (see Fig.3). After a certain time (determined by the oscillator voltage RC and the internal regulation level), the switch is turned off and the secondary stroke starts. The internal regulation level is determined by the voltage on pin REG. After the secondary stroke, the drain voltage shows an oscillation with a frequency of approximately
1
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(2 × π × (Lp × Cp))
where Lp is the primary self inductance and Cp is the parasitic capacitance on the drain node.
As soon as the oscillator voltage is high again and the secondary stroke has ended, the circuit waits for a low drain voltage before starting a new primary stroke.
Figure 3 shows the drain voltage together with the valley signal, the signal indicating the secondary stroke and the RC voltage.
The primary stroke starts some time before the actual valley at low ringing frequencies, and some time after the actual valley at high ringing frequencies. Figure 4 shows a typical curve for a reflected output voltage N × Vo of 80 V. This voltage is the output voltage Vo (see Fig.5) transferred to the primary side of the transformer with the factor N (determined by the turns ratio of the transformer). Figure 4 shows that the system switches exactly at minimum drain voltage for ringing frequencies of 480 kHz, thus reducing the switch-on losses to a minimum.
At 200 kHz, the next primary stroke is started at 33° before the valley. The switch-on losses are still reduced significantly.
Demagnetization
The system operates in discontinuous conduction mode all the time. As long as the secondary stroke has not ended, the oscillator will not start a new primary stroke. During the first tsuppr seconds, demagnetization recognition is suppressed. This suppression may be necessary in applications where the transformer has a large leakage inductance and at low output voltages.
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