Diodes AP65200 User Manual

A

C

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LIGHT LOAD IMPROVED 2A SYNCH DC/DC BUCK CONVERTER

high

Pin Assignments

Applications

 Gaming Consoles
 Flat Screen TV Sets and Monitors
 Set Top Boxes
 Distributed Power Systems
 Home Audio
 Consumer Electronics
 Network Systems
 FPGA, DSP and ASIC Supplies
 Green Electronics

Description

The AP65200 is a 340kHz switching frequency external compensated

synchronous DC/DC buck converter. It has integrated low R

DSON

and low side MOSFETs.

The AP65200 enables continues load current of up to 2A with

efficiency as high as 95%.

The AP65200 implements an automatic custom light load

efficiency improvement algorithm.

The AP65200 features current mode control operation, which enables

fast transient response times and easy loop stabilization.

The AP65200 simplifies board layout and reduces space

requirements with its high level of integration and minimal need for

external components, making it ideal for distributed power

architectures.

The AP65200 is available in a standard Green SO-8, MSOP-8EP,

NEW PRODUCT

U-DFN2626-10 and SO-8EP package and is RoHS compliant.

Features

 VIN 4.7V to 18V
 2A Continuous Output Current, 3A Peak
 Efficiency Up to 95%
 Automated Light Load improvement
 V
 340kHz Switching Frequency
 External Programmable Soft-Start
 Enable Pin
 OCP and Thermal Protection
 Totally Lead-Free & Fully RoHS Compliant (Notes 1 & 2)
 Halogen and Antimony Free. “Green” Device (Note 3)

Notes: 1. No purposely added lead. Fully EU Directive 2002/95/EC (RoHS) & 2011/65/EU (RoHS 2) compliant.

2. See http://www.diodes.com/quality/lead_free.html for more information about Diodes Incorporated’s definitions of Halogen- and Antimony-free, "Green"
and Lead-free.

3. Halogen- and Antimony-free "Green” products are defined as those which contain <900ppm bromine, <900ppm chlorine (<1500ppm total Br + Cl) and
<1000ppm antimony compounds.

Adjustable to 0.925 to 16V

OUT

Typical Applications Circuit

100

5V

IN

95

P65200

)

(

IEN

EFFI

AP65200

Document number: DS35548 Rev. 6 - 2

12V

90

85

80

75

IN

LOAD CURRENT (A)

Effici ency vs . Load Current

V = 3.3V

OUT

2.01.80.20.0 0.60.4 1.00.8 1.41.2 1.6

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Figure 1 Typical Application Circuit

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Pin Descriptions

Pin Number

Pin

Name

BS 1 2

IN 2 3

SW 3 4

GND 4 5. 6 Ground

FB 5 7

COMP 6 8

SO-8

SO-8EP

MSOP-8EP

NEW PRODUCT

EN 7 9

SS 8 10

AGND NA 1 Analog GND

PAD Exposed PAD for thermal performance improvement connect to GND

Functional Block Diagram

U-DFN2626-10

P65200

Function

High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET a

0.01µF or greater capacitor from SW to BS to power the high side switch.

Power Input. IN supplies the power to the IC, as well as the step-down converter switches. Drive
IN with a 4.7V to 18V power source. Bypass IN to GND with a suitably large capacitor to eliminate
noise on the input to the IC. See Input Capacitor.

Power Switching Output. SW is the switching node that supplies power to the output. Connect the
output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to
power the high-side switch.

Feedback Input. FB senses the output voltage and regulates it. Drive FB with a resistive voltage
divider connected to it from the output voltage. The feedback threshold is 0.925V. See Setting the
Output Voltage.

Compensation Node. COMP is used to compensate the regulation control loop. Connect a series
RC network from COMP to GND. In some cases, an additional capacitor from COMP to GND is
required. See Compensation Components.

Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to turn on the
regulator; low to turn it off.

Attach EN to IN with a 100kΩ pull up resistor for automatic startup. With this configuration an
internal voltage clamp ensures that a safe voltage is set for Enable not to exceed the absolute
maximum voltage for this pin.

Soft-Start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GND to
set the soft-start period. A 0.1µF capacitor sets the soft-start period to 15ms. To disable the soft­start feature, leave SS floating.

AP65200

Document number: DS35548 Rev. 6 - 2

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Absolute Maximum Ratings (Note 4) (@T

Symbol Parameter Rating Unit

VIN

VSW

VBS

VFB

VEN

V

COMP

TST

TJ

TL

ESD Susceptibility (Note 5)

HBM Human Body Model 1.5 kV

MM Machine Model 150 V

Notes: 4. Stresses greater than the 'Absolute Maximum Ratings' specified above may cause permanent damage to the device. These are stress ratings only;
functional operation of the device at these or any other conditions exceeding those indicated in this specification is not implied. Device reliability may
be affected by exposure to absolute maximum rating conditions for extended periods of time.

5. Semiconductor devices are ESD sensitive and may be damaged by exposure to ESD events. Suitable ESD precautions should be taken when

NEW PRODUCT

handling and transporting these devices.

Supply Voltage

Switch Node Voltage

Bootstrap Voltage

Feedback Voltage -0.3V to +6.0 V

Enable/UVLO Voltage -0.3V to +6.0 V

Comp Voltage -0.3V to +6.0 V

Storage Temperature -65 to +150 °C

Junction Temperature +160 °C

Lead Temperature +260 °C

= +25°C, unless otherwise specified.)

A

-0.3 to +20

-1.0 to V

V

-0.3 to VSW +6.0

SW

IN

+0.3

Thermal Resistance (Note 6)

P65200

V

V

V

Symbol Parameter Rating Unit

SO-8 119

θJA

θJC

Note: 6. Test condition: SO-8: Device mounted on 1"x1" FR-4 substrate PCB, 2oz copper, with minimum recommended pad layout.

SO-8EP: Device mounted on 2"x2" FR-4 substrate PCB, 2oz copper, with minimum recommended pad layout and thermal vias to bottom layer GND

plane.
MSOP-8EP: Device mounted on 2"x2" FR-4 substrate PCB, 2oz copper, with minimum recommended pad layout.
U-DFN2626-10: Device mounted on 2"x2" FR-4 substrate PCB, 2oz copper, with minimum recommended pad layout.

Recommended Operating Conditions (Note 7) (@T

Symbol Parameter Min Max Unit

VIN

TA

Note: 7. The device function is not guaranteed outside of the recommended operating conditions.

AP65200

Document number: DS35548 Rev. 6 - 2

Supply Voltage

Operating Ambient Temperature Range

Junction to Ambient

Junction to Case

= +25°C, unless otherwise specified.)

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SO-8EP 40

MSOP-8EP 48

U-DFN2626-10 53

SO-8 31

SO-8EP 9

MSOP-8EP 9

U-DFN2626-10 8.5

4.7

-40

18.0 V

+85 °C

°C/W

°C/W

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Electrical Characteristics (@T

Symbol Parameter Test Conditions Min Typ Max Unit

IIN

IIN

R

DS(ON)1

R

DS(ON)2

I

LIMIT

I

LIMIT

Shutdown Supply Current

Supply Current (Quiescent)

High-Side Switch On-Resistance (Note 8) 130 mΩ

Low-Side Switch On-Resistance (Note 8) 130 mΩ

HS Current Limit Minimum Duty Cycle 4.4 A

LS Current Limit From Drain to Source 0.9 A

High-Side Switch Leakage Current

AVEA

Error Amplifier Voltage Gain
(Note 8)

GEA Error Amplifier Transconductance

COMP to Current Sense
Transconductance

Oscillator Frequency

Fold-back Frequency

Maximum Duty Cycle

Minimum On Time 130 ns

Feedback Voltage

NEW PRODUCT

GCS

FSW

FFB

D

MAX

TON

VFB

Feedback Overvoltage Threshold 1.1 V

V

EN_RISING

EN Rising Threshold 0.7 0.8 1.2 V

EN Lockout Threshold Voltage 2.2 2.5 2.7 V

EN Lockout Hysteresis 220 mV

INUV

INUV

V

VTH

VIN Under Voltage Threshold Hysteresis

HYS

Under Voltage Threshold Rising

IN

Soft-Start Current

Soft-Start Period

TSD

Note: 8. Guaranteed by design.

Thermal Shutdown (Note 8) 160 °C

AP65200

Document number: DS35548 Rev. 6 - 2

= +25°C, VIN = 12V, unless otherwise specified.)

A

VEN = 0V

VEN = 2.0V, VFB = 1.0V

V

= 0V, VSW = 0V, V

EN

SW

=12V

800 V/V

∆I

= ±10µA

C

2.8 A/V

V

= 0.75V

FB

V

= 0V

FB

VFB = 800mV

TA = -40°C to +85°C

3.80 4.05 4.40 V

250 mV

V

= 0V

SS

C

= 0.1µF

SS

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P65200

0.3 3.0 µA

0.6 1.5 mA

0 10 μA

1000 µA/V

300 340 380 kHz

0.30

90 %

900 925 950 mV

6 μA

15 ms

fSW

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Y

C

R

R

OUTPU

T VOLTAG

F

C

OLT

G

Typical Performance Characteristics (@T

0.40

= +25°C, VIN = 12V, V

A

= 3.3V, unless otherwise specified.)

OUT

0.024

P65200

NEW PRODUCT

0.35

0.30

0.25

0.20

0.15

0.10

QUIESCENT SUPPLY CURRENT (mA)

0.05

0.00
0 5 10 15 20

Quiescent Supply Current vs. Input Voltage

4.65

4.60

4.55

4.50

4.45

4.40

INPUT VOLTAGE (V)

0.022

0.020

0.018

ENT (µA)

U

0.016

0.014

0.012

0.010

WN SUPPL

0.008

SHUTD

0.006

0.004
0 5 10 15 20

3.330

3.329

3.328

3.327

E (V)

3.326

3.325

Shutdown Supply Current vs. Input Voltage

INPUT VOLTAGE (V)

V = 12V

IN

4.35

4.30

CURRENT LIMIT (A)

4.25

4.20

4.15

-50 0 50 100
TEMPERATURE (°C)

Current Limit vs. Temperature

0.932

0.930

0.928

E (V)

0.926

A

0.924

K V

0.922

EEDBA

0.920

0.918

3.324

3.323

3.322

3.321

3.320

4.75 9.75 14.75 19.75 24.75

344

343

342

341

340

339

338

OSCILLATOR FREQUENCY (KHZ)

337

INPUT VOLTAGE (V)

Line Regulation

0.916

-50 0 50 100

AP65200

Document number: DS35548 Rev. 6 - 2

TEMPERATURE (°C)

Feedback Voltage vs. Temperature

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336

-50 0 50 100
TEMPERATURE (°C)

Oscillator Frequency vs. Temperature

© Diodes Incorporated

January 2014

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F

FIC

N

C

Y

F

FICIENCY

C

C

Y

Typical Performance Characteristics (cont.) (@T

95

5V

85

IN

12V

IN

75

(%)

65

IE

E

55

18V

IN

= +25°C, VIN = 12V, V

A

100

95

(%)

90

85

E

= 3.3V, unless otherwise specified.)

OUT

5V

IN

12V

IN

18V

IN

P65200

80

75

LOAD CURRENT (A)

Efficiency vs. Load Current

V = 3.3V

OUT

2.01.80.20.0 0.60.4 1.00.8 1.41.2 1.6

NEW PRODUCT

45

35

100

1.0

1.20.00.20.40.6 1.82.01.4 1.60.8

LOAD CURRENT (A)

Efficiency vs. Load Current

V = 1.2V

OUT

95

12V

IN

90

18V

IN

(%)

IEN

EFFI

85

80

75

70

65

60

0.0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 2.01.81.6
LOAD CURRENT

Efficiency vs. Load Current

V = 5V

OUT

AP65200

Document number: DS35548 Rev. 6 - 2

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Typical Performance Characteristics (cont.)

(@TA = +25°C, VIN = 12V, V

Steady State Test 2A

= 3.3V, L = 3.3µH, C1 = 22µF, C2 = 47µF, unless otherwise specified.)

OUT

Startup Through Vin No Load

P65200

Startup Through Vin 2A Load

NEW PRODUCT

Time-2µs/div

Load Transient Test 0.15 to 2A

Time-500µs/div

Short Circuit Test

Time-20µs/div

Load Transient Test 2A to 0.15A

Time-5ms/div

Shutdown Through Vin no load

Time-20ms/div

Short Circuit Recovery

Time-50µs/div

Time-5ms/div

Shutdown Through Vin 2A

Time-100µs/div

Load Transient Test 0.15 to 2A

Time-20µs/div

Time-20µs/div

AP65200

Document number: DS35548 Rev. 6 - 2

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Application Information

Theory of Operation

The AP65200 is a 2A current mode control, synchronous buck regulator with built in power MOSFETs. Current mode control assures excellent

line and load regulation and a wide loop bandwidth for fast response to load transients. The Figure 1 depicts the functional block diagram of

AP65200.

The operation of one switching cycle can be explained as follows. At the beginning of each cycle, HS (high-side) MOSFET is off. The error

amplifier (EA) output voltage is higher than the current sense amplifier output, and the current comparator’s output is low. The rising edge of the

340kHz oscillator clock signal sets the RS Flip-Flop. Its output turns on HS MOSFET. The current sense amplifier is reset for every switching

cycle.

When the HS MOSFET is on, inductor current starts to increase. The current sense amplifier senses and amplifies the inductor current. Since

the current mode control is subject to sub-harmonic oscillations that peak at half the switching frequency, ramp slope compensation is utilized.

This will help to stabilize the power supply. This ramp compensation is summed to the current sense amplifier output and compared to the error

amplifier output by the PWM comparator. When the sum of the current sense amplifier output and the slope compensation signal exceeds the

EA output voltage, the RS Flip-Flop is reset and HS MOSFET is turned off.

For one whole cycle, if the sum of the current sense amplifier output and the slope compensation signal does not exceed the EA output, then the

falling edge of the oscillator clock resets the Flip-Flop. The output of the error amplifier increases when feedback voltage (VFB) is lower than the

NEW PRODUCT

reference voltage of 0.925V. This also increases the inductor current as it is proportional to the EA voltage.

If in one cycle the current in the power MOSFET does not reach the COMP set current value, the power MOSFET will be forced to turn off. When

the HS MOSFET turns off, the synchronous LS MOSFET turns on until the next clock cycle begins. There is a “dead time” between the HS turn

off and LS turn on that prevents the switches from “shooting through” from the input supply to ground.

The voltage loop is compensated through an internal transconductance amplifier and can be adjusted through the external compensation

components.

Enable

Above the ‘EN Rising Threshold’, the internal regulator is turned on and the quiescent current can be measured above this threshold. The enable

(EN) input allows the user to control turning on or off the regulator. To enable the AP65200, EN must be pulled above the ‘EN Lockout Threshold

Voltage’ and to disable the AP65200, EN must be pulled below ‘EN Lockout Threshold Voltage - EN Lockout Hysteresis’

(2.2V - 0.22V = 1.98V).

Automated No-Load and Light-Load Operation

The AP65200 operates in Light load high efficiency mode during light load operation. The advantage of this light load high efficiency mode is low

power loss at no-load and light-load conditions.

The AP65200 automatically detects the output current and enters the light load high efficiency mode. The output current reaches a critical level

at which the transitions between the light-load and heavy current mode occurs. Once the output current exceeds the critical level, the AP65200

transitions from light load high efficiency mode to continuous PWM mode.

External Soft Start

Soft start is traditionally implemented to prevent the excess inrush current. This in turn prevents the converter output voltage from overshooting

when it reaches regulation. The AP65200 has an internal current source with a soft start capacitor to ramp the reference voltage from 0V to

0.925V. The soft start current is 6µA. The soft start sequence is reset when there is a Thermal Shutdown, Under Voltage Lockout (UVLO) or

when the part is disabled using the EN pin.

AP65200

Document number: DS35548 Rev. 6 - 2

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P65200

January 2014

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Application Information (cont.)

External Soft Start (cont.)

External Soft Start can be calculated from the formula below:

DV

I 

Where;

I

C = External Capacitor

DV=change in feedback voltage from 0V to maximum voltage

DT = Soft Start Time

SS

SS

Current Limit Protection

In order to reduce the total power dissipation and to protect the application, AP65200 has cycle-by-cycle current limiting implementation. The

voltage drop across the internal high-side MOSFET is sensed and compared with the internally set current limit threshold. This voltage drop is

sensed at about 30ns after the HS turns on. When the peak inductor current exceeds the set current limit threshold, current limit protection is

activated. During this time the feedback voltage (VFB) drops down. When the voltage at the FB pin reaches 0.3V, the internal oscillator shifts

the frequency from the normal operating frequency of 340kHz to a fold-back frequency of 102kHz. The current limit is reduced to 70% of nominal

current limit when the part is operating at 102kHz. This low fold-back frequency prevents runaway current.

Under Voltage Lockout (UVLO)

NEW PRODUCT

Under Voltage Lockout is implemented to prevent the IC from insufficient input voltages. The AP65200 has a UVLO comparator that monitors

the input voltage and the internal bandgap reference. If the input voltage falls below 4.0V, the AP65200 will latch an under voltage fault. In this

event the output will be pulled low and power has to be re-cycled to reset the UVLO fault.

Over Voltage Protection

When the AP65200 FB pin exceeds 20% of the nominal regulation voltage of 0.925V, the over voltage comparator is tripped and the COMP pin

and the SS pin are discharged to GND, forcing the high-side switch off.

Thermal Shutdown

The AP65200 has on-chip thermal protection that prevents damage to the IC when the die temperature exceeds safe margins. It implements a

thermal sensing to monitor the operating junction temperature of the IC. Once the die temperature rises to approximately +160°C, the thermal

protection feature gets activated. The internal thermal sense circuitry turns the IC off thus preventing the power switch from damage.

A hysteresis in the thermal sense circuit allows the device to cool down to approximately +120°C before the IC is enabled again through soft

start. This thermal hysteresis feature prevents undesirable oscillations of the thermal protection circuit.

Setting the Output Voltage

The output voltage can be adjusted from 0.925V to 16V using an external resistor divider. Table 1 shows a list of resistor selection for common

output voltages. Resistor R1 is selected based on a design tradeoff between efficiency and output voltage accuracy. For high values of R1 there

is less current consumption in the feedback network. However the trade off is output voltage accuracy due to the bias current in the error

amplifier. R1 can be determined by the following equation:

*C

DT

= Soft Start Current

V

R



2

1



0.925





OUT

R

 1







P65200

Figure 2 Feedback Divider Network

AP65200

Document number: DS35548 Rev. 6 - 2

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V

(V)

OUT

5 44.2 10

3.3 26.1 10

2.5 16.9 10

1.8 9.53 10

1.2 3 10

R1 (kΩ) R2 (kΩ)

Table 1 Resistor Selection for Common Output

Voltages

January 2014

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Application Information (cont.)

Compensation Components

The AP65200 has an external COMP pin through which system stability and transient response can be controlled. COMP pin is the output of the

internal trans-conductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to control the characteristics of

the control system. The DC gain of the voltage feedback loop is given by:

V

FB

Where V

amplifier voltage gain. The control loop transfer function incorporates two poles one is due to the compensation capacitor (C3) and the output

resistor of error amplifier, and the other is due to the output capacitor and the load resistor. These poles are located at:

Where G

One zero is present due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at:

NEW PRODUCT

The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency where

the feedback loop has the unity gain is crucial.

A rule of thumb is to set the crossover frequency to below one-tenth of the switching frequency. Use the following procedure to optimize the

compensation components:

1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine the R3 value by the following equation:

Where f

2. Choose the compensation capacitor (C3) to achieve the desired phase margin set the compensation zero, f
crossover frequency to provide sufficient phase margin. Determine the C3 value by the following equation:

Where R3 is the compensation resistor value.

is the feedback voltage (0.925V), R

FB

G

f



P1

is the error amplifier trans-conductance.

EA

f



Z1

3R 



is the crossover frequency, which is typically less than one tenth of the switching frequency.

C

3C



EA

A3C2



1

3R3C2



fc2C2



GG



CSEA

2

fc3R



VEA

V

V

OUT

FB

AGRA 

VEACSLOADVDC

f

P2



G

EA

V

V

OUT

is the load resistor value, GCS is the current sense trans-conductance and A

LOAD





OUT

(V)

1.2 22 47 3.24 6.8 3.3

1.8 22 47 6.8 6.8 3.3

2.5 22 47 6.8 6.8 10

3.3 22 47 6.8 6.8 10

5 22 47 6.8 6.8 10

12 22 47 6.8 6.8 15

Table 2 Recommended Component Selection

1

R2C2



V

fs1.02C2



G

CS

CIN/C1

(µF)

LOAD

OUT

V

FB

C

OUT

(µF)

/C2

RC/R3

(kΩ)

CC/C3

(nF)

L1

(µH)

, to below one fourth of the

Z1

Inductor

Calculating the inductor value is a critical factor in designing a buck converter. For most designs, the following equation can be used to calculate

the inductor value;



)V(VV

OUTINOUT



Where

And

L

∆I

is the inductor ripple current.

L

f

is the buck converter switching frequency.

SW



AP65200

Document number: DS35548 Rev. 6 - 2

f∆IV

SWLIN

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P65200

is the error

VEA

January 2014

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Application Information (cont.)

Inductor (cont.)

Choose the inductor ripple current to be 30% of the maximum load current. The maximum inductor peak current is calculated from:

∆I

II

LOADL(MAX)

Peak current determines the required saturation current rating, which influences the size of the inductor. Saturating the inductor decreases the

converter efficiency while increasing the temperatures of the inductor and the internal MOSFETs. Hence choosing an inductor with appropriate

saturation current rating is important.

A 1µH to 10µH inductor with a DC current rating of at least 25% percent higher than the maximum load current is recommended for most

applications.

For highest efficiency, the inductor’s DC resistance should be less than 200mΩ. Use a larger inductance for improved efficiency under light load

conditions.

Input Capacitor

The input capacitor reduces the surge current drawn from the input supply and the switching noise from the device. The input capacitor has to

sustain the ripple current produced during the on time on the upper MOSFET. It must hence have a low ESR to minimize the losses.

NEW PRODUCT

The RMS current rating of the input capacitor is a critical parameter that must be higher than the RMS input current. As a rule of thumb, select an

input capacitor which has RMs rating that is greater than half of the maximum load current.

Due to large dI/dt through the input capacitors, electrolytic or ceramics should be used. If a tantalum must be used, it must be surge protected.

Otherwise, capacitor failure could occur. For most applications, a 4.7µF ceramic capacitor is sufficient.

Output Capacitor

The output capacitor keeps the output voltage ripple small, ensures feedback loop stability and reduces the overshoot of the output voltage. The

output capacitor is a basic component for the fast response of the power supply. In fact, during load transient, for the first few microseconds it

supplies the current to the load. The converter recognizes the load transient and sets the duty cycle to maximum, but the current slope is limited

by the inductor value.

Maximum capacitance required can be calculated from the following equation:

ESR of the output capacitor dominates the output voltage ripple. The amount of ripple can be calculated from the equation below:

L



2

P65200



∆I

out

inductorcapacitor

inductor

2

2



V)V V(∆

out

An output capacitor with ample capacitance and low ESR is the best option. For most applications, a 22µF ceramic capacitor will be sufficient.

L(I



out



o

is the maximum output voltage overshoot.

Where

C

∆V

AP65200

Document number: DS35548 Rev. 6 - 2

ESR*∆IVout

2

)

2

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P65200

Application Information (cont.)

PC Board Layout

This is a high switching frequency converter. Hence attention must be paid to the switching currents interference in the layout. Switching current

from one power device to another can generate voltage transients across the impedances of the interconnecting bond wires and circuit traces.

These interconnecting impedances should be minimized by using wide, short printed circuit traces.

NEW PRODUCT

External Bootstrap Diode

It is recommended that an external bootstrap diode be added when the input voltage is no greater than 5V or the 5V rail is available in the

system. This helps to improve the efficiency of the regulator. This solution is also applicable for D > 65%. The bootstrap diode can be a low cost

one such as BAT54 or a Schottky that has a low V

Figure 7 External Bootstrap Compensation Components

Recommended Diodes:

AP65200

Document number: DS35548 Rev. 6 - 2

.

F

Part Number

B130 30V, 1A Diodes Inc

SK13 30V, 1A Diodes Inc

Voltage/Current

Rating

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Vendor

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A

Ordering Information

P65200

NEW PRODUCT

Part Number Package Code

AP65200S-13 S SO-8 NA 2500 -13

AP65200SP-13 SP SO-8EP NA 2500 -13

AP65200MP-13 MP MSOP-8EP NA 2500 -13

AP65200FK-7 FK U-DFN2626-10 R2 3000 -7

Note: 9. Pad layout as shown on Diodes Inc. suggested pad layout document AP02001, which can be found on our website at

http://www.diodes.com/datasheets/ap02001.pdf.

Marking Information

(1) SO-8

Packaging

(Note 9)

Identification Code

Tape and Reel

Quantity Part Number Suffix

AP65200

Document number: DS35548 Rev. 6 - 2

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Marking Information (cont.)

(2) SO-8EP

P65200

(3) MSOP-8EP

NEW PRODUCT

(4) U-DFN2626-10

AP65200

Document number: DS35548 Rev. 6 - 2

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Package Outline Dimensions (All dimensions in mm.)

Please see AP02002 at http://www.diodes.com/datasheets/ap02002.pdf for latest version.

(1) SO-8

E1

E

A1

h

Detail ‘A’

°

45

e

D

A2

A3

A

b

L

0.254
Gauge P lane

Seating Plane

7°~9

°

(2) SO-8EP

NEW PRODUCT

Detail ‘A’

Dim Min Max

SO-8

A - 1.75
A1 0.10 0.20
A2 1.30 1.50
A3 0.15 0.25

b 0.3 0.5

D 4.85 4.95

E 5.90 6.10
E1 3.85 3.95

e 1.27 Typ

h - 0.35

L 0.62 0.82

0 8



All Dimensions in mm

P65200

9° (All side s)

(3) MSOP-8EP

D

x

y

1

e

A1

A

85

E1

14

b

4° ± 3°

A

e

A1

D

D1

E

E2

8Xb

A3

A2

D

E3

E1

F

Bottom View

E

N

45

7

°

See Detail C

°

E0

Gauge Plane
Seating Plane

4

c

0.25

X

1

0

Exposed Pad

H

Q

L

°

Detail C

C

Gauge Plane
Seating Plane

4

X

1

0

°

L

SO-8EP (SOP-8L-EP)

Dim Min Max Typ

A 1.40 1.50 1.45

A1 0.00 0.13 -

b 0.30 0.50 0.40

C 0.15 0.25 0.20

D 4.85 4.95 4.90

E 3.80 3.90 3.85

E0 3.85 3.95 3.90
E1 5.90 6.10 6.00

e - - 1.27

F 2.75 3.35 3.05

H 2.11 2.71 2.41

L 0.62 0.82 0.72

N - - 0.35

Q 0.60 0.70 0.65

All Dimensions in mm

MSOP-8EP

Dim Min Max Typ

A - 1.10 ­A1 0.05 0.15 0.10
A2 0.75 0.95 0.86
A3 0.29 0.49 0.39

b 0.22 0.38 0.30

c 0.08 0.23 0.15

D 2.90 3.10 3.00

a

D1 1.60 2.00 1.80

E 4.70 5.10 4.90
E1 2.90 3.10 3.00
E2 1.30 1.70 1.50
E3 2.85 3.05 2.95

e - - 0.65

L 0.40 0.80 0.60

a 0° 8° 4°

x - - 0.750

y - - 0.750

All Dimensions in mm

AP65200

Document number: DS35548 Rev. 6 - 2

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Package Outline Dimensions (cont.) (All dimensions in mm.)

Please see AP02002 at http://www.diodes.com/datasheets/ap02002.pdf for latest version.

(4) U-DFN2626-10

NEW PRODUCT

A

A1

D

D2

C'0.2x45°

(Pin #1 ID)

D2/2

E

E2

0

0

1

.

0

R

e

b

A3

Seating Pla ne

E2/2

L

Suggested Pad Layout

Please see AP02001 at http://www.diodes.com/datasheets/ap02001.pdf for the latest version.

(1) SO-8

X

C2

C1

Y

(2) SO-8EP

X2

Y2

Y1

X1

C

Y

X

AP65200

Document number: DS35548 Rev. 6 - 2

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U-DFN2626-10

Dim Min Max Typ

A 0.57 0.63 0.60
A1 0 0.05 0.03
A3 - - 0.15

b 0.20 0.30 0.25

D 2.55 2.675 2.60
D2 2.05 2.25 2.15

E 2.55 2.675 2.60

E2 1.16 1.36 1.26

e 0.50 BSC

L 0.30 0.40 0.35
All Dimensions in mm

Dimensions Value (in mm)

X 0.60

Y 1.55
C1 5.4
C2 1.27

Dimensions Value (in mm)

C 1.270

X 0.802
X1 3.502
X2 4.612

Y 1.505
Y1 2.613
Y2 6.500

P65200

January 2014

© Diodes Incorporated

A

Y

Suggested Pad Layout (cont.)

Please see AP02001 at http://www.diodes.com/datasheets/ap02001.pdf for the latest version.

3) MSOP-8EP

X C

G

Y

Y2

Y1

X1

NEW PRODUCT

(4) U-DFN2626-10

Y2

Pin1

X2

Dimensions Value (in mm)

X1

Y1

C

X

Dimensions

C 0.650

G 0.450

X 0.450

X1 2.000

Y 1.350
Y1 1.700
Y2 5.300

X 0.45

Y 1.4
C1 4.4
C2 0.65

P65200

Value

(in mm)

AP65200

Document number: DS35548 Rev. 6 - 2

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DIODES INCORPORATED MAKES NO WARRANTY OF ANY KIND, EXPRESS OR IMPLIED, WITH REGARDS TO THIS DOCUMENT,
INCLUDING, BUT NOT LIMITED TO, THE IMPLIED WARRANTIES OF MERCHANTABILITY AND FITNESS FOR A PARTICULAR PURPOSE
(AND THEIR EQUIVALENTS UNDER THE LAWS OF ANY JURISDICTION).

Diodes Incorporated and its subsidiaries reserve the right to make modifications, enhancements, improvements, corrections or other changes
without further notice to this document and any product described herein. Diodes Incorporated does not assume any liability arising out of the
application or use of this document or any product described herein; neither does Diodes Incorporated convey any license under its patent or
trademark rights, nor the rights of others. Any Customer or user of this document or products described herein in such applications shall assume
all risks of such use and will agree to hold Diodes Incorporated and all the companies whose products are represented on Diodes Incorporated
website, harmless against all damages.

Diodes Incorporated does not warrant or accept any liability whatsoever in respect of any products purchased through unauthorized sales channel.
Should Customers purchase or use Diodes Incorporated products for any unintended or unauthorized application, Customers shall indemnify and
hold Diodes Incorporated and its representatives harmless against all claims, damages, expenses, and attorney fees arising out of, directly or
indirectly, any claim of personal injury or death associated with such unintended or unauthorized application.

Products described herein may be covered by one or more United States, international or foreign patents pending. Product names and markings
noted herein may also be covered by one or more United States, international or foreign trademarks.

This document is written in English but may be translated into multiple languages for reference. Only the English version of this document is the
final and determinative format released by Diodes Incorporated.

NEW PRODUCT

Diodes Incorporated products are specifically not authorized for use as critical components in life support devices or systems without the express
written approval of the Chief Executive Officer of Diodes Incorporated. As used herein:

A. Life support devices or systems are devices or systems which:

1. are intended to implant into the body, or

labeling can be reasonably expected to result in significant injury to the user.

B. A critical component is any component in a life support device or system whose failure to perform can be reasonably expected to cause the
failure of the life support device or to affect its safety or effectiveness.

Customers represent that they have all necessary expertise in the safety and regulatory ramifications of their life support devices or systems, and
acknowledge and agree that they are solely responsible for all legal, regulatory and safety-related requirements concerning their products and any
use of Diodes Incorporated products in such safety-critical, life support devices or systems, notwithstanding any devices- or systems-related
information or support that may be provided by Diodes Incorporated. Further, Customers must fully indemnify Diodes Incorporated and its
representatives against any damages arising out of the use of Diodes Incorporated products in such safety-critical, life support devices or systems.

Copyright © 2013, Diodes Incorporated

www.diodes.com

2. support or sustain life and whose failure to perform when properly used in accordance with instructions for use provided in the

IMPORTANT NOTICE

LIFE SUPPORT

P65200

AP65200

Document number: DS35548 Rev. 6 - 2

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January 2014

© Diodes Incorporated