Datasheet TDA5341 Datasheet (Philips)

INTEGRATED CIRCUITS

DATA SH EET

TDA5341

Brushless DC motor and VCM drive
circuit with speed control

Product specification
File under Integrated Circuits, IC11

1997 Jul 10

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

FEATURES

• Full-wave commutation (using push-pull output stages)
without position sensors

• Built-in start-up circuitry

• Three push-pull MOS outputs:

– 1 A output current
– Low voltage drop
– Built-in current limiter

• Thermal protection

• General purpose operational amplifier

• Reset generator

• Motor brake facility

• Actuator driver (H-bridge current-controlled)

• Power-down detector

• Automatic park and brake procedure

• Adjustable park voltage

• Sleep mode

• Speed control with Frequency-Locked Loop (FLL)

• Serial port

• Friction reduction prior to spin-up.

APPLICATIONS

• Hard Disk Drive (HDD).

GENERAL DESCRIPTION

The TDA5341 is a BiCMOS integrated circuit used to drive
brushless DC motors in full-wave mode. The device
senses the rotor position using an EMF sensing technique
and is ideally suited as a drive circuit for a hard disk drive
motor.

The TDA5341 also includes a Voice Coil Motor driver
(VCM), reset and park facilities and an accurate speed
regulator. In addition, a serial port facilitates the control of
the device.

TDA5341

QUICK REFERENCE DATA

Measured over full voltage and temperature range.

SYMBOL PARAMETER MIN. TYP. MAX. UNIT

V

DD

I

oMOT

R

DS(MOT)

I

oACT

R

DS(ACT)

ORDERING INFORMATION

TYPE

NUMBER

TDA5341G LQFP64

general supply voltage for logic and power 4.5 5.0 5.25 V
motor output current 1.3 1.6 1.9 A
motor output resistance − 1.1 1.56 Ω
actuator output current 0.7 1.1 1.4 A
actuator output resistance − 2.0 2.5 Ω

PACKAGE

NAME DESCRIPTION VERSION

plastic low profile quad flat package; 64 leads; body 10 × 10 × 1.4 mm

SOT314-2

1997 Jul 10 2

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

BLOCK DIAGRAM

handbook, full pagewidth

CAPCP

FREDENA

TESTIN

CAPCDM

CAPCDS

CAPTI

CAPST

BRAKE

FG

FMOT

CLOCK

DATA

ENABLE

RESET

ROSC

DPULSE

RETRACT

V

CMIN1

V

CMIN2

V

ref

GAINSEL

CAPXA

27

9

12

18
19

2

1

11

10
58

39
38
42
57

48

35

30

33
34
36

15

CAPXB

UPPER VOLTAGE

THERMAL

SWITCH

ADAPTIVE

COMMUTATION

DELAY

TIMING

OSCILLATOR

START

OSCILLATOR

BRAKE

CONTROLLER

POLES

DIVIDER

SERIAL

PORT

PROGRAMMING

FREQUENCY

DIVIDER

VCM

PREAMPLIFIER

50 14 55 31 49 17

CAPYA

CONVERTER

CAPYB

COMMUTATION

AND
OUTPUT
DRIVING

LOGIC

brake

BAND GAP 1

sleep

fill

DIGITAL

FREQUENCY

COMPARATOR

park

CNTRL

CAPCPC

222463625961

CONTROL

AMPLIFIER

POWER 1

POWER 2

POWER 3

COMPARATORS

BAND GAP 2

UNDER-VOLTAGE

DETECTOR

BRAKE

AFTER PARK

CHARGE

PUMP

SENSE

AMPLIFIER

VCM

H-BRIDGE

CURRENT

LIMIT

CONTROL

TDA5341

25 64 40 16 41

ILIM

TDA5341

23

20

PRESET

60

MOT1

8

MOT2

21

MOT3

7

MOT0

3

CLAMP1

26

CLAMP2

43

RESETOUT

44

UVDIN1

54

UVDIN2

46

BRAKEDELAY

4

AMPOUT

5

AMPIN−

6

AMPIN+

32

FILTER

53

SENSEOUT

52

SENSEIN+

51

SENSEIN−

37

VCM+

45

VCM−

28

FB1

29

FB2

V

EEDVEE1VEE2VEE3VEE4VEEVDD1VDD2VDD3VDDVDDD

Fig.1 Block diagram.

1997 Jul 10 3

MGE817

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit

TDA5341

with speed control

PINNING

SYMBOL PIN DESCRIPTION

CAPST 1 external capacitor for starting oscillator
CAPTI 2 external capacitor for timer circuit
CLAMP1 3 external capacitor used to park the heads; must be externally connected to CLAMP2
AMPOUT 4 uncommitted operational amplifier output
AMPIN− 5 uncommitted operational amplifier invert input
AMPIN+ 6 uncommitted operational amplifier direct input
MOT0 7 motor centre tap input
MOT2 8 motor driver output 2
FREDENA 9 friction reduction mode enable input (active HIGH)
FG 10 frequency generator (tacho) output
BRAKE 11 brake input command (active LOW)
TESTIN 12 test input for power output switch-off (active HIGH)
TP1 13 test purpose 1 (should be left open-circuit)
V

EE1

GAINSEL 15 VCM gain adjustment input (switch ON when GAINSEL is LOW)
V

DD

V

EE

CAPCDM 18 external capacitor for adaptive commutation delay (master)
CAPCDS 19 external capacitor for adaptive commutation delay (slave)
PRESET 20 set the motor drivers into a fixed state: MOT1 = F (floating), MOT2 = L, MOT3 = H
MOT3 21 motor driver output 3
CAPCPC 22 frequency compensation of the current control
ILIM 23 current limit control input
CNTRL 24 motor control
V

DD1

CLAMP2 26 external capacitor used to park the heads; must be externally connected to CLAMP1
CAPCP 27 external capacitor for the charge pump output
FB1 28 output of the VCM preamplifiers
FB2 29 switchable output of the VCM preamplifier
RETRACT 30 park input command (active LOW)
V

EE3

FILTER 32 charge pump output to be connected to an external filter
V

CMIN1

V

CMIN2

DPULSE 35 data pulse input of the frequency comparator of the speed control
V

ref

VCM+ 37 positive output of the VCM amplifier
DATA 38 input data of the serial port (active HIGH)
CLOCK 39 clock input signal to shift DATA into SERIALIN register (active HIGH)
V

DD3

14 ground for the spindle motor drivers

16 general power supply
17 general ground

25 power supply 1 for the spindle motor drivers

31 ground 3 for the actuator driver

33 VCM voltage control input
34 switchable VCM voltage control input

36 voltage reference input

40 power supply 3 for the actuator driver

1997 Jul 10 4

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit

TDA5341

with speed control

SYMBOL PIN DESCRIPTION

V

DDD

ENABLE 42 enable input; enables the serial port, i.e. allows DATA to be shifted in (active LOW)
RESETOUT 43 under-voltage detector output flag (active LOW)
UVDIN1 44 external capacitor for the
VCM− 45 negative output of the VCM amplifier
BRAKEDELAY 46 delay control input for brake after park
TP2 47 test purpose 2 (should be left open-circuit)
ROSC 48 reference oscillator input for motor speed control
V

EE4

V

EED

SENSEIN− 51 inverting input of the VCM sense amplifier
SENSEN+ 52 non-inverting input of the VCM sense amplifier
SENSEOUT 53 output of the VCM sense amplifier
UVDIN2 54 external voltage reference for the under-voltage detector
V

EE2

TP3 56 test purpose 3 (should be left open-circuit)
RESET 57 reset input; forces all bits of the SERIALIN register to 0 (active HIGH)
FMOT 58 tachometer output (one pulse per mechanical revolution)
CAPXB 59 external capacitor for the charge pump output
MOT1 60 motor driver output 1
CAPXA 61 external capacitor for the charge pump output
CAPYA 62 external capacitor for the charge pump output
CAPYB 63 external capacitor for the charge pump output
V

DD2

41 digital power supply

RESETOUT duration

49 ground 4 for the actuator driver
50 digital ground

55 ground 2 for the spindle motor drivers

64 power supply for the spindle motor drivers

1997 Jul 10 5

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

handbook, full pagewidth

DD2

CAPYB

CAPST

CAPTI

CLAMP1

AMPOUT

AMPIN−
AMPIN+

MOT0
MOT2

FREDENA

FG

BRAKE

TESTIN

TP1

V

EE1

GAINSEL

V

DD

V

64
1
2
3
4
5
6
7
8
9

10
11
12
13
14
15
16

17

EE

V

CAPYA

63

62

18

19

CAPCDS

CAPCDM

CAPXA

MOT1

61

60

20

21

MOT3

PRESET

FMOT

CAPXB
59

58

TDA5341

22

23

ILIM

CAPCPC

RESET
57

24

CNTRL

TP3
56

25

DD1

V

EE2

V

UVDIN2

55

54

26

27

CAPCP

CLAMP2

SENSEIN+

SENSEOUT
53

52

28

29

FB2

FB1

EED

SENSEIN−

V

51

50

30

31

EE3

V

RETRACT

EE4

V

49

48
47
46
45
44
43
42
41
40
39
38
37
36
35
34
33

32

FILTER

TDA5341

ROSC
TP2
BRAKEDELAY
VCM−
UVDIN1
RESETOUT
ENABLE

V

DDD

V

DD3

CLOCK
DATA
VCM+
V

ref
DPULSE
V

CMIN2
V

CMIN1

MGE816

Fig.2 Pinning diagram.

1997 Jul 10 6

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

FUNCTIONAL DESCRIPTION

The TDA5341 offers a sensorless three-phase motor
full-wave drive function. The device also offers protected
outputs capable of handling high currents and can be used
with star or delta connected motors.

The TDA5341 can easily be adapted for different motors
and applications.

The TDA5341 offers the following features:

• Sensorless commutation by using the motor EMF

• Built-in start-up circuit

• Optimum commutation, independent of motor type or

motor loading

• Built-in flyback diodes

• Three-phase full-wave drive

• High output current (1.3 A)

• Low MOS R

• Outputs protected by current limitation and thermal

protection of each output transistor

• Low current consumption

• Additional uncommitted operational amplifier

• H-bridge actuator driver current controlled with an

external series sense resistor

• Automatic retract procedure

• Adjustable park voltage

• Sleep mode

• Automatic brake (after park) procedure

DSon

(1 Ω)

TDA5341

• Speed control based on FLL technique

• Serial port DATAIN (24 bits)

• Friction reduction prior to spin-up.

TDA5341 modes description

The TDA5341 can be used in two main modes, depending
on whether they are controlled or not.

The ‘controlled modes’ (user commands) are executed by
the TDA5341 without delay or priority treatment, either by
software via the serial port or by hardware. BRAKE is a
hardware command whereas RETRACT can be controlled
in both ways. If it is preferable to control the heads parking
via the serial bus, the equivalent pin can be left
open-circuit.

The sleep mode is controlled by software only; it results
from the combination of the spindle and actuator being
disabled. The spindle is turned off by bit SPINDLE
DISABLE, whereas the actuator is disabled towards bit
VCM DISABLE of the serial port (see Section “Serial
port”). In addition, a special spin-up mode can be activated
in the event of high head stiction

The ‘uncontrolled modes’ only result from different failures
caused by either a too high internal temperature or an
abnormally low power voltage, which will cause the
actuator to retract and, after the spindle, to brake.
The output signals mainly affected by those failures are
RESETOUT, MOT1, 2 and 3, VCM+ and VCM−. This is
summarised in Tables 1 and 2.

Table 1 Summary of controlled modes

HARDWARE/

SOFTWARE

Software spindle disable high impedance high impedance HIGH spindle off
Software VCM disable not affected high impedance HIGH spindle on; VCM off
Hardware brake LOW not affected HIGH spindle coils ground
Software/

hardware
Hardware friction reduction − not affected HIGH heads in vibration

1997 Jul 10 7

MODE MOT1, 2 AND 3

retract not affected VCM− = 0.65 V;

VCM+ AND

VCM−

VCM+=0V

RESETOUT EFFECT

HIGH heads parked

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

Table 2 Summary of uncontrolled modes

FAILURE MOT1, 2 AND 3 VCM+ AND VCM− RESETOUT EFFECT

Thermal
shut-down

Voltage
shut-down

Controlled modes

S

PINDLE DISABLE

The spindle circuitry is switched off when bit 23 (SPINDLE
DISABLE) of the serial port is pulled HIGH. In that mode,
the reference band gap generator is cut off so that all
internal current sources are disabled. Both the spindle and
actuator outputs will be set to the high impedance state
because the upper converter is also turned off.

It should be noted that the uncommitted operational
amplifier is also disabled in that mode.

VCM

DISABLE

The actuator will be disabled when bit 22 (VCM DISABLE)
is set to logic 1; the spindle circuitry is not affected in that
mode. The retract circuitry also remains active, so that the
heads can be parked although the VCM is disabled. In that
mode, the current consumption can be reduced by ±4 mA.

high impedance → LOW VCM− = 0.65 V;

VCM+ = 0 V

high impedance → LOW VCM− = 0.65 V;

VCM+ = 0 V

RICTION REDUCTION

F
Pulling FREDENA HIGH activates the friction reduction

mode of the TDA5341. In that mode, a clock signal fed via
pin TESTIN will cause the MOT outputs to sequentially
switch-on and switch-off at the same frequency and, as a
result, generate an AC spindle torque high enough to
overcome the head stiction.

Before start-up, the head stiction might be higher than
normal due to condensation between the head(s) and the
disk(s). Normal spin-up is not possible when this friction
torque is higher than the start-up torque of the spindle
motor. Spin-up is then only possible after friction has been
reduced by breaking the head(s) free. Bringing a static
friction system into mechanical resonance is an effective
method to break static friction head(s) free.

The resonance frequency is:

f

res

1



×=

------ -



2π

LOW automatic park and brake

LOW automatic park and brake

C



0.5

--- -



J

TDA5341

S

LEEP MODE

The sleep mode is obtained by pulling both the SPINDLE
and VCM DISABLE bits of the serial port HIGH. The power
monitor circuitry only remains active in sleep mode.

ETRACT

R
Retract is activated by pulling either bit 21 (PARK) HIGH

or RETRACT (pin 30) LOW. WhenRETRACT is set LOW,
a voltage of 0.65 V is applied to pin VCM− for parking.

It should be noted that the park voltage can be made
adjustable by changing one of the interconnect masks.
Accordingly, some different voltages, varying from

0.2 to 1.2 V, can quickly be obtained on customer
demand. This mode does not affect the control of the
spindle rotation.

B

RAKE MODE

The brake mode is activated by pulling BRAKE (pin 11)
LOW. When a voltage of less than 0.8 V is applied to pin
BRAKE, the 3 motor outputs are short-circuited to ground,
which results in a quick reduction of the speed until the
motor stops completely.

Where:

C = Stiffness of the head-spring(s) in direction of disk(s)
rotation, (N/m)

2

J = Inertia of the disk(s), (kg/m

).

The external clock input frequency must be:

f

clk

6



------ -



2π

C



0.5

×=

--- -



J

A burst of n × 6 clock pulse will bring the system into
resonance and break the heads free (n > 2). Once the
heads have been broken free, the normal spin-up
procedure can be applied.

It should be noted that the clock frequency must be smaller
than 40000/CAPCDM (nF).

1997 Jul 10 8

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

Uncontrolled modes

P

OWER SHUT-DOWN

If the power supply decreases to less than the voltage
threshold determined by the ratio between R1 and R2
connected to UVDIN2 (see Fig.8) (for more than 1 µs), the
TDA5341 will issue a reset (RESETOUT goes LOW) and
the following operation will start:

• Firstly, the MOT outputs are switched to the high
impedance state so as to get back the rectified EMF
issued from the motor itself. At the same time, the
voltage upper converter is cut off in order to preserve the
voltage on the charge pump capacitance at CAPCP.
The energy supplied in that way is then used to park the
heads in a safe position

• Secondly, after a certain period of time, depending on
the RC constant of the device connected to
BRAKEDELAY, the lower MOS drivers will be turned on
in order to stop the motor completely.

TDA5341

The system will only function when the EMF voltage from
the motor is present. Consequently, a start oscillator is
provided that will generate commutation pulses when no
zero-crossings in the motor voltage are available.

A timing function is incorporated into the device for internal
timing and for timing of the reverse rotation detection.

The TDA5341 also contains a control amplifier, directly
driving output amplifiers.

The TDA5341 also provides access to the user of some of
its internal test modes. Firstly, a PRESET mode can be
used for prepositioning the three motor output drivers into
a fixed state. By pulling pin PRESET to 0.75 V above V
MOT3 goes HIGH, MOT2 goes LOW and MOT1 goes to
the high impedance state.

In addition, when TESTIN is pulled HIGH (provided that
FREDENA is LOW), the 3 motor output drivers are
switched off. It should be noted that RESETOUT goes
LOW in that particular event.

DD

,

T

HERMAL SHUT-DOWN

Should the temperature of the chip exceed +140 ±10 °C, a
shut-down operation will also be processed. The actions
described for power shut-down will be sequenced in the
same manner.

PINDLE SECTION (see Fig.1)

S
Full-wave driving of a three-phase motor requires three

push-pull output stages. In each of the six possible states
two outputs are active, one sourcing current and one
sinking current. The third output presents a high
impedance to the motor which enables measurement of
the motor EMF in the corresponding motor coil by the EMF
comparator at each output. The commutation logic is
responsible for control of the output transistors and
selection of the correct EMF comparator.

The zero-crossing in the motor EMF (detected by the
comparator selected by the commutation logic) is used to
calculate the correct moment for the next commutation, i.e.
the change to the next output state. The delay is calculated
(depending on the motor loading) by the adaptive
commutation delay block.

Because of high inductive loading the output stages
contain flyback diodes. The output stages are also
protected by a current limiting circuit and by thermal
protection of the six output transistors.

The zero-crossings can be used to provide speed
information such as the tacho signal (FG).

Adjustments

The system has been designed in such a way that the
tolerances of the application components are not critical.
However, the approximate values of the following
components must still be determined:

• The start capacitor; this determines the frequency of the
start oscillator

• The two capacitors in the adaptive commutation delay
circuit; these are important in determining the optimum
moment for commutation, depending on the type and
loading of the motor

• The timing capacitor; this provides the system with its
timing signals.

The start capacitor (CAPST)

This capacitor determines the frequency of the start
oscillator. It is charged and discharged, with a current of

5.5 µA, from 0.05 to 2.2 V and back to 0.05 V. The time

taken to complete one cycle is given by:
t

= (0.78 × C); where C is given in µF.

start

The start oscillator is reset by a commutation pulse and so
is only active when the system is in the start-up mode.
A pulse from the start oscillator will cause the outputs to
change to the next state (torque in the motor). If the
movement of the motor generates enough EMF the
TDA5341 will run the motor.

1997 Jul 10 9

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

If the amount of EMF generated is insufficient, then the
motor will move one step only and will oscillate in its new
position. The amplitude of the oscillation must decrease
sufficiently before the arrival of the next start pulse, to
prevent the pulse arriving during the wrong phase of the
oscillation. The oscillation of the motor is given by:

1

-- ­2

0.5

f

osc

=



×

K

------- -



Π

Where:

K

= torque constant (N.m/A)

t

I = current (A)
p = number of magnetic pole-pairs
J = inertia J (kg/m

Example: J = 6.34 × 10−7 kg/m2, K = 4.5 × 10−3 N.m/A,
p = 6 and I = 0.48 A; thus f
damping, a start frequency of 48.4 Hz can be chosen or
t = 24 ms, thus C = 0.024/0.78 = 0.031 µF, (choose
33 nF).

The Adaptive Commutation Delay
(CAPCDM and CAPCDS)

P

I

××

--- -

t

J

2

).

= 22.7 Hz. Without

osc

TDA5341

During the next commutation period this capacitor
(CAPCDM) is discharged at twice the charging current.
The charging current is 10 µA and the discharging current
20 µA; the voltage range is from 0.87 to 2.28 V.
The voltage must stay within this range at the lowest
commutation frequency of interest, f

10 10×

C

==

-----------------------­f1.41×

6–

7092

------------ ­f

C1

Where C is in nF.
If the frequency is lower, then a constant commutation

delay after the zero-crossing is generated by the discharge
from 2.28 to 0.87 V at 20 µA.

Maximum delay = (0.070 × C) ms: Where C is in nF.
Example: nominal commutation frequency is 3240 Hz and

the lowest usable frequency is 1600 Hz, thus
CAPCDM = 7092/1600 = 4.43 (choose 4.7 nF)

The other capacitor, CAPCDS, is used to repeat the same
delay by charging and discharging with 20 µA. The same
value can be chosen as for CAPCDM. Figure 3 illustrates
typical voltage waveforms.

C1

:

In this circuit capacitor CAPCDM is charged during one
commutation period, with an interruption of the charging
current during the diode pulse.

handbook, full pagewidth

voltage
on CAPCDM

voltage
on CAPCDS

MGE820

Fig.3 CAPCDM and CAPCDS voltage waveforms in normal running mode.

1997 Jul 10 10

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

The Timing Capacitor (CAPTI)

Capacitor CAPTI is used for timing the successive steps
within one commutation period; these steps include some
internal delays.

The most important function is the watchdog time in which
the motor EMF has to recover from a negative diode pulse
back to a positive EMF voltage (or vice-versa). A watchdog
timer is a guarding function that only becomes active when
the expected event does not occur within a predetermined
time.

The EMF usually recovers within a short time if the motor
is running normally (<<ms). However, if the motor is
motionless or rotating in the reverse direction, then the
time can be longer (>>ms).

A watchdog time must be chosen so that it is long enough
for a motor without EMF (still) and eddy currents that may
stretch the voltage in a motor winding. However, it must be
short enough to detect reverse rotation. If the watchdog
time is made too long, then the motor may run in the wrong
direction (with little torque).

TDA5341

The capacitor is charged, with a current of 60 µA, from

0.03 to 0.3 V. Above this level it is charged, with a current
of 5 µA, up to 2.2 V only if the selected motor EMF remains
in the wrong polarity (watchdog function). At the end, or, if
the motor voltage becomes positive, the capacitor is
discharged with a current of 30 µA. The watchdog time is
the time taken to charge the capacitor, with a current of
5 µA, from 0.3 to 2.2 V. The value of CAPTI is given by:

t

6–

C510

×

Where: C is in nF and t is in ms.
Example: If, after switching off, the voltage from a motor

winding is reduced, in 3.5 ms, to within 10 mV (the offset
of the EMF comparator), then the value of the required
timing capacitor is given by:

C = 2.63 × 3.5 = 9.2 (choose 10 nF)
Typical voltage waveforms are illustrated by Fig.4.

m

------- -

1.9

=×=

2.63t

m

handbook, full pagewidth

V

MOT1

voltage
on CAPTI

MGE821

If the chosen value of CAPTI is too small, then oscillations can occur in certain positions of a blocked rotor. If the chosen value is too large, then it is
possible that the motor may run in the reverse direction (synchronously with little torque).

Fig.4 Typical CAPTI and V

voltage waveforms in normal running mode.

MOT1

1997 Jul 10 11

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

Other design aspects

There are other design aspects concerning the application
of the TDA5341 besides the commutation function.
They are as follows:

• Generation of the tacho signal FG

• Motor control

• Current limiting

• Thermal protection.

FG signal

The FG signal is generated in the TDA5341 by using the
zero-crossing of the motor EMF from the three motor
windings and the commutation signal.

Output FG switches from HIGH-to-LOW on all
zero-crossings and LOW-to-HIGH on all commutations
and can source more than 40 µA and sink more than

1.6 mA.
Example: A three-phase motor with 6 magnetic pole-pairs

at 1500 rpm and with a full-wave drive has a commutation
frequency of 25 × 6 × 6 = 900 Hz and generates a tacho
signal of 900 Hz.

Motor control

TDA5341

Current limiting

Outputs MOT1 to MOT3 are protected against high
currents in two ways; current limiting of the ‘lower’ output
transistor and current limiting of the ‘upper’ one.
This means that the current from and to the output stages
is limited.

It is possible to adjust the limiting current externally by
using an external resistor connected between pin ILIM and
ground, the value is determined by the formula:

ILIM

10020

I

Where R = R (min.) = 19.5 kΩ and I
If R < 19.5 kΩ, then I

protection purposes.

Thermal protection

Thermal protection of the six output transistors of the
spindle section is achieved by each transistor having a
thermal sensor that is active when the transistor is
switched on. The transistors are switched off when the
local temperature becomes too high. In that event, a
RESET is automatically generated to the external world by
pulling RESETOUT LOW.

×=

2.54

----------­R

ILIM

is internally limited for device

ILIM

= 1.3 A.

Figure 5 shows the spindle transconductance by giving the
relative output current as a function of the voltage applied
to pin CNTRL.

handbook, halfpage

(% of I

100

I

o

)

max

80

60

40

20

0

05

1234

control voltage (V)

MGE822

Fig.5 Output current control.

Reset section

This circuit provides the following:

• An external signal that sends a

RESETOUT (active
LOW) to the disk drive circuitry at power-up and
power-down

• Causes actuator to retract (PARK).
The power-up reset signal (RESETOUT) applied to

external circuits as a digital output is typically 150 ms after
power-up. In the same way, as soon as VDD goes below a
threshold that is externally set (UVDIN2), RESETOUT
goes LOW. The under voltage detection threshold is
adjustable with external resistors (see Fig.8).

The reset circuitry has a minimum output pulse (100 ms)
even for brief power interruptions (higher than 1 ms).
The pulse duration can be adjusted with an external
capacitor (UVDIN1).

1997 Jul 10 12

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

The power for retraction is received from the rectification
of the EMF of the spindle before it is spun down.
After retraction, a brake procedure is automatically settled.
The time needed for retraction, prior to braking, can be
precisely adjusted with the external RC device connected
to pin BRAKEDELAY. The discharge of the capacitance
across the resistance from VDD− 0.7 V down to 1 V will
provide the desired time constant.

Actuator section

The actuator driver has a control input voltage that is
proportional to the actuator current which is capable of a
closed-loop band-pass frequency higher than 10 kHz.

T

RANSFER FUNCTION

handbook, full pagewidth

C

L1

TDA5341

An operational amplifier input allows passive external
components for compensation and gain setting.
The compensation amplifier is able to be pulled out of a
saturation state within 5 µs and its output swing is
VDD− 1.5 V.

An actuator current-sense amplifier is provided for use by
the disc drive controller. The gain from current-sense
resistor to sense the amplifier output is typically 10 (±3%)
and the output voltage swing is ±1.25 V. An input common
mode range insures operation through all normal coil
voltage excursions. Maximum recovery time from
saturation is 20 µs (typ.).

actuator

input

GAINSEL

T11R

×Z

×

f

C

L2

R

IN1

R

IN2

R

f

V

CMIN2

V

CMIN1

V

ref

SENSEOUT

PREAMP

TDA5341

FB2 FB1

OUTPUT
GAIN 11

R

s

VCM−

SENSE

AMP

SENSEIN−

VCM+ SENSEIN+

MGE825

Fig.6 VCM section application diagram.



×–=

--------------------------------------------------------------------------------------------------------------------

L



R

RfRsRfZ

IN

1

VCM

110 Rs× ZL×+×+×()×

With GAINSEL = HIGH; RIN=R

With GAINSEL = LOW;

R

=

IN

IN1

R

×

IN1RIN2

------------------------------

+

R

IN1RIN2

1997 Jul 10 13

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

Speed control function

Speed control is efficiently achieved by the
frequency-locked loop circuitry which is enabled by bit D20
of the CONTROL register.

Its aim is to keep the tachometer signal set to a reference
programmed by the user via the serial port (see Section
“Serial port”).

The FLL operates as follows:
When power is first applied to the circuit, the FILTER pin is

pulled HIGH so that maximum output current can be
sourced for optimum torque.

FG pulses will appear rapidly so as to provide a ‘clean’
clock signal (FMOT) that will issue one pulse per
mechanical revolution. This may be used for speed
regulation, by re-entering the signal through the DPULSE
pin. Then, after it has been synchronised to the ROSC
clock, it is compared to an accurate reference derived from
the ROSC clock and programmed by the user via the serial
port. The resulting variation in frequency generates a
speed error term that will switch a charge-pump up or
down in order to charge or discharge an external RC filter
(FILTER). The voltage at the FILTER pin is then used as
an input to the current control amplifier that regulates the
current in both upper and lower NMOS transistors.

A velocity regulation based upon (maximum) one
corrective action per mechanical revolution may be
considered insufficient in some applications. That is the
reason why the second input of the FLL circuitry was
intentionally left open-circuit and directly accessible to the
external world via pin DPULSE. In that way, total freedom
is given to the user to use any signal coming out of the
microcontroller in order to regulate the motor velocity with
a finer accuracy.

Moreover, a mixed regulation is also possible: firstly,
the FMOT signal is fed via DPULSE into the FLL circuitry
and then once data is read out off the disc, it is switched to
another clock signal with a higher frequency than FMOT.
Simultaneously, a new division factor is programmed via
the serial port.

It should be noted that there is no need for external
synchronization. However, it is recommended to change
the division factor and the DPULSE clock rate during the
period when FMOT is HIGH.

TDA5341

Serial port

The serial port operates as follows:
When ENABLE is HIGH, the serial port is disabled, which

means the TDA5341 functions regardless of any change
at pins DATA and CLOCK.

When ENABLE is set LOW some set-up time before the
falling edge of CLOCK, the serial port is enabled, i. e. data
is serially shifted into the 24-bit shift register on the falling
edge of the CLOCK signal. The least significant bit
(LSB = DATA 0) is the first in, DATA(23) the MSB is the
last in.

ENABLE goes HIGH, the contents of the shift

When
register are loaded into the internal fixed register
(CONTROL register), it will not change until the next rising
edge of ENABLE.

It should be noted that when RESET goes HIGH it will
force all bits of the shift register and the control register to
logic 0. However, there is no reset effect on both power-up
and power-down i.e there is no correlation between
RESET and RESETOUT.

CLOCK can be stopped (either in the HIGH or LOW state)
once RESET or ENABLE have been asserted.

The 24-bit control register is organized as follows:

• D23: SPINDLE DISABLE
– When LOW, the spindle circuitry is enabled

• D22: VCM DISABLE
– When LOW, the actuator circuitry is enabled

• D21: PARK
– When HIGH, it enables the head retraction. This has

the same effect as pin RETRACT pulled LOW

• D20: FLL ENABLE
– When HIGH, it closes the complete speed regulation

loop

– When LOW, it will set the output of the charge pump

(FILTER) to the high impedance state

• D19 and D18
– The combination of these bits fixes the division factor

to apply on the FG signal with respect to the number
of poles.

1997 Jul 10 14

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

Table 3 Division factor

D19 D18 POLE PAIRS

004
016
108
1112

• D17 to D0
These bits program the division factor to apply to the

ROSC signal so as to generate a reference that will
precisely control the spindle rotation;

– The division factor can range from 8 (DIV = 1) to

– The relationship between this division factor, ROSC

18

8 × [2

− 1] = 2097144 (DIV = 3FFFF)

and the motor frequency is as follows:
DIVISION FACTOR = 7.5 × ROSC/MOTOR speed

where the MOTOR speed is given in rpm and ROSC
in Hz.

TDA5341

Example: for a motor speed of 3600 rpm and a reference
oscillation ROSC of 16 MHz, the division factor that has to
be programmed via the bus, will be:

×

3600

6–

16 10

DIV 7.5

× 33333==

------------------------

The resulting error will be less than 0.04 rpm.

LIMITING VALUES

In accordance with the Absolute Maximum Rating System (IEC 134).

SYMBOL PARAMETER MIN. MAX. UNIT

V

DD

V

i

V

60,8,21

V

45,37,53

V

1,2,18,19

T

stg

T

amb

P

tot

positive supply voltage − 5.5 V
input voltage (all pins) −0.3 VDD+ 0.3 V
output voltage pins MOT1, MOT2 and MOT3 −0.25 +5.5 V
output voltage pins VCM−, VCM+ and SENSEOUT 0.7 VDD+ 0.7 V
input voltage pins CAPST, CAPTI, CAPCDM and CAPCDS − 2.5 V
IC storage temperature −55 +150 °C
operating ambient temperature 0 +70 °C
total power dissipation see Fig.7

HANDLING

Every pin withstands the ESD test in accordance with MIL-STD-883C. Method 3015 (HBM 1900 Ω, 100 pF) 3 pulses
positive and 3 pulses negative on each pin with reference to ground. Class 1 : 0 to 1999 V.

THERMAL CHARACTERISTICS

SYMBOL PARAMETER VALUE UNIT

R

th j-a

thermal resistance from junction to ambient in free air 54 K/W

1997 Jul 10 15

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

3

P

tot

(W)

2

1

0

0 50 150

(2)

(1)

SAFE

OPERATING

AREA

(1) T
(2) T

j(max)
j(max)

handbook, halfpage

= 130 °C.
= 150 °C.

100

T

amb

TDA5341

MGE823

(°C)

Fig.7 Power derating curve.

CHARACTERISTICS (SPINDLE FUNCTION)

V

DD

= 5 V; V

DD1

and V

DD2>VDD

is not allowed; T

=25°C; unless otherwise specified.

amb

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

Supply

V
V

DD
DD1

general supply voltage 4.5 5.0 5.25 V
supply voltage 1 for the spindle

4.5 5.0 5.25 V

motor drivers

V

DD2

supply voltage 2 for the spindle

4.5 5.0 5.25 V

motor drivers

V

DD3

supply voltage for the actuator

4.5 5.0 5.25 V

driver

I

DD

I

q(sm)

general supply current − 11 15 mA
quiescent current in sleep mode − 1.4 2 mA

Thermal protection

T

SD

local temperature at temperature

130 140 150 °C

sensor causing shut-down

∆T reduction in temperature before

after shut-down − T

− 30 −°C

SD

switch-on

V

so

test pin switch-off voltage 2.5 −−V

1997 Jul 10 16

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit

TDA5341

with speed control

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

MOT0

V

i

I

bias

V

CSW

∆V

CWS

MOT1, MOT2 and MOT3; pins 60, 8 and 21

V

DO

t

r

t

f

Output current limiting circuit; V

I

ILIM

V

ILIM

I

ILIM(CR)

input voltage level −0.3 − VDD− 1.7 V
input bias current −1 − 0 µA
comparator switching voltage level note 1 ±6.8 ±9.2 ±11.6 mV
variation in comparator switching

−3.4 − +3.4 mV

voltage levels within one IC

drop-out voltage Io= 250 mA −−0.34 V

I

= 250 mA;

o

T

=70°C

amb

output rise time from 0.2 to 0.8V
output fall time from 0.8 to 0.2V

= 5 V; pin 23

ILIM

limiting current (estimation) R
input voltage I
limiting current control range

(estimation)

=20kΩ 1.15 1.25 1.35 A

ILIM

= 100 µA 2.43 2.51 2.60 V

ILIM

I

=

o

---------------­10000

I

ILIM

−−0.39 V

10 25 35 µs

DD

10 25 35 µs

DD

0.01 − 1.3 A

Output current control circuit; pin 24

V

CNTRL

C

CPC

input voltage level 0 − V
control loop stability capacitor − 100 − nF

CAPCPC; pin 22

I

o(sink)

I

o(source)

output sink current 30 40 50 µA
output source current −5.5 −3.5 −1.5 µA

CAPCP; pin 27

C

extCP

external output capacitor for the
charge pump

I

o(sink)

V

CP

output sink current VDD=0V;

charge pump voltage 9.0 9.9 10.8 V

CAPST; pin 1

I

o(sink)

I

o(source)

V

SW(L)

V

SW(M)

V

SW(H)

output sink current 4.5 6.0 7.5 µA
output source current −7.0 −5.5 −4.0 µA
lower switching level − 0.20 − V
middle switching level − 0.30 − V
upper switching level − 2.20 − V

DD

V

note 2 22 −−nF

− 1 2.5 µA

V

= 1.2 V

clamp

1997 Jul 10 17

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit

TDA5341

with speed control

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

CAPTI; pin 2

I

o(sink)

I

oH(source)

I

oL(source)

V

SW(L)

V

SW(M)

V

SW(H)

CAPCDM; pin 18

I

o(sink)

I

o(source)

I

sink/Isource

V

IL

V

IH

CAPCDS; pin 19

I

o(sink)

I

o(source)

I

sink/Isource

V

IL

V

IH

FG; pin 10

V

OL

I

OL

I

OH

R

F

δ duty factor − 50 − %

output sink current 25 35 45 µA
HIGH level output source current −85 −70 −55 µA
LOW level lower source current −7.5 −5.0 −2.5 µA
lower switching level − 30 − mV
middle switching level − 0.3 − V
upper switching level − 2.2 − V

output sink current 13 20 27 µA
output source current −13.5 −10 −6.5 µA
ratio of sink-to-source current −2.2 −2.0 −1.8
LOW level input voltage 0.82 0.87 0.92 V
HIGH level input voltage 2.20 2.28 2.37 V

output sink current 13 20 27 µA
output source current −27 −20 −13 µA
ratio of sink-to-source current −1.1 −1.0 −0.9 µA
LOW level input voltage 0.82 0.87 0.92 V
HIGH level input voltage 2.20 2.28 2.37 V

LOW level output voltage Io=0µA −−0.5 V
LOW level output current VOL= 1 V 3.3 5.3 − mA
HIGH level output current VOH= 4.5 V −−83 −40 mA
ratio of FG frequency and

− 1 −

commutation frequency

BRAKE; pin 11

I

NM

V

NM

V

BM

I

BM

normal mode current VNM= 2.8 V −40 −27 −µA
normal mode voltage 2.65 − V
brake mode voltage −−2.35 V
brake mode current −40 −24 −µA

Upper converter; pins 61 and 62

C

XA

C

YA

external pump capacitor pin 61 − 10 − nF
external pump capacitor pin 62 − 10 − nF

Notes

1. Switching levels with respect to MOT1, MOT2 and MOT3.

2. CAPCP value is dependant of the powerless park and brake operations.

1997 Jul 10 18

DD

V

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit

TDA5341

with speed control

CHARACTERISTICS (RESET FUNCTION)

V

= 5 V; V

DD

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

UVDIN1; pin 44

I

UVDIN1

V

UVDIN1

UVDIN2; pin 54

V

UVDIN2

I

UVDIN2

RESETOUT; pin 43

V

PTH

t

dPU

t

dPD

t

PDW

t

W(min)

R

pu

V

OL

and V

DD1

DD2>VDD

load capacitance current to

is not allowed; T

=25°C; unless otherwise specified.

amb

−2.3 −1.7 −1.3 µA

control the reset pulse width
input voltage threshold to

2.4 2.55 2.75 V

activate the reset output

comparator voltage for

see Fig.8 1.280 1.315 1.340 V
power-up and power-down
detection

input current V

= 1.6 V −0.5 − +0.5 µA

UVDIN2

power threshold voltage see Fig.9 − 4.25 − V
power-up reset delay C = 0.1 µF;

100 150 200 ms

see Fig.9
power-down reset delay see Fig.9 −−4µs
power-down reset pulse width see Fig.9 1.0 − 4 µs
minimum output pulse width C = 0.1 µF 100 −−ms
pull-up resistance 6 10 14 kΩ
LOW level output voltage IOL= 8.5 mA −−0.5 V

under-voltage threshold 1.32

handbook, halfpage

R2 R1+()

×=

----------------------------­R1

V

DD

UVDIN2

Fig.8 Reset mode threshold.

1997 Jul 10 19

R1R2

MGE818

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

handbook, full pagewidth

V

DD

t

< 1.2 µs

PDW

RESETOUT

t

dPU

t

dPD

t

PDW

> 4 µs

t

W(min)

TDA5341

V

DD

V

PTH

t

d

V

OH

V

OL

MGE819

Fig.9 Reset mode timing.

CHARACTERISTICS (VCM FUNCTION)

V

DD

= 5 V; V

DD1

and V

DD2>VDD

is not allowed; T

=25°C; unless otherwise specified.

amb

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

SENSEIN− and SENSEIN+; pins 51 and 52

V

CS

I

iSENSE

common input sense voltage 0 − V

DD

input sense current −250 − +250 µA

SENSEOUT; pin 53

∆V

SENSE

I

oSENSE

G

SENSE

f

co

V

o(os)

t

RSA

V

; pin 36

ref

V

ref

I

ref

differential output voltage V
output sense current −250 − +250 µA
sense amplifier gain 9.9 10.2 10.5
cross-over frequency − 40 − MHz
output offset voltage I
recovery time from saturation − 20 −µs

reference input voltage 1.9 − 2.6 V
reference input current −5 − +5 µA

= 1.9 to 2.6 V 0.5 V

ref

SENSEIN

=0 −66 − +66 mV

±1.25 4.0 V

ref

V

1997 Jul 10 20

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit

TDA5341

with speed control

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

VCM+ and VCM−; pins 37 and 45

V

CMdo

I

oLIM

G

v

V

oPARK

VCMIN1 and VCMIN2

V

i

I

ibias

I

i(os)

GAINSEL; pin 15

V

IH

V

IL

I

IH

I

IL

R

SW

drop-out voltage Io= 400 mA − 0.8 1.0 V
output current limiting 0.7 1.15 1.5 A
power amplifier voltage gain 9 − 12
output park voltage RL=40Ω; note 1 − 0.75 − V

input voltage level 1.9 − 2.6 V
input bias current −−0.25 µA
input offset current − 25 − nA

HIGH level input voltage 2 −− V
LOW level input voltage −−0.8 V
HIGH level input current −10 − +10 µA
LOW level input current −20 − +10 µA
switch resistance GAINSEL = LOW −−40 Ω

GAINSEL = HIGH 10 −− MΩ

FB1 and FB2; pins 28 and 29

V
∆V

i(os)

FB

input offset voltage −5 − +5 mV
feed-back differential output

voltage

f

co

I

oFB

t

RSB

R

SW

cross-over frequency − 10 − MHz
feed-back output current −250 +250 µA
recovery time from saturation − 5 −µs
switch resistance GAINSEL = LOW −−40 Ω

RETRACT; pin 30

V

IH

V

IL

I

IH

I

IL

HIGH level input voltage 2 −− V
LOW level input voltage −−0.8 V
HIGH level input current −10 − +10 µA
LOW level input current −20 − +10 µA

BRAKEDELAY; pin 46

V

BM

V

NM

brake mode threshold voltage − 0.75 1.0 V
normal mode voltage VDD− 0.85 −− V

VDD= 5.25 V ±0.4 −±V

− 0.45 V

DD

GAINSEL = HIGH 10 −− MΩ

1997 Jul 10 21

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit

TDA5341

with speed control

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

Uncommitted operational amplifier; pins 4 to 6

V

i(os)

I

i(bias)

I

i(os)

V

CM

G

OL

f

co

V

OL

V

OH

Note

1. This is the PARK default value. Other values can be obtained with a metal mask change.

CHARACTERISTICS (SPEED CONTROL FUNCTION)

= 5 V; V

V

DD

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

input offset voltage −3.5 − +3.5 mV
input bias current −250 − +250 nA
input offset current − 25 − nA
common mode voltage 1.7 − 2.6 V
open loop gain − 68 − dB
cross-over frequency − 10 − MHz
LOW level output voltage IOL= 250 µA −−0.7 V
HIGH level output voltage IOH= −250 µA 4.3 −− V

DD1

and V

DD2>VDD

is not allowed; T

=25°C; unless otherwise specified.

amb

FILTER; pin 32

I

o(sink)

I

o(source)

I

sink/Isource

I

 charge pump leakage current −5 − +5 nA

LO

DATA, RESET and

V

IL

V

IH

I

i

output sink current 80 100 120 µA
output source current −110 −90 −70 µA
ratio of sink-to-source current 0.9 1.1 1.2

ENABLE; pins 38, 57 and 42

LOW level input voltage −−0.8 V
HIGH level input voltage 2.4 −− V
input current − 0 −µA

CLOCK; pin 39

V

IL

V

IH

f

clk

LOW level input voltage −−0.8 V
HIGH level input voltage 2.4 −− V
clock frequency −−18 MHz

ROSC; pin 48

V

IL

V

IH

f

refOSC

LOW level input voltage −−0.8 V
HIGH level input voltage 2.4 −− V
reference oscillator frequency 1 − 20 MHz

DPULSE; pin 35

V

IL

V

IH

f

DPULSE

LOW level input voltage −−0.8 V
HIGH level input voltage 2.4 −− V
data pulse frequency −−10 MHz

1997 Jul 10 22

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit

TDA5341

with speed control

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

FMOT; pin 58

V

OL

δ duty factor − 50 − %
Timing; see Fig.10
t

su1

t

su2

t

h

handbook, full pagewidth

LOW level output voltage IOL= 500 µA −−0.1 V

ENABLE set-up time 8 −− ns
DATA set-up time 6 −− ns
DATA hold time 10 −− ns

CLOCK

t

su1

ENABLE

DATA

SHIFTED
DATA

t

su2

t

h

MGE824

Fig.10 Timing diagram.

1997 Jul 10 23

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

APPLICATION INFORMATION

V

DD2

V

V

EE1

+5 V

DD3

V

DD

TDA5341

V

EE2VEE3

V

handbook, full pagewidth

C2 C1

to micro-

controller

R1

CNTRL
FILTER

FREDENA

CLOCK

DATA

ENABLE

RESET

ROSC

TESTIN

RESETOUT

BRAKE

FG

FMOT

DPULSE

CAPCP
CAPXA
CAPXB
CAPYA
CAPYB

CAPCDM

CAPCDS

CAPTI

CAPST

V

DD1

24
32

9
39
38
42
57
48
12
43
11
10
58
35

27
61
59
62
63
18
19
2
1

50 14 55 31 49 17 36

V

EED

DDD

V

EE4

CLAMP1 CLAMP2

2634116406425

V

V

EE

ref

MOT1

60

MOT2

8

MOT3

21

MOT0

7

ILIM

23

CAPCPC

22

UVDIN1

44

UVDIN2

54

RETRACT

30

GAINSEL

15

VCM−

45

VCM+

37

SENSEIN−

51

SENSEIN+

52

SENSEOUT

53

V

CMIN1

33

FB1

28

V

CMIN2

34

FB2

29

BRAKEDELAY

46

C

C

R

L1

L2

TDA5341

SPINDLE
MOTOR

+5 V

R

s

f

R

R

MGE826

IN1

IN2

input

Fig.11 Application diagram of the TDA5341 in a hard disk drive.

1997 Jul 10 24

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

PACKAGE OUTLINE

LQFP64: plastic low profile quad flat package; 64 leads; body 10 x 10 x 1.4 mm

c

y

X

A

48 33

49

Z

32

E

TDA5341

SOT314-2

e

w M

b

p

e

pin 1 index

1.45

1.35

b

0.25

17

16

Z

w M

p

D

H

D

0.27

0.18

0.17

0.12

D

(1)

(1) (1)(1)

D

10.1

10.1

9.9

9.9

v M

B

v M

B

0 2.5 5 mm

scale

eH

H

D

12.15

0.5

11.85

64

1

DIMENSIONS (mm are the original dimensions)

mm

A

A1A2A3bpcE

max.

0.20

1.60

0.05

UNIT

Note

1. Plastic or metal protrusions of 0.25 mm maximum per side are not included.

E

A

12.15

11.85

Q

H

E

E

A

2

A

A

1

detail X

LLpQZywv θ

0.69

0.75

0.45

0.59

0.12 0.11.0 0.2

L

Z

L

D

1.45

1.05

(A )

3

θ

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1.45

1.05

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7

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0

OUTLINE
VERSION

SOT314-2

IEC JEDEC EIAJ

REFERENCES

1997 Jul 10 25

EUROPEAN

PROJECTION

ISSUE DATE

94-01-07
95-12-19

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit
with speed control

SOLDERING
Introduction

There is no soldering method that is ideal for all IC
packages. Wave soldering is often preferred when
through-hole and surface mounted components are mixed
on one printed-circuit board. However, wave soldering is
not always suitable for surface mounted ICs, or for
printed-circuits with high population densities. In these
situations reflow soldering is often used.

This text gives a very brief insight to a complex technology.
A more in-depth account of soldering ICs can be found in
our

“IC Package Databook”

Reflow soldering

Reflow soldering techniques are suitable for all LQFP
packages.

Reflow soldering requires solder paste (a suspension of
fine solder particles, flux and binding agent) to be applied
to the printed-circuit board by screen printing, stencilling or
pressure-syringe dispensing before package placement.

Several techniques exist for reflowing; for example,
thermal conduction by heated belt. Dwell times vary
between 50 and 300 seconds depending on heating
method. Typical reflow temperatures range from
215 to 250 °C.

Preheating is necessary to dry the paste and evaporate
the binding agent. Preheating duration: 45 minutes at
45 °C.

Wave soldering

Wave soldering is not recommended for LQFP packages.
This is because of the likelihood of solder bridging due to
closely-spaced leads and the possibility of incomplete
solder penetration in multi-lead devices.

(order code 9398 652 90011).

TDA5341

If wave soldering cannot be avoided, the following
conditions must be observed:

• A double-wave (a turbulent wave with high upward

pressure followed by a smooth laminar wave)
soldering technique should be used.

• The footprint must be at an angle of 45° to the board

direction and must incorporate solder thieves
downstream and at the side corners.

Even with these conditions, do not consider wave
soldering LQFP packages LQFP48 (SOT313-2),
LQFP64 (SOT314-2) or LQFP80 (SOT315-1).

During placement and before soldering, the package must
be fixed with a droplet of adhesive. The adhesive can be
applied by screen printing, pin transfer or syringe
dispensing. The package can be soldered after the
adhesive is cured.

Maximum permissible solder temperature is 260 °C, and
maximum duration of package immersion in solder is
10 seconds, if cooled to less than 150 °C within
6 seconds. Typical dwell time is 4 seconds at 250 °C.

A mildly-activated flux will eliminate the need for removal
of corrosive residues in most applications.

Repairing soldered joints

Fix the component by first soldering two diagonally­opposite end leads. Use only a low voltage soldering iron
(less than 24 V) applied to the flat part of the lead. Contact
time must be limited to 10 seconds at up to 300 °C. When
using a dedicated tool, all other leads can be soldered in
one operation within 2 to 5 seconds between
270 and 320 °C.

1997 Jul 10 26

Philips Semiconductors Product specification

Brushless DC motor and VCM drive circuit

TDA5341

with speed control

DEFINITIONS

Data sheet status

Objective specification This data sheet contains target or goal specifications for product development.
Preliminary specification This data sheet contains preliminary data; supplementary data may be published later.
Product specification This data sheet contains final product specifications.

Limiting values

Limiting values given are in accordance with the Absolute Maximum Rating System (IEC 134). Stress above one or
more of the limiting values may cause permanent damage to the device. These are stress ratings only and operation
of the device at these or at any other conditions above those given in the Characteristics sections of the specification
is not implied. Exposure to limiting values for extended periods may affect device reliability.

Application information

Where application information is given, it is advisory and does not form part of the specification.

LIFE SUPPORT APPLICATIONS

These products are not designed for use in life support appliances, devices, or systems where malfunction of these
products can reasonably be expected to result in personal injury. Philips customers using or selling these products for
use in such applications do so at their own risk and agree to fully indemnify Philips for any damages resulting from such
improper use or sale.

1997 Jul 10 27

Philips Semiconductors – a worldwide company

Argentina: see South America
Australia: 34 Waterloo Road, NORTH RYDE, NSW 2113,

Tel. [phone], Fax. [phone]
Austria: Computerstr. 6, A-1101 WIEN, P.O. Box 213, Tel. [phone],

Fax. [phone]
Belarus: Hotel Minsk Business Center, Bld. 3, r. 1211, Volodarski Str. 6,

220050 MINSK, Tel. [phone], Fax. [phone]

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Brazil: see South America
Bulgaria: Philips Bulgaria Ltd., Energoproject, 15th floor,

51 James Bourchier Blvd., 1407 SOFIA,
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Canada: PHILIPS SEMICONDUCTORS/COMPONENTS,
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Czech Republic: see Austria
Denmark: Prags Boulevard 80, PB 1919, DK-2300 COPENHAGEN S,

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Indonesia: see Singapore
Ireland: Newstead, Clonskeagh, DUBLIN 14,

Tel. [phone], Fax. [phone]
Israel: RAPAC Electronics, 7 Kehilat Saloniki St, PO Box 18053,

TEL AVIV 61180, Tel. [phone], Fax. [phone]
Italy: PHILIPS SEMICONDUCTORS, Piazza IV Novembre 3,

20124 MILANO, Tel. [phone], Fax. [phone]
Japan: Philips Bldg 13-37, Kohnan 2-chome, Minato-ku, TOKYO 108,

Tel. [phone], Fax. [phone]
Korea: Philips House, 260-199 Itaewon-dong, Yongsan-ku, SEOUL,

Tel. [phone], Fax. [phone]
Malaysia: No. 76 Jalan Universiti, 46200 PETALING JAYA, SELANGOR,

Tel. [phone], Fax. [phone]
Mexico: 5900 Gateway East, Suite 200, EL PASO, TEXAS 79905,

Tel. [phone]

Middle East: see Italy

Netherlands: Postbus 90050, 5600 PB EINDHOVEN, Bldg. VB,

Tel. [phone], Fax. [phone]
New Zealand: 2 Wagener Place, C.P.O. Box 1041, AUCKLAND,

Tel. [phone], Fax. [phone]
Norway: Box 1, Manglerud 0612, OSLO,

Tel. [phone], Fax. [phone]
Philippines: Philips Semiconductors Philippines Inc.,

106 Valero St. Salcedo Village, P.O. Box 2108 MCC, MAKATI,
Metro MANILA, Tel. [phone], Fax. [phone]

Poland: Ul. Lukiska 10, PL 04-123 WARSZAWA,
Tel. [phone], Fax. [phone]

Portugal: see Spain
Romania: see Italy
Russia: Philips Russia, Ul. Usatcheva 35A, 119048 MOSCOW,

Tel. [phone], Fax. [phone]
Singapore: Lorong 1, Toa Payoh, SINGAPORE 1231,

Tel. [phone], Fax. [phone]

Slovakia: see Austria
Slovenia: see Italy
South Africa: S.A. PHILIPS Pty Ltd., 195-215 Main Road Martindale,

2092 JOHANNESBURG, P.O. Box 7430 Johannesburg 2000,
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South America: Rua do Rocio 220, 5th floor, Suite 51,
04552-903 São Paulo, SÃO PAULO - SP, Brazil,
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Spain: Balmes 22, 08007 BARCELONA,
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Sweden: Kottbygatan 7, Akalla, S-16485 STOCKHOLM,
Tel. [phone], Fax. [phone]

Switzerland: Allmendstrasse 140, CH-8027 ZÜRICH,
Tel. [phone], Fax. [phone]

Taiwan: Philips Semiconductors, 6F, No. 96, Chien Kuo N. Rd., Sec. 1,
TAIPEI, Taiwan Tel. [phone], Fax. [phone]

Thailand: PHILIPS ELECTRONICS (THAILAND) Ltd.,
209/2 Sanpavuth-Bangna Road Prakanong, BANGKOK 10260,
Tel. [phone], Fax. [phone]

Turkey: Talatpasa Cad. No. 5, 80640 GÜLTEPE/ISTANBUL,
Tel. [phone], Fax. [phone]

Ukraine: PHILIPS UKRAINE, 4 Patrice Lumumba str., Building B, Floor 7,
252042 KIEV, Tel. [phone], Fax. [phone]

United Kingdom: Philips Semiconductors Ltd., 276 Bath Road, Hayes,
MIDDLESEX UB3 5BX, Tel. [phone], Fax. [phone]

United States: 811 East Arques Avenue, SUNNYVALE, CA 94088-3409,
Tel. [phone]

Uruguay: see South America
Vietnam: see Singapore
Yugoslavia: PHILIPS, Trg N. Pasica 5/v, 11000 BEOGRAD,

Tel. [phone], Fax.[phone]

For all other countries apply to: Philips Semiconductors, Marketing & Sales Communications,
Building BE-p, P.O. Box 218, 5600 MD EINDHOVEN, The Netherlands, Fax. [phone]

© Philips Electronics N.V. 1997 SCA55
All rights are reserved. Reproduction in whole or in part is prohibited without the prior written consent of the copyright owner.

The information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed
without notice. No liability will be accepted by the publisher for any consequence of its use. Publication thereof does not convey nor imply any license
under patent- or other industrial or intellectual property rights.

Internet: http://www.semiconductors.philips.com

Printed in The Netherlands 297027/1200/01/pp28 Date of release: 1997Jul 10 Document order number: 9397 750 02621