Datasheet MP1583DNLF Specification

MP1583

3A, 23V, 385KHz

Step-Down Converter

The Future of Analog IC Technology

DESCRIPTION

The MP1583 is a step-down regulator with a built-in internal Power MOSFET. It achieves 3A of continuous output current over a wide input supply range with excellent load and line regulation.

Current mode operation provides fast transient response and eases loop stabilization.

Fault condition protection includes cycle-by-cycle current limiting and thermal shutdown. An adjustable soft-start reduces the stress on the input source at startup. In shutdown mode the regulator draws 20A of supply current.

The MP1583 requires a minimum number of external components, providing a compact solution.

FEATURES

• 3A Output Current

• Programmable Soft-Start

• 100m Internal Power MOSFET Switch

• Stable with Low ESR Output Ceramic Capacitors

• Up to 95% Efficiency

• 20A Shutdown Mode

• Fixed 385KHz Frequency

• Thermal Shutdown

• Cycle-by-Cycle Over Current Protection

• Wide 4.75V to 23V Operating Input Range

• Output Adjustable from 1.22V to 21V

• Under-Voltage Lockout

APPLICATIONS

• Distributed Power Systems

• Battery Chargers

• Pre-Regulator for Linear Regulators

TYPICAL APPLICATION

INPUT

4.75V to 23V

OPEN =

AUTOMATIC

STARTUP

CERAMIC

10μ F

2

7

EN

8

10nF

MP1583

SS

GND COMP

BSIN

1

SW

FB

64

B330A

5.6nF

3.9kΩ

3

5

10nF

15μ H

10.5kΩ

10kΩ

“MPS” and “The Future of Analog IC Technology” are Registered Trademarks of Monolithic Power Systems, Inc.

Efficiency Curve

V

= 10V

IN

OUTPUT

2.5V 3A

22μ F CERAMIC

100

90

V

80

70

EFFICIENCY (%)

60

50

OUT

0 0.5 1.0 1.5 2.0 2.5 3.0 3.5

LOAD CURRENT (A)

=2.5V

V

OUT

=5.0V

=3.3V

MP1583_EC01

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

ORDERING INFORMATION

Part Number* Package Top Marking Free Air Temperature (TA)

MP1583DN SOIC8E MP1583DN MP1583DP PDIP8 MP1583DP

–40°C to +85°C –40°C to +85°C

* For Tape & Reel, add suffix –Z (e.g. MP8736DL–Z)

For RoHS compliant packaging, add suffix –LF (e.g. MP8736DL–LF–Z)

PACKAGE REFERENCE

TOP VIEW

SOIC8N/PDIP8

BS

1

IN

2

SW

3

GND

4

EXPOSED PAD

(SOIC8N ONLY)

CONNECT TO PIN 4

ABSOLUTE MAXIMUM RATINGS

(1)

Supply Voltage VIN.......................–0.3V to +28V

Switch Voltage V Bootstrap Voltage V

................. –1V to VIN + 0.3V

SW

....VSW – 0.3V to VSW + 6V

BS

FB, COMP and SS Pins.................–0.3V to +6V

Continuous Power Dissipation (T

= +25°C)

A

(2)

SOIC8E...................................................... 2.5W

PDIP8 ........................................................ 1.2W

Junction Temperature...............................150°C

Lead Temperature ....................................260°C

Storage Temperature ............. –65°C to +150°C

Recommended Operating Conditions

(3)

Input Voltage VIN............................4.75V to 23V

Operating Junct. Temp (T

)...... -40°C to +125°C

J

SS

8

EN

7

COMP

6

FB

5

MP1583_PD01

Thermal Resistance

(4)

θ

JA

θJC

SOIC8E .................................. 50...... 10... °C/W

PDIP8 .................................... 104 ..... 45... °C/W

Notes:

1) Exceeding these ratings may damage the device.

2) The maximum allowable power dissipation is a function of the maximum junction temperature T ambient thermal resistance 

. The maximum allowable continuous power dissipation at

T

A

any ambient temperature is calculated by P T

)/JA. Exceeding the maximum allowable power dissipation

A

will cause excessive die temperature, and the regulator will go into thermal shutdown. Internal thermal shutdown circuitry protects the device from permanent damage.

3) The device is not guaranteed to function outside of its operating conditions.

4) Measured on JESD51-7, 4-layer PCB

(MAX), the junction-to-

J

, and the ambient temperature

JA

(MAX)=(TJ(MAX)-

D

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

ELECTRICAL CHARACTERISTICS

VIN = 12V, TA = +25°C, unless otherwise noted.

Parameters Symbol Condition Min Typ Max Units

Shutdown Supply Current VEN = 0V 20 30 µA

Supply Current VEN = 2.8V, VFB =1.4V 1.0 1.2 mA

Feedback Voltage VFB

Error Amplifier Voltage Gain A

VEA

Error Amplifier Transconductance GEA

High-Side Switch On-Resistance R

Low-Side Switch On-Resistance R

DS(ON)1

DS(ON)2

4.75V ≤ V

400 V/V

ΔI

COMP

0.1 

10 

≤ 23V

IN

= ±10A

High-Side Switch Leakage Current VEN = 0V, VSW = 0V 0 10 µA

Current Limit 4.0 4.9 6.0 A

Current Sense to COMP Transconductance GCS 3.8 A/V

Oscillation Frequency fS 335 385 435 KHz

Short Circuit Oscillation Frequency VFB = 0V 25 40 55 KHz

Maximum Duty Cycle D

VFB = 1.0V 90 %

MAX

Minimum Duty Cycle VFB = 1.5V 0 %

EN Shutdown Threshold Voltage 0.9 1.2 1.5 V

Enable Pull Up Current VEN = 0V 1.1 1.8 2.5 µA

EN UVLO Threshold VEN Rising 2.37 2.54 2.71 V

EN UVLO Threshold Hysteresis 210 mV

Soft-Start Period CSS = 0.1µF 10 ms

Thermal Shutdown 160

1.194 1.222 1.250 V

500 800 1120 µA/V

°C

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

TYPICAL PERFORMANCE CHARACTERISTICS

Efficiency Curve

VIN = 7V

100

90

V

=2.5V

80

70

EFFICIENCY (%)

60

50

0 0.5 1.0 1.5 2.0 2.5 3.0 3.5

V

EN

5V/div.

V

OUT

2V/div.

OUT

V

LOAD CURRENT (A)

V

OUT

=5.0V

=3.3V

MP1583-TPC01

Soft-Start

CSS Open, V

1.5A Resistive Load

V

EN

5V/div.

V

OUT

2V/div.

I

L

1A/div.

V

EN

5V/div.

V

OUT

2V/div.

= 10V, V

IN

OUT

= 3.3V,

MP1583-TPC02

I

1A/div.

L

MP1583-TPC03

1A/div.

I

L

1ms/div.

PIN FUNCTIONS

Pin # Name Description

1 BS

2 IN

3 SW

4 GND Ground. (Note: For the SOIC8E package, connect the exposed pad on backside to Pin 4).

5 FB

6 COMP

High-Side Gate Drive Bootstrap Input. BS supplies the drive for the high-side N-Channel MOSFET switch. Connect a 4.7nF or greater capacitor from SW to BS to power the high-side switch.

Power Input. IN supplies the power to the IC. Drive IN with a 4.75V to 23V power source. Bypass

IN to GND with a suitably large capacitor to eliminate noise on the input to the IC. See Input Capacitor

Power Switching Output. SW is the switching node that supplies power to the output. Connect the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch.

Feedback Input. FB senses the output voltage and regulates it. Drive FB with a resistive voltage

divider from the output voltage. The feedback threshold is 1.222V. See Setting the Output Voltage

Compensation Node. COMP is used to compensate the regulation control loop. Connect a series

RC network from COMP to GND to compensate the regulation control loop. See Compensation

MP1583-TPC04

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

PIN FUNCTIONS (continued)

Pin # Name Description

Enable/UVLO. A voltage greater than 2.71V enables operation. For complete low current shutdown the EN pin voltage needs to be at less than 900mV. When the

7 EN

voltage on EN exceeds 1.2V, the internal regulator will be enabled and the soft-start capacitor will begin to charge. The MP1583 will start switching after the EN pin voltage reaches 2.71V. There is 7V zener connected between EN and GND. If EN is driven by external signal, the voltage should never exceed 7V.

8 SS

Soft-Start Control Input. SS controls the soft-start period. Connect a capacitor from SS to GND to set the soft-start period. To disable the soft-start feature, leave SS unconnected.

OPERATION

The MP1583 is a current-mode step-down regulator. It regulates input voltages from 4.75V to 23V down to an output voltage as low as 1.222V, and is able to supply up to 3A of load current.

The MP1583 uses current-mode control to regulate the output voltage. The output voltage is measured at FB through a resistive voltage divider and amplified through the internal error amplifier. The output current of the transconductance error amplifier is presented at COMP where a RC network compensates the regulation control system.

The voltage at COMP is compared to the internally measured switch current to control the output voltage.

The converter uses an internal N-Channel MOSFET switch to step-down the input voltage to the regulated output voltage. Since the MOSFET requires a gate voltage greater than the input voltage, a boost capacitor connected between SW and BS drives the gate. The capacitor is internally charged when SW is low.

An internal 10 switch from SW to GND is used to insure that SW is pulled to GND when SW is low in order to fully charge the BS capacitor.

IN

EN

2

1.2V

7

2.54V

FREQUENCY

FOLDBACK

COMPARATOR

+

SHUTDOWN

-- COMPARATOR

COMPARATOR

--

+

INTERNAL

REGULATORS

OSCILLATOR

LOCKOUT

+

--

5

CURRENT

SENSE

40/385KHz

7V

1.222V0.7V

FB

SLOPE

COMP

CLK

1μ A

--

+

ERROR

AMPLIFIER

GM = 800μ A/V

AMPLIFIER

Σ

+

--

6

COMP

CURRENT

COMPARATOR

+

--

SRQ

Q

1.8V

8

SS

Figure 1—Functional Block Diagram

5V

1

BS

3

SW

4

GND

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

APPLICATION INFORMATION

COMPONENT SELECTION

Setting the Output Voltage

The output voltage is set using a resistive voltage divider from the output voltage to the FB pin. The voltage divider divides the output voltage down to the feedback voltage by the ratio:

2

R

VV

=

OUTFB

Where V

is the feedback voltage and V

FB

the output voltage.

Thus the output voltage is:

VV

22.1

OUT

×=

A typical value for R2 can be as high as 100k, but a typical value is 10k. Using that value, R1 is determined by:

OUT

For example, for a 3.3V output voltage, R2 is 10k, and R1 is 17k.

Inductor

The inductor is required to supply constant current to the output load while being driven by the switched input voltage. A larger value inductor will result in less ripple current and lower output ripple voltage. However, larger value inductors have a larger physical size, higher series resistance, and/or lower saturation current. A good rule for determining the inductance to use is to allow the inductor peak-to-peak ripple current to be approximately 30% of the maximum switch current limit. Also, make sure that the peak inductor current is below the maximum switch current limit. The inductance value can be calculated by:

21

RR

+

is

OUT

RR

21

+

R

2

))(22.1(18.81 Ω−×= kVVR

Choose an inductor that will not saturate under the maximum inductor peak current.

The peak inductor current can be calculated by:

⎞

V

OUT

⎟ ⎟

V

IN

⎠

Where I

II

LOADLP

is the load current.

LOAD

V

+=

OUT

S

⎛ ⎜

1

−×

⎜

Lf2

××

⎝

Table 1 lists a number of suitable inductors from various manufacturers. The choice of which inductor to use mainly depends on the price vs. size requirements and any EMI requirements.

Table 1—Inductor Selection Guide

Package

Dimensions

Vendor/

Model

Sumida

CR75 Open Ferrite 7.0 7.8 5.5

CDH74 Open Ferrite 7.3 8.0 5.2

CDRH5D28 Shielded Ferrite 5.5 5.7 5.5

CDRH6D28 Shielded Ferrite 6.7 6.7 3.0

CDRH104R Shielded Ferrite 10.1 10.0 3.0

Toko

D53LC

Type A

D75C Shielded Ferrite 7.6 7.6 5.1

D104C Shielded Ferrite 10.0 10.0 4.3

D10FL Open Ferrite 9.7 1.5 4.0

Coilcraft

DO3308 Open Ferrite 9.4 13.0 3.0

DO3316 Open Ferrite 9.4 13.0 5.1

Core Type

Shielded Ferrite 5.0 5.0 3.0

Core

Material

(mm)

WL H

V

OUT

=

ΔIf

×

LS

Where V

L

is the input voltage, fS is the 385KHz

IN

switching frequency and I

⎛ ⎜

1

−×

⎜ ⎝

is the peak-to-peak

L

⎞

V

OUT

⎟

V

IN

⎠

inductor ripple current.

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

V

Output Rectifier Diode

The output rectifier diode supplies the current to the inductor when the high-side switch is off. Use a Schottky diode to reduce losses due to the diode forward voltage and recovery times.

Choose a diode whose maximum reverse voltage rating is greater than the maximum input voltage, and whose current rating is greater than the maximum load current. Table 2 lists example Schottky diodes and manufacturers.

Table 2—Diode Selection Guide

Diode

SK33 30V, 3A Diodes Inc.

SK34 40V, 3A Diodes Inc.

B330 30V, 3A Diodes Inc.

B340 40V, 3A Diodes Inc.

MBRS330 30V, 3A On Semiconductor

MBRS340 40V, 3A On Semiconductor

oltage/Current

Rating

Manufacture

Input Capacitor

The input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the AC current to the step-down converter while maintaining the DC input voltage. Use low ESR capacitors for the best performance. Ceramic capacitors are preferred, but tantalum or low-ESR electrolytic capacitors will also suffice.

Since the input capacitor absorbs the input switching current it requires an adequate ripple current rating. The RMS current in the input capacitor can be estimated by:

⎛

V

⎜

OUT

×

−×=

II

1

LOADC

1

⎜ ⎜

V

IN

⎝

⎞

V

⎟

OUT

⎟ ⎟

V

IN

⎠

The input capacitor can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor (i.e. 0.1F) should be placed as close to the IC as possible.

When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at the input. The input voltage ripple caused by capacitance can be estimated by:

⎞

V

OUT

⎟

V

IN

⎠

V

OUT

IN

⎛ ⎜

1

−××

⎜ ⎝

I

V

IN

LOAD

=Δ

×

S

V

Cf

1

Where C1 is the input capacitance value.

Output Capacitor

The output capacitor is required to maintain the DC output voltage. Ceramic, tantalum or low ESR electrolytic capacitors are recommended. Low ESR capacitors are preferred so as to keep the output voltage ripple low. The output voltage ripple can be estimated by:

⎛

V

OUT

=Δ

S

⎛ ⎜

1

−×

⎜

Lf

×

⎝

⎞

V

OUT

V

⎜

⎟

IN

⎠

+×

R

ESR

⎜ ⎝

1

××

Cf

28

S

Where L is the inductor value, C2 is the output capacitance value and R

is the equivalent

ESR

series resistance (ESR) value of the output capacitor.

In the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance, which is the main cause for the output voltage ripple. For simplification, the output voltage ripple can be estimated by:

⎞ ⎟

⎟ ⎠

The worst-case condition occurs at V where:

I

I =

LOAD

1

C

2

For simplification, choose an input capacitor whose RMS current rating is greater than half of

IN

= 2V

OUT

,

ΔV

OUT

=

In the case of tantalum or electrolytic capacitors, the ESR dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated to:

the maximum load current.

ΔV ×

OUT

V

OUT

2

×××

S

V

=

S

OUT

×

⎛

1

⎜

Lf

⎝

⎛ ⎜

−×

1

⎜

CLf

28

⎝

V

⎞

OUT

−×

⎟

IN

V

⎠

⎞

V

OUT

⎟

V

IN

⎠

R

ESR

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

The MP1583 can be optimized for a wide range of capacitance and ESR values.

Compensation Components

The MP1583 employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the COMP pin. COMP is the output of the internal transconductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the control system.

The DC gain of the voltage feedback loop is:

V

AGRA ×××=

VEACSLOADVDC

Where A G

is the current sense transconductance and

CS

R

is the load resistor value.

LOAD

is the error amplifier voltage gain,

VEA

FB

V

OUT

The system has two poles of importance. One is due to the compensation capacitor (C3) and the output resistor of error amplifier while the other is due to the output capacitor and the load resistor. These poles are located at:

G

f××=

1

P

EA

32

π

AC

VEA

In this case, a third pole set by the compensation capacitor (C6) and the compensation resistor (R3) is used to compensate the effect of the ESR zero on the loop gain. This pole is located at:

f

=

3

P

1

π

362

RC

××

The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency (where the feedback loop has unity gain) is important.

Lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system instability. A good standard is to set the crossover frequency to approximately one-tenth of the switching frequency. The switching frequency for the MP1583 is 385KHz, so the desired crossover frequency is around 38KHz.

Table 3 lists the typical values of compensation components for some standard output voltages with various output capacitors and inductors. The values of the compensation components have been optimized for fast transient responses and good stability at given conditions.

Where G

=

2

P

is the error amplifier

EA

1

RCf××

22

π

LOAD

transconductance.

The system has one zero of importance, due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at:

f

=

1

Z

1

π

332

RC

××

The system may have another zero of importance, if the output capacitor has a large capacitance and/or a high ESR value. The zero due to the ESR and capacitance of the output capacitor is located at:

ESR

=

1 22

π

RCf××

ESR

Table 3—Compensation Values for Typical

Output Voltage/Capacitor Combinations

(Please reference Fig. 3 and Fig. 4)

V

C2 R3 C3 C6

OUT

2.5V

3.3V

5V

12V

2.5V

3.3V

5V

12V

22F

Ceramic

22F

Ceramic

22F

Ceramic

22F

Ceramic

560F Al.

30m ESR

560F Al

30m ESR

470F Al.

30m ESR

220F Al.

30m ESR

3.9k 5.6nF None

4.7k 4.7nF None

7.5k 4.7nF None

16.9k 1.5nF None

91k 1nF 150pF

120k 1nF 120pF

100k 1nF 120pF

169k 1nF 39pF

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

To optimize the compensation components for conditions not listed in Table 2, the following procedure can be used.

1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine R3 by the following equation:

V

f2C2

Where f

3R ×

=

is the desired crossover frequency

C

××π

GG

×

CSEA

OUT

C

V

FB

(which typically has a value no higher than 38KHz).

2. Choose the compensation capacitor (C3) to achieve the desired phase margin. For applications with typical inductor values, setting the compensation zero, f

, below one forth of

Z1

the crossover frequency provides sufficient phase margin. Determine C3 by the following equation:

3C

>

4

f3R2

××π

C

Where R3 is the compensation resistor value.

3. Determine if the second compensation capacitor (C6) is required. It is required if the ESR zero of the output capacitor is located at less than half of the 385KHz switching frequency, or if the following relationship is valid:

PCB Layout Guide

PCB layout is very important to achieve stable operation. Please follow these guidelines and take Figure2 and 3 for references.

1) Keep the path of switching current short and minimize the loop area formed by Input cap, high-side and low-side MOSFETs.

2) Keep the connection of low-side MOSFET between SW pin and input power ground as short and wide as possible.

3) Ensure all feedback connections are short and direct. Place the feedback resistors and compensation components as close to the chip as possible.

4) Route SW away from sensitive analog areas such as FB.

5) Connect IN, SW, and especially GND respectively to a large copper area to cool the chip to improve thermal performance and long-term reliability. For single layer, do not solder exposed pad of the IC

5

FB

R1 R2 C6

C3

R3

SGND

C4

R4

8

SS/REFBS

7

EN

6

COMP

1

××π

R2C2

ESR

If this is the case, then add the second compensation capacitor (C6) to set the pole f at the location of the ESR zero. Determine C6 by the equation:

6C

×

=

f

S

<

2

C5

IN

SW

GND

1

2

3

4

L1

P3

C1

R2C

ESR

3R

PGND

D1

C2

Figure 2―PCB Layout (Single Layer)

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

C6

R4

8

SS/REFBS

1

C2

7 EN

IN 2

C4 R3 C3

6

5FB

COMP

SW

GND

3

4

R1

R2

SGND

L1

C1

PGND

D1

C5

Top Layer

External Bootstrap Diode

An external bootstrap diode may enhance the efficiency of the regulator, the applicable conditions of external BST diode are:

z V

z Duty cycle is high: D=

=5V or 3.3V; and

OUT

V

OUT

>65%

V

IN

In these cases, an external BST diode is recommended from the output of the voltage regulator to BST pin, as shown in Fig.4

External BST Diode

BST

MP1583

SW

IN4148

C

BST

5V or 3.3V

+

L

C

OUT

Figure 4—Add Optional External Bootstrap

Diode to Enhance Efficiency

The recommended external BST diode is IN4148, and the BST cap is 0.1~1µF.

Bottom Layer

Figure 3―PCB Layout (Double Layer)

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

TYPICAL APPLICATION CIRCUITS

INPUT

4.75V to 23V

OPEN = AUTOMATIC

STARTUP

10μ F/25V CERAMIC

C1

Figure 5—3.3V output 3A solution with Murata 22µF, 10V Ceramic Output Capacitor

2

7

EN

8

SS

GND COMP

C4 10nF

MP1583

C6

NS

BSIN

1

SW

FB

64

C3

4.7nF R3

4.7kΩ

C5

10nF

L1

3

5

D1

15μ H

R1

16.9kΩ

R2 10kΩ

OUTPUT

3.3V 3A

C2 22μ F/10V Murata

PACKAGE INFORMATION

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

SOIC8E (EXPOSED PAD)

PIN 1 ID

0.013(0.33)

0.020(0.51)

0.189(4.80)

0.197(5.00)

85

0.150(3.80)

0.157(4.00)

14

TOP VIEW

0.051(1.30)

0.067(1.70) SEATING PLANE

0.000(0.00)

0.006(0.15)

0.050(1.27) BSC

FRONT VIEW

0.228(5.80)

0.244(6.20)

BOTTOM VIEW

SEE DETAIL "A"

GAUGE PLANE

0.010(0.25) BSC

0.124(3.15)

0.136(3.45)

SIDE VIEW

0.010(0.25)

0.020(0.50)

0.089(2.26)

0.101(2.56)

0.0075(0.19)

0.0098(0.25)

o

x 45

0.024(0.61)

0.063(1.60)

0.050(1.27)

0o-8

o

0.016(0.41)

0.050(1.27)

DETAIL "A"

0.103(2.62)

0.213(5.40)

NOTE:

1) CONTROL DIMENSION IS IN INCHES. DIMENSION IN BRACKET IS IN MILLIMETERS.

2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.

3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH

0.138(3.51)

RECOMMENDED LAND PATTERN

OR PROTRUSIONS.

4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.004" INCHES MAX.

5) DRAWING CONFORMS TO JEDEC MS-012, VARIATION BA.

6) DRAWING IS NOT TO SCALE.

MP1583 – 3A, 23V, 385KHz STEP-DOWN CONVERTER

PDIP8

0.387 (9.830)

0.367 (9.322)

0.040 (1.016)

0.020 (0.508)

PIN 1 IDENT.

0.260 (6.604)

0.240 (6.096)

0.065 (1.650)

0.050 (1.270)

0.035 (0.889)

0.015 (0.381)

0.140(3.556)

0.120(3.048)

0.100 BSC(2.540)

0.021(0.533)

0.015(0.381)

0.325(8.255)

0.300(7.620)

0.014 (0.356)

0.008 (0.200)

0.392(9.957)

0.332(8.433)

0.145(3.683)

0.134(3.404)

3°~11° Lead Bend

NOTE:

1) Control dimension is in inches. Dimension in bracket is millimeters.

NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications.

Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications.