Datasheet MP1469GJ Datasheet (MPS)

MP1469

The Future of Analog IC Technology

DESCRIPTION

The MP1469 is a high-frequency, synchronous, rectified, step-down, switch-mode converter with internal power MOSFETs. It offers a very compact solution to achieve a 1.5A continuous output current over a wide input supply range, with excellent load and line regulation. The MP1469 has synchronous-mode operation for higher efficiency over the output current-load range.

Current-mode operation provides fast transient response and eases loop stabilization.

Protection features include over-current protection and thermal shutdown.

The MP1469 requires a minimal number of readily-available, standard, external components and is available in a space-saving 6-pin TSOT23 package.

High-Efficiency, 1.5A, 16V, 500kHz

Synchronous, Step-Down Converter

In 6 Pin SOT 23

FEATURES

• Wide 4.7V-to-16V Operating Input Range

• 255m/160m Low-R

Internal Power

DS(ON)

MOSFETs

• Proprietary Switching-Loss–Reduction

Technique

• High-Efficiency Synchronous-Mode

Operation

• Fixed 500kHz Switching Frequency

• AAM Power-Save Mode for High Efficiency

at Light Load

• Internal Soft-Start

• Over-Current Protection and Hiccup

• Thermal Shutdown

• Output Adjustable from 0.8V

• Available in a 6-pin TSOT-23 package

APPLICATIONS

• GameStations

• Digital Set-Top Boxes

• Flat-Panel Television and Monitors

• General Purposes

All MPS parts are lead-free and adhere to the RoHS directive. For MPS green status, please visit MPS website under Products, Quality Assurance page.

“MPS” and “The Future of Analog IC Technology” are registered trademarks of Monolithic Power Systems, Inc.

TYPICAL APPLICATION

VIN

GND

EN

1

5

IN

U1

MP1469

EN

GND

2

BST

SW

FB

4

3

R3

6

59k

3.3V/1.5A VOUT

R1

40.2k

R2 13k

100

95

90

85

80

75

70

65

60

55

50

0.01 0.1 1 10

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

ORDERING INFORMATION

Part Number* Package Top Marking

MP1469GJ TSOT23-6 ADM

* For Tape & Reel, add suffix –Z (e.g. MP1469GJ–Z);

PACKAGE REFERENCE

TOP VIEW

ABSOLUTE MAXIMUM RATINGS

(1)

VIN ..................................................-0.3V to 17V

V

......................................................................

SW

-0.3V (-5V for <10ns) to 17V (19V for <10ns)

V

......................................................... VSW+6V

BS

All Other Pins...................................–0.3V to 6V

Continuous Power Dissipation (T

= +25°C)

A

(2)

........................................................... 0.57W

Junction Temperature...............................150°C

Lead Temperature ....................................260°C

Storage Temperature................. -65°C to 150°C

Recommended Operating Conditions

(3)

Supply Voltage VIN...........................4.7V to 16V

Output Voltage V Operating Junction Temp. (T

.................... 0.8V to Vin-3V

OUT

). -40°C to +125°C

J

Thermal Resistance

(4)

θ

JA

θJC

TSOT-23-6............................. 220 .... 110.. °C/W

Notes:

1) Exceeding these ratings may damage the device.

2) The maximum allowable power dissipation is a function of the maximum junction temperature T ambient thermal resistance 

. The maximum allowable continuous power dissipation at

T

A

any ambient temperature is calculated by P (MAX)-TA)/JA. Exceeding the maximum allowable power dissipation will cause excessive die temperature, and the regulator will go into thermal shutdown. Internal thermal shutdown circuitry protects the device from permanent damage.

3) The device is not guaranteed to function outside of its operating conditions.

4) Measured on JESD51-7, 4-layer PCB.

(MAX), the junction-to-

J

, and the ambient temperature

JA

(MAX) = (T

D

J

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

ELECTRICAL CHARACTERISTICS

(5)

VIN = 12V, TA = 25°C, unless otherwise noted.

Parameter Symbol Condition Min Typ Max Units

Supply Current (Shutdown) IIN VEN = 0V 1 A

Supply Current (Quiescent) Iq VEN = 2V, VFB = 1V 0.83 mA

HS Switch-On Resistance HS

LS Switch-On Resistance LS

Switch Leakage SW

Current Limit

AAM Peak Current I

(5)

I

AAM_PEAK

Oscillator Frequency fSW VFB=0.75V 400 490 580 kHz

Maximum Duty Cycle D

Minimum On Time

(5)

t

ON_MIN

Feedback Voltage VFB 776 800 824 mV

EN Rising Threshold V

EN Falling Threshold V

EN_RISING

EN_FALLING

V

RDS-ON

Vcc=5V 160 m

RDS-ON

VEN = 0V, VSW =12V 1 A

LKG

2.5 3.0 A

LIMIT

=5V 255 m

BST-SW

0.5 A

VFB=700mV 88 92 %

MAX

90 ns

1.4 1.5 1.6 V

1.23 1.32 1.41 V

EN Input Current IEN

VEN=2V 1.6 A

=0 0 A

V

EN

VIN Under-Voltage Lockout Threshold—Rising

VIN Under-Voltage Lockout Threshold—Hysteresis

INUV

3.85 4.2 4.55 V

Vth

340 mV

HYS

Soft-Start Period tSS 1 ms

Thermal Shutdown

Thermal Hysteresis

Notes:

5) Guaranteed by design.

(5)

150 °C

(5)

20 °C

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

TYPICAL CHARACTERISTICS

VIN = 12V, V

= 3.3V, L = 6.5µH, TA = +25°C, unless otherwise noted.

OUT

100

95

90

85

80

75

EFFICIENCY (%)

70

65

60

0.01 0.1 1 10 0.01 0.1 1 10 0.01 0.1 1 10

100

90

80

70

60

EFFICIENCY (%)

50

40

0.01 0.1 1 10

LOAD CURRENT (A)

100

95

90

85

80

75

70

65

60

55

50

LOAD CURRENT (A)

2

1.5

1

0.5

0

-0.5

-1

REGULATION (%)

-1.5

-2 0 0.3 0.6 0.9 1.2 1.5

LOAD CURRENT (A)

100

95

90

85

80

75

70

65

60

55

50

LOAD CURRENT (A)

2

1.5

1

0.5

0

-0.5

-1

-1.5

-2 5678910111213141516

INPUT VOLTAGE (V)

Peak Current vs. Duty Cycle

4.0

3.8

3.6

3.4

3.2

3.0

2.8

2.6

PEAK CURRENT (A)

2.4

2.2

2.0 01020304050607080 90

DUTY CYCLE (%)

30

25

20

15

10

5

0

0.0 0.3 0.6 0.9 1.2 1.5 LOAD CURRENT (A)

870

860

850

840

830

820

810

800

46810121416

INPUT VOLTAGE (V)

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

TYPICAL CHARACTERISTICS (continued)

VIN = 12V, V

= 3.3V, L = 6.5µH, TA = +25°C, unless otherwise noted.

OUT

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

TYPICAL PERFORMANCE CHARACTERISTICS

VIN = 12V, V

Startup through Input Voltage

I

OUT

= 3.3V, L = 6.5µH, TA = +25°C, unless otherwise noted.

OUT

Shutdown through Input Voltage

= 0A

I

OUT

= 0A

Startup through Input Voltage

I

= 1.5A

OUT

V

OUT

2V/div.

V

10V/div.

V

SW

5V/div.

500mA/div.

V

OUT

2V/div.

V

10V/div.

V

SW

5V/div.

1A/div.

IN

I

L

Shutdown through Input Voltage

I

= 1.5A

OUT

IN

I

L

V

OUT

2V/div.

V

10V/div.

V

SW

5V/div.

200mA/div.

V

OUT

2V/div.

V

EN

2V/div.

V

SW

10V/div.

500mA/div.

IN

I

L

Startup through Enable

I

= 0A

OUT

I

L

V

OUT

2V/div.

V

10V/div.

V

SW

5V/div.

1A/div.

V

OUT

2V/div.

V

EN

2V/div.

V

SW

10V/div.

500mA/div.

IN

I

L

Shutdown through Enable

I

= 0A

OUT

I

L

V

OUT

2V/div.

V

2V/div.

V

SW

10V/div.

1A/div.

Startup through Enable

I

= 1.5A

OUT

EN

I

L

Shutdown through Enable

I

= 1.5A

OUT

V

OUT

2V/div.

V

EN

2V/div.

V

SW

10V/div.

I

L

1A/div.

V

OUT/AC

50mV/div.

V

IN/AC

200mV/div.

V

SW

10V/div.

1A/div.

Input/Output Ripple

I

= 1.5A

OUT

I

L

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

TYPICAL PERFORMANCE CHARACTERISTICS (continued)

VIN = 12V, V

= 3.3V, L = 6.5µH, TA = +25°C, unless otherwise noted.

OUT

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

PIN FUNCTIONS

Package

Pin #

1 IN

Name Description

Supply Voltage. The MP1469 operates from a 4.7V-to-16V input rail. Requires C1 to decouple the input rail. Connect using a wide PCB trace.

2 GND System Ground. Reference ground of the regulated output voltage: requires extra care

during PCB layout. Connect to GND with copper traces and vias.

3 SW Switch Output. Connect using wide PCB trace.

4 BST

5 EN

Bootstrap. Connect a capacitor and a resistor between SW and BS pins to form a floating supply across the high-side switch driver. Recommend to use 1uF BST capacitor.

EN=HIGH to enable the MP1469. For automatic start-up, connect EN to V

using a 100k

IN

resistor.

Feedback. Set the output voltage with from the tap of an external resistor divider running

6 FB

from the output to GND. The frequency fold-back comparator lowers the oscillator frequency when the FB voltage is below 200mV to prevent current-limit runaway during a short circuit fault.

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

BLOCK DIAGRAM

IN

VCC Regulator

Currrent Sense Amplifer

+

-

RSEN

EN

FB

6.5V

1MEG

Reference

20k

Oscillator

+

1.2pF

47pF

500k

+ +

-

Error Amplifier

-

Current Limit Comparator

Comparator On Time Control Logic Control

Figure 1: Functional Block Diagram

Bootstrap

Regulator

BST

HS Driver

SW

VCC

LS Driver

GND

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

OPERATION

The MP1469 is a high-frequency, synchronous, rectified, step-down, switch-mode converter with internal power MOSFETs. It offers a very compact solution to achieve a 1.5A continuous output current over a wide input supply range, with excellent load and line regulation.

The MP1469 operates in a fixed-frequency, peak-current–control mode to regulate the output voltage. An internal clock initiates the PWM cycle to turn on the integrated high-side power MOSFET. This MOSFET remains on until its current reaches the value set by the COMP voltage. When the power switch is off, it remains off until the next clock cycle starts. If the current in the power MOSFET does not reach the COMP set current value within 90% of one PWM period, the power MOSFET is forced to turn off.

Internal Regulator

The 5V internal regulator powers most of the internal circuits. This regulator takes V operates in the full V exceeds 5.0V, the regulator output is in full regulation. When V output decreases.

Error Amplifier

The error amplifier compares the FB voltage against the internal 0.8V reference (REF) and outputs a current proportional to the difference between the two. This output current charges or discharges the internal compensation network to form the COMP voltage, which is used to control the power MOSFET current. The optimized internal compensation network minimizes the external component counts and simplifies the control-loop design.

Enable

EN is a digital control pin that turns the regulator on and off: Drive EN HIGH to turn on the regulator, drive it LOW to turn it off. An internal 1M resistor from EN to GND allows EN to float to shut down the chip.

The EN pin is clamped internally using a 6.5V series-Zener-diode as shown in Figure 2. Connecting the EN input pin through a pullup resistor to the voltage on the V EN input current to less than 100A.

and

IN

range. When VIN

IN

falls below 5.0V, the

IN

pin limits the

IN

For example, with 12V connected to Vin, R

≥ (12V-6.5V)÷100A =55k

PULLUP

Connecting the EN pin is directly to a voltage source without any pullup resistor requires limiting the amplitude of the voltage source to ≤ 6V to prevent damage to the Zener diode.

Figure 2: 6.5V Zener Diode Connection

Under-Voltage Lockout (UVLO)

Under-voltage lockout (UVLO) protects the chip from operating at an insufficient supply voltage. The MP1469 UVLO comparator monitors the output voltage of the internal regulator, VCC. The UVLO rising threshold is about 4.2V while its falling threshold is consistently 3.86V.

Internal Soft-Start

Soft-start prevents the converter output voltage from overshooting during startup. When the chip starts, the internal circuit generates a softstart voltage (SS) that ramps up from 0V to

1.2V: When SS falls below the internal reference (REF), SS overrides REF so that the error amplifier uses SS as the reference; when SS exceeds REF, the error amplifier resumes using REF as its reference. The SS time is internally set to 1ms.

Over-Current-Protection and Hiccup

The MP1469 has a cycle-by-cycle over-current limit for when the inductor current peak value exceeds the set current-limit threshold. First, when the output voltage drops until FB falls below the Under-Voltage (UV) threshold (typically 200mV) to trigger a UV event, the MP1469 enters hiccup mode to periodicall restart the part. This protection mode is especially useful when the output is deadshorted to ground. This greatly reduces the average short-circuit current to alleviate thermal issues and to protect the regulator. The MP1469 exits hiccup mode once the overcurrent condition is removed.

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

Thermal Shutdown

Thermal shutdown prevents the chip from operating at exceedingly high temperatures. When the silicon die temperature exceeds 150°C, it shuts down the whole chip. When the temperature falls below its lower threshold (typically 130°C) the chip is enabled again.

Floating Driver and Bootstrap Charging

An external bootstrap capacitor powers the floating power MOSFET driver. This floating driver has its own UVLO protection, with a rising threshold of 2.2V and a hysteresis of 150mV. V

regulates the bootstrap capacitor

IN

voltage internally through D1, M1, R4, C4, L1 and C2 (Figure 3). If (V

) exceeds 5V,U2

IN-VSW

will regulate M1 to maintain a 5V BST voltage across C4.

V

IN

U2

5V

U1

D1

M1

R4

SW

C4

V

OUT

L1

C2

Figure 3: Internal Bootstrap Charging

Startup and Shutdown Circuit

If both V

and EN exceed their appropriate

IN

thresholds, the chip starts. The reference block starts first, generating stable reference voltage and currents, and then the internal regulator is enabled. The regulator provides a stable supply for the remaining circuits.

AAM Operation

The MP1469 has AAM (Advanced Asynchronous Modulation) power save mode for light load. The AAM voltage is set at 0.5V internally. Under the heavy load condition, the V

is higher than V

COMP

. When clock goes

AAM

high, the high-side power MOSFET turns on and remains on until V

reaches the value

ILsense

set by the COMP voltage. The internal clock resets every time when V V

.

AAM

is higher than

COMP

Under the light load condition, the value of

is low. When V

V

COMP

V

is less than V

FB

exceeds V

REF

, during this time, the internal

AAM

is less than V

COMP

, V

ramps up until it

COMP

AAM

and

clock is blocked, thus the MP1469 skips some pulses for PFM (Pulse Frequency Modulation) mode and achieves the light load power save.

Clock

V

REF

20k

OUT

R1

V

R2

FB

HS_driver

QS

R

COMP

V

1.2pF

47pF 500k

IL sense

-

+

V

AAM

+

V

-

+

Figure 4—Simplified AAM Control Logic

When the load current is light, the inductor peak current is set internally which is about 340mA for V

=12V, V

IN

=3.3V, and L=6.5H.The

OUT

curve of inductor peak current vs. inductor is shown in Figure 5.

Inductor Peak Current vs. Inductor

1.2

Three events can shut down the chip: EN low, V

low, and thermal shutdown. In the shutdown

IN

procedure starts by initially blocking the signaling path to avoid any fault triggering. The COMP voltage and the internal supply rail are then pulled down. The floating driver is not

1

0.8

0.6

0.4

subject to this shutdown command.

0.2

0

01234567

Figure5—Inductor Peak Current vs. Inductor

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

APPLICATION INFORMATION

Setting the Output Voltage

The external resistor divider sets the output voltage. The feedback resistor R1 also sets the feedback-loop bandwidth through the internal compensation capacitor (see the Typical Application circuit). Choose R1 and R2 by:

R1

OUT

R2

−

R1

1

is low.

OUT

VOUT

R2

=

V

0.8V

Use a T-type network for when V

FB

RT

Figure 6: T-Type Network

Table 1 lists the recommended T-type resistors value for common output voltages.

Table 1: Resistor Selection for Common Output

Voltages

V

(V) R1 (kΩ) R2 (kΩ) Rt (kΩ)

OUT

1.05 10(1%) 32.4(1%) 150(1%)

1.2 20.5(1%) 41.2(1%) 130(1%)

1.8 40.2(1%) 32.4(1%) 100(1%)

2.5 40.2(1%) 19.1(1%) 59(1%)

3.3 40.2(1%) 13(1%) 59(1%)

5 40.2(1%) 7.68(1%) 59(1%)

Δ

I

L

+=

II

LOAD)MAX(L

2

Under light-load conditions (below 100mA), use a larger inductance for improved efficiency.

Selecting the Input Capacitor

The input current to the step-down converter is discontinuous, and therefore requires a capacitor to both supply the AC current to the step-down converter and maintain the DC input voltage. Use low ESR capacitors for the best performance, such as ceramic capacitors with X5R or X7R dielectrics of their low ESR and small temperature coefficients. A 22µF capacitor is sufficient for most applications.

The input capacitor (C1) requires an adequate ripple current rating because it absorbs the input switching. Estimate the RMS current in the input capacitor with:

⎛

V

OUT

⎜

×

−×=

II

LOAD1C

1

⎜

V

IN

⎝

The worst-case condition occurs at VIN = 2V

V

OUT

V

⎞ ⎟

⎟

IN

⎠

,

OUT

where:

I

LOAD

=

I

1C

2

For simplification, choose an input capacitor with an RMS current rating greater than half the maximum load current.

Selecting the Inductor

The input capacitor can be electrolytic, tantalum, or ceramic. Place a small, high-quality, ceramic

Use a 1µH-to-10µH inductor with a DC current rating of at least 25% percent higher than the maximum load current for most applications. For highest efficiency, select an inductor with a DC resistance less than 15m. For most designs, derive the inductance value from the following equation.

V(VV)

×−

Where I

OUT IN OUT

L

=

1

VIf

×Δ ×

IN L OSC

is the inductor ripple current. Choose

L

an inductor current approximately 30% of the maximum load current. The maximum inductor peak current is:

capacitor (0.1F) as close to the IC as possible when using electrolytic or tantalum capacitors. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive input voltage ripple. Estimate the input voltage ripple caused by the capacitance with:

IV V

LOAD OUT OUT

V1

Δ= × ×−

IN

fC1V V

×

SIN

⎛⎞ ⎜⎟

IN

⎝⎠

Selecting the Output Capacitor

The output capacitor (C2) maintains the DC output voltage. Use ceramic, tantalum, or lowESR electrolytic capacitors. Use low ESR

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

capacitors to limit the output voltage ripple. Estimate the output voltage ripple with:

V1R

Δ= ×− × +

Where L

VV

OUT ESR

fL V 8fC2

S1 IN S

is the inductor value and R

1

⎛⎞

OUT OUT

⎜⎟

×××

⎝⎠

⎛⎞ ⎜⎟

1

⎝⎠

is the

ESR

equivalent series resistance (ESR) of the output capacitor.

For ceramic capacitors, the capacitance dominates the impedance at the switching frequency and causes most of the output voltage ripple. For simplification, estimate the output voltage ripple with:

VV

V1

=×−

OUT

OUT OUT

2

×××

8f L C2

S1

⎛⎞ ⎜⎟ ⎝⎠

V

IN

For tantalum or electrolytic capacitors, the ESR dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated with:

V1R

VV

=×−×

OUT ESR

fL V

S1

⎛⎞

OUT OUT

⎜⎟

×

IN

⎝⎠

The characteristics of the output capacitor also affect the stability of the regulation system. The MP1469 can be optimized for a wide range of capacitance and ESR values.

External Bootstrap Diode

An external bootstrap (BST) diode can enhance the efficiency of the regulator givien the following applicable conditions:

For most applications, use an IN4148 for the external BST diode is IN4148, and a 1µF capacitor for the BST cap.

PC Board Layout

PCB layout is very important to achieve stable operation. For best results, use the following guidelines and Figure 8 as reference.

1) Keep the connection between the input ground and GND pin as short and wide as possible.

2) Keep the connection between the input capacitor and IN pin as short and wide as possible.

3) Use short and direct feedback connections. Place the feedback resistors and compensation components as close to the chip as possible.

4) Route SW away from sensitive analog areas such as FB.

C3

R3

R1

R7

R2

R5

VIN

C1A

C5

6

12

C1

R6

45

R4

C4

3

GND

SW

C2

C2A

L1

OUT

V

z V

z Duty cycle is high: D=

is 5V or 3.3V; and

OUT

V

OUT

V

>65%

IN

Connect the external BST diode from the output of voltage regulator to the BST pin, as shown in Figure 7.

External BST Diode IN4148

R4

BST

MP1469

SW

L

C

OUT

5V or 3.3V

Figure 7: Optional External Bootstrap Diode

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

Design Example

Below is a design example following the application guidelines for the specifications:

Table 2—Design Example

12V

V

IN

V

3.3V

OUT

Io 1.5A

The detailed application schematic is shown in Figure 9. The typical performance and circuit waveforms have been shown in the Typical Performance Characteristics section. For more device applications, please refer to the related Evaluation Board Datasheets.

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

TYPICAL APPLICATION CIRCUITS

1

VIN

GND

EN

GND

R6

NS

R5

100k

GND

NS

C1

25V

C5

C1A

25V

GND

IN

MP1469

5

EN

GND

2

BST

SW

FB

R4

0

4

C4

40.2k

R2

7.68k

C3

NS

R1

L1

GND

5V/1.5A

C2

NS

GND

C2A

VOUT

GND

3

6

R3

NS

R7

59k

SW

VIN

GND

EN

VIN

GND

EN

GND

R6

NS

GND

R6

NS

GND

R5

100k

R5

100k

GND

C5

NS

C5

NS

C1

25V

C1

25V

GND

C1A

25V

C1A

25V

1

IN

MP1469

5

EN

1

IN

MP1469

5

EN

GND

Figure 8: 12VIN, 5V/1.5A

R4

BST

SW

4

3

0

R3

NS

6

GND

2

GND

FB

Figure 9: 12VIN, 3.3V/1.5A

R4

0

R3

NS

GND

2

BST

SW

FB

4

3

6

R7

59k

R7

59k

C4

GND

SW

GND

SW

40.2k

R2

13k

40.2k

R2

19.1k

C3

NS

R1

C3

NS

R1

L1

GND

3.3V/1.5A

C2

NS

GND

2.5V/1.5A

C2

NS

GND

C2A

GND

C2A

VOUT

GND

VOUT

GND

Figure 10: 12VIN, 2.5V/1.5A

VIN

GND

EN

GND

R6

NS

R5

100k

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

R4

0

4

C4

40.2k

R2

32.4k

C3

NS

R1

L1

GND

1.8V/1.5A

C2

NS

GND

SW

3

6

R3

NS

R7

100k

GND

NS

C1

25V

C5

GND

C1A

25V

1

IN

MP1469

5

EN

GND

2

BST

SW

FB

VOUT

C2A

GND

VIN

GND

EN

GND

R6

NS

GND

R5

100k

GND

NS

C1

25V

C5

GND

C1A

25V

1

IN

MP1469

5

EN

GND

Figure 11: 12VIN, 1.8V/1.5A

R4

0

4

BST

3

GND

2

GND

SW

FB

6

R3

NS

R7

130k

Figure 12: 12VIN, 1.2V/1.5A

C4

GND

SW

GND

20.5k

R2

41.2k

C3

NS

R1

L1

GND

1.2V/1.5A

C2

NS

GND

C2A

GND

VOUT

GND

MP1469 – SYNCHRONOUS, STEP-DOWN CONVERTER WITH INTERNAL MOSFETS

PACKAGE INFORMATION

2.80

3.00

46

See Not e 7 EXAMPLE TOP MARK

PIN 1

AAAA

13

TSOT23-6

1.50

1.70

2.60

3.00

1.20 TYP

0.60 TYP

0.95

BSC

2.60 TYP

0.84

0.90

0.30

0.50

GAUGE PLANE

0.25 BSC

TOP VIEW

0.95 BSC

1.00 MAX

SEATING PL ANE

0.00

0.10

RECOMMENDED LAND PATTERN

SEE DET AIL "A"

FRONT VIEW SIDE VIEW

NOTE:

1) ALL DIMENSIONS ARE IN MILLIMETERS.

2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH, PROT RUSION OR GATE B URR.

3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH OR PROT RUSION.

4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.10 MILLIMETERS MAX.

5) DRAWING CONFORMS TO JEDEC MO-193, VARIATION AB.

6) DRAWING IS NOT TO SCALE.

7) PIN 1 IS LOWER LEFT PIN WHEN READING TOP MARK FROM LEFT TO RIGHT, (SEE EXAMPLE TOP MARK)

o

0o-8

DETAIL “ A”

0.30

0.50

0.09

0.20

NOTICE: The information in this document is subject to change without notice. Users should warrant and guarantee that third

party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications.