Philips tda9880t DATASHEETS

INTEGRATED CIRCUITS

DATA SH EET

TDA9880T

Alignment-freemultistandardvision and FM sound IF-PLL demodulator

Product speciﬁcation Supersedes data of 1999 Jul 21 File under Integrated Circuits, IC02

2000 Nov 22

Philips Semiconductors Product speciﬁcation

Alignment-free multistandardvisionand FM sound IF-PLL demodulator

FEATURES

• 5 V supply voltage

• Gain controlled wide-band Vision Intermediate

Frequency (VIF) amplifier (AC-coupled)

• True synchronous demodulation with active carrier regeneration (very linear demodulation, good intermodulation figures, reduced harmonics and excellent pulse response)

• Fully integrated VIF Voltage Controlled Oscillator (VCO), alignment-free

• Digital acquisition help, VIF frequencies of 38.0, 38.9,

45.75 and 58.75 MHz

• 4 MHz reference frequency input [signal from Phase-Locked Loop (PLL) tuning system] or operating as crystal oscillator

• VIF Automatic Gain Control (AGC) detector for gain control, operating as peak sync detector, fast reaction time

TDA9880T

• Precise fullydigital Automatic Frequency Control (AFC) detector with 4-bit digital-to-analog converter

• Fully integrated sound carrier trap for 4.5, 5.5,

6.0 and 6.5 MHz, controlled by reference signal

• Alignment-freeselectiveFM-PLL demodulator with high linearity and low noise

• Digital frequency control, sound carrier frequencies

4.5, 5.5, 6.0 and 6.5 MHz

• Stabilizer circuit for ripple rejection and to achieve constant output signals

• Electrostatic discharge (ESD) protection for all pins.

GENERAL DESCRIPTION

The TDA9880T is an integrated circuit for multistandard vision IF signal processing and FM demodulation in TV and VTR sets.

ORDERING INFORMATION

TYPE NUMBER

NAME DESCRIPTION VERSION

TDA9880T SO20 plastic small outline package; 20 leads; body width 7.5 mm SOT163-1

PACKAGE

2000 Nov 22 2

Philips Semiconductors Product speciﬁcation

Alignment-free multistandard vision and

TDA9880T

FM sound IF-PLL demodulator

QUICK REFERENCE DATA

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

i(sens)(VIF)(rms)

VIF(cr)

VIF

∆f

VIF

o(v)(p-p)

dif

v(−3dB)(trap)

SC1

S/N

PSRR

v(−1dB)

ch(max)(20)

dch(max)(20)

sink(14)

AFC

stps

o(source)(19)

o(sink)(19)

o(intc)(rms)

supply voltage note 1 4.5 5.0 5.5 V supply current 85 100 115 mA VIF input voltage sensitivity

−1 dB video at output − 50 100 µV

(RMS value) VIF gain control range see Fig.3 65 69 − dB VIF frequencies see Table 2 − 38.0 − MHz

− 38.9 − MHz

− 45.75 − MHz

− 58.75 − MHz

VIF frequency window of digital

referenced to f

VIF

−±2.38 − MHz

acquisition help video output signal voltage

(peak-to-peak value)

sound carrier off; see Fig.9 1.7 2.0 2.3 V trap bypass mode;

0.95 1.10 1.25 V

see Fig.9 differential gain differential phase

−3 dB video bandwidth including sound carrier trap

“NTC-7 Composite”

CL< 20 pF; RL>1kΩ;

AC load; note 2

= 4.5 MHz

trap

− 25%

− 2 4 deg

3.95 4.05 − MHz

(M/N standard) f

= 5.5 MHz

trap

4.90 5.00 − MHz

(B/G standard)

trap attenuation at ﬁrst sound carrier M/N standard 30 36 − dB

B/G standard 30 36 − dB weighted signal-to-noise ratio of

see Fig.5; note 3 56 60 − dB video signal

power supply ripple rejection at pin 13

−1 dB video bandwidth CL< 20 pF; RL>1kΩ;

= 70 Hz; video signal;

ripple

grey level; see Fig.8

25 28 − dB

56−MHz

AC load; trap bypass mode AGC maximum charge current at

6810µA

pin 20 AGC maximum discharge current at

7.5 10 12.5 µA

pin 20 sink current of tuner AGC at pin 14 maximum tuner gain

450 600 750 µA reduction; V14=1V; see Fig.3

AFC steepness ∆I19/∆f 0.85 1.05 1.25 µA/kHz AFC output source current at pin 19 160 200 240 µA AFC output sink current at pin 19 160 200 240 µA intercarrier output voltage

(RMS value)

i(SC)

-------------V

i(PC)

note 4

24 dB;–=

− 49 − mV

2000 Nov 22 3

Philips Semiconductors Product speciﬁcation

Alignment-free multistandard vision and

TDA9880T

FM sound IF-PLL demodulator

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

intc(−3dB)(ul)

o(AF)(8)(rms)

THD

AF(−3dB)

S/N

W(AF)

AM(sup)

PSRR

∆f

ref(15)

ref(15)(rms)

upper limit −3 dB intercarrier

7.5 9.0 − MHz

bandwidth audio output signal voltage at pin 8

(RMS value)

25 kHz FM deviation; 75 µs de-emphasis

400 500 600 mV

total harmonic distortion at pin 8 − 0.15 0.5 %

−3 dB audio frequency bandwidth without de-emphasis;

100 120 − kHz dependent on loop ﬁlter at pin 4

weighted signal-to-noise ratio of audio signal

black picture 50 56 − dB white picture 45 51 − dB 6 kHz sine wave

40 46 − dB (black-to-white modulation)

sound carrier

35 40 − dB subharmonics; f = 2.25 MHz ±3 kHz

AM suppression of FM demodulator 75 µs de-emphasis;

40 46 − dB AM: f = 1 kHz; m = 0.3 referenced to 25 kHz FM deviation

power supply ripple rejection at pin 8 f frequency window of digital

= 70 Hz; see Fig.8 14 20 − dB

ripple

−±225 − kHz

acquisition help for FM demodulator frequency of reference signal at

− 4.0 − MHz

pin 15 amplitude of referencesignal source

operation as input terminal 80 − 400 mV

at pin 15 (RMS value)

Notes

1. Values of video and sound parameters can be decreased at VP= 4.5 V.

2. The sound carrier frequencies (depending on TV standard) are attenuated by the integrated sound carrier traps (see Figs 12 to 17); H (s) is the absolute value of transfer function.

3. S/N is the ratio of black-to-white amplitude to the black level noise voltage (RMS value, pin 13). B = 4.2 MHz (M/N standard) or B = 5.0 MHz (B/G, I and D/K standard) weighted in accordance with

“CCIR 567”

4. The intercarrier output signal at pin 11 can be calculated by the following formula taking into account the internal video signal with 1.1 V (p-p) as a reference:

iSC()

dB()6 dB 3 dB±+

--------------V

iPC()

o(intc)(rms)

1.1 V (p-p)

× 10

---------- 22

--------------------------------------------------------------- -

×=

where:

= correction term for RMS value, = sound-to-picture carrier ratio at VIF input (pins 1 and 2) in dB,

---------- 22

iSC()

--------------V

iPC()

dB()

6 dB = correction term of internal circuitry and ±3 dB = tolerance of video output and intercarrier output amplitude V

o(intc)(rms)

2000 Nov 22 4

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2000 Nov 22 5

book, full pagewidth

BLOCK DIAGRAM

Philips Semiconductors Product speciﬁcation

Alignment-free multistandard vision and

FM sound IF-PLL demodulator

VIF1 VIF2

external reference

or 4 MHz crystal

TOP

VAGC TAGC 14 3 20 15 19 12

1 2

TOP

AGC

VAGC

RC VCO

VIF-PLL

DIGIT AL VCO CONTROL AFC DETECTOR

REF

SOUND TRAPS

trap disable

switch

AFC

4.5 to 6.5 MHz

TDA9880T

SUPPL Y

VPLLVPGND

sound

intercarrier

output

SIO

LOGIC

911181617

S1S0

NARROW-BAND FM-PLL DETECTOR

FAGC

FMPLL DEEM AFD

FAGC

DEEM

CVBS

AUD

645710

AFD

video output 2 V (p-p)

[1.1 V (p-p) without trap]

audio output

VIF-PLL

filter

FM-PLL

filter

Fig.1 Block diagram.

de-emphasis decoupling

MHB506

TDA9880T

Philips Semiconductors Product speciﬁcation

Alignment-free multistandard vision and FM sound IF-PLL demodulator

PINNING

SYMBOL PIN DESCRIPTION

VIF1 1 VIF differential input 1 VIF2 2 VIF differential input 2 TOP 3 tuner AGC TakeOver Point (TOP) FMPLL 4 FM-PLL ﬁlter DEEM 5 de-emphasis capacitor AFD 6 AF decoupling capacitor FAGC 7 FM-PLL AGC capacitor AUD 8 audio output S0 9 switch input S0 S1 10 switch input S1 SIO 11 sound intercarrier output TR 12 trap control CVBS 13 video output TAGC 14 tuner AGC output REF 15 4 MHz crystal or reference input GND 16 ground supply V

VPLL 18 VIF-PLL ﬁlter AFC 19 AFC output VAGC 20 VIF-AGC capacitor

17 supply voltage (+5 V)

handbook, halfpage

VIF1

VIF2

TOP

FMPLL

DEEM

5 6 7 8 9

TDA9880T

MHB106

AFD

FAGC

AUD

S0 S1

Fig.2 Pin configuration.

TDA9880T

VAGC

20 19

AFC

VPLL V

GND

REF TAGC

CVBS

SIO

2000 Nov 22 6

Philips Semiconductors Product speciﬁcation

Alignment-free multistandard vision and FM sound IF-PLL demodulator

FUNCTIONAL DESCRIPTION

Figure 1 shows the simplified block diagram of the integrated circuit. The integrated circuit comprises the following functional blocks:

1. VIF amplifier

2. Tuner-AGC and VIF-AGC

3. VIF-AGC detector

4. Frequency Phase-Locked Loop (FPLL) detector

5. VCO and Travelling Wave Divider (TWD)

6. Digital acquisition help and AFC

7. Video demodulator and amplifier

8. Sound carrier trap

9. Intercarrier mixer

10. FM demodulator and acquisition help

11. Audio amplifier

12. Internal voltage stabilizer.

VIF ampliﬁer

The VIF amplifier consists of three AC-coupled differential amplifier stages. Each differential stage comprises a feedback network controlled by emitter degeneration.

Tuner-AGC and VIF-AGC

The AGC capacitor voltage is converted to an internal VIF gaincontrol signal, and is fedto the tuner AGC togenerate the tuner AGC output current at pin TAGC (open-collector output). The tuner AGC takeover point can be adjusted with R filter in order to achieve the optimum IF input level.

VIF-AGC detector

The AGC detector generates the required VIF gain control voltage for constant video output by charging or discharging the AGC capacitor. Gain control is performed by sync level detection. The newly developed AGC circuit provides fast reaction time to cope with ‘aeroplane fluttering’. The time constants for decreasing or increasing gain are nearly equal.

. This allows the tuner to be matchedto the SAW

TOP

TDA9880T

After frequency lock-in the phase detector produces a DC current proportional to the phase difference between the VCO and the input signal. The DC current of either the frequency detector or the phase detector is converted into aDCvoltagevia the VIF-PLL filter, which controls the VCO frequency.

VCO and Travelling Wave Divider (TWD)

The Resistor Capacitor (RC) VCO operates as an integrated relaxation oscillator atdouble the picture carrier frequency.The control voltage required totunethe VCO to actually double the picture carrier frequency is generated by the FPLL detector and fed via the loop filter to the VCO control input terminal.

The oscillator signal is divided-by-two with a TWD which generatestwo differential output signals witha 90 degrees phase difference independent of the frequency.

Digital acquisition help and AFC

The integrated relaxation oscillator has a very wide frequency range from approximately 30 to 70 MHz (after the TWD). To prevent false locking of the FPLL and with respect to the catching range of the frequency detector of maximum ±2.5 MHz, the Digital Acquisition Help (DAH) provides current into the loop filter until the VCO is in a frequency window of ±2.3 MHz around the wanted VIF frequency. In this case the analog operating FPLL willlock the VCO to the VIF carrier and the acquisition help does not provide any current to the loop filter.

The principle of the digital acquisition help is as follows: the VCO is connected to a downcounter, which is preset depending on the required VIF frequency. The counting time, as well as the counter control, is derived from a 4 MHz reference signal. This signal can be supplied from the internal 4 MHz crystal oscillator or from the 4 MHz reference oscillator of an external tuning system. The counting result after a counting cycle corresponds to the actual VCO frequency.

The digital AFC is also derived from the counting result after a counting cycle by digital-to-analog converting the last four bits of the counter.

Frequency Phase-Locked Loop (FPLL) detector

The VIF amplifier output signal is fed into a Frequency Detector(FD) and into a PhaseDetector (PD) via a limiting amplifier. During acquisition the frequency detector produces a DC current proportional to the frequency difference between the input and the VCO signal.

2000 Nov 22 7

Video demodulator and ampliﬁer

The video demodulator is realized by a multiplier which is designedforlowdistortionandlargebandwidth.Thevision IF input signal is multiplied with the ‘in phase’ signal of the travelling wave divider output.

Philips Semiconductors Product speciﬁcation

Alignment-free multistandard vision and FM sound IF-PLL demodulator

The demodulator output signal is fed via an integrated low-pass filter for attenuation of the carrier harmonics to the video amplifier. The video amplifier is realized by an operational amplifier with internal feedback and high bandwidth. A low-pass filter is integrated to achieve an attenuation of the carrier harmonics. The video signal of

1.1 V (p-p) for nominal vision IF modulation is fed internally to the integrated sound carrier trap as well as to the VIF-AGC detector. The second stage of the video amplifier converts and amplifies the differential output signal from the sound carrier trap to the single-ended CVBS output signal at pin 13 with a 2 V (p-p) amplitude.

Noise clipping is provided. Furthermore the trap can be bypassed by the implemented input switch of the second amplifier stage, forced by connecting pin 12 to ground.

Sound carrier trap

The sound carrier trap consists of a reference filter, a phase detector and the sound trap itself.

A sound carrier reference signal is fed into the reference low-pass filter and is shifted by a nominal 90 degrees. The phasedetectorcomparestheoriginalreferencesignal with the signal shiftedby the reference filter and produces, at the external capacitor CTR, a DC voltage by charging or discharging the capacitor with a current proportional to the phase difference between both signals, respectively to the frequency error of the integrated filters. The DC voltage is converted to currents which control the frequency position of the reference filter and the sound trap.

The sound trap itselfis constructed of three separate traps to realize sufficient suppression of the first and second sound carrier. The right frequency position of the different standards is set by the sound carrier reference signal.

Intercarrier mixer

The intercarrier mixer is realized by a multiplier, operating inquadraturemodeforsuppressionoflowfrequencyvideo signals. The VIF amplifier output signal is fed to the intercarrier mixer and converted to an intercarrier frequency by the regenerated 90 degree picture carrier from the VCO. The mixer output signal is fed via a band-pass filter and amplifier for attenuation of the high frequency video signal components and carrier harmonics to the output pin 11. The intercarrier signal is fed also to the integrated FM demodulator.

TDA9880T

FM demodulator and acquisition help

The FM demodulator is realized as a narrow-band PLL with external loop filter, which provides the necessary selectivity. To achieve good selectivity, a linear phase detector and constant input level are required. The intercarrier signal from the intercarrier mixer is fed via a gain controlled amplifier to the phase detector and it’s output signal controls (via the loop filter) the integrated relaxation oscillator. The possible frequency range is from 4 to 7 MHz. As a result of locking the oscillator frequency tracks with the FM modulation of the input signal; therefore,theoscillator control voltage is superimposed by the AF voltage. In this way the FM-PLL operates as an FM demodulator. The AF voltage is present at the loop filter and is fed via a buffer with 0 dB gain to the audio amplifier.

The digital acquisition help operates in the same way as described in Section “Digital acquisition help and AFC”.

Audio ampliﬁer

The audio amplifier consists of two parts:

1. The AF preamplifier is an operational amplifier with internal feedback, high gain and high common mode rejection. The AF voltage from the PLL demodulator, by principle a small output signal, is amplified by 30 dB. A DC operating point control circuit (pin 6) decouples the AF amplifier from the DC voltage of the PLL. The low-pass characteristic of the amplifier reduces the harmonics of the intercarrier signal at the sound output terminal. If required, a de-emphasis network can be realized by the amplifier output resistance and an external capacitor.

2. The AF output amplifier (10 dB) provides the required output level by a rail-to-rail output stage. This amplifier makes use of an input selector for switching to mute state, automatically controlled by the mute switching voltage from the digital acquisition help in order to avoid lock-in noise. During normal operation the automatic audio mute function is not active. Application of a 2.2 kΩ resistor between the intercarrier output (pin 11) and ground will activate the automatic audio mute function.

Internal voltage stabilizer

The band gap circuit internally generates a voltage of approximately 2.4 V, independent of the supply voltage and the temperature. Avoltage regulator circuit, controlled by this voltage, produces a constant voltage of 3.55 V which is used as an internal reference voltage.

2000 Nov 22 8

Philips Semiconductors Product speciﬁcation

Alignment-free multistandard vision and

TDA9880T

FM sound IF-PLL demodulator

LIMITING VALUES

In accordance with the Absolute Maximum Rating System (IEC 60134).

SYMBOL PARAMETER CONDITIONS MIN. MAX. UNIT

stg

amb

Notes

1. Charge device model class A; machine model: discharging a 200 pF capacitor via a 0.75 µH inductance.

2. Charge device model class B; human body model: discharging a 100 pF capacitor via a 1.5 kΩ series resistor.

supply voltage IP= 115 mA; T

=70°C; at

amb

− 5.5 V

maximum chip temperature of 125 °C

voltage at

pins 1 to 4, 6 to 10, 12 and 17 to 20 0 V

pin 14 0 13.2 V

short-circuit time to ground or V

− 10 s storage temperature −25 +150 °C ambient temperature −20 +70 °C electrostatic handling voltage for all

pins

note 1 −250 +250 V note 2 −3000 +3000 V

THERMAL CHARACTERISTICS

SYMBOL PARAMETER CONDITIONS VALUE UNIT

th(j-a)

thermal resistance from junction to ambient in free air 85 K/W

2000 Nov 22 9

Philips Semiconductors Product speciﬁcation

Alignment-free multistandard vision and

TDA9880T

FM sound IF-PLL demodulator

CHARACTERISTICS

VP=5V; T PC/SC = 10 dB) is used for speciﬁcation; V 1 : 1; DSB video modulation; 10% residual carrier; video signal in accordance with taken in test circuit of Fig.18; unless otherwise specified.

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

Supply (pin 17)

tot

VIF ampliﬁer (pins 1 and 2)

i(sens)(VIF)(rms)

i(max)(rms)

∆V

int

VIF(cr)

VIF(−3dB)(ll)

VIF(−3dB)(ul)

i(dif)

FPLL and true synchronous video demodulator; note 4 f

VCO(max)

VIF

∆f

VIF

acq

i(sens)(VIF)(rms)

SIGNAL AT PIN 18 I

o(source)(PD)(max)

=25°C; see Table 2 for input frequencies; M standard (fPC= 45.75 MHz; fSC= 41.25 MHz;

amb

i(VIF)(rms)

= 10 mV (sync level); IF input from 50 Ω via broadband transformer

“NTC-7 Composite”

supply voltage note 1 4.5 5 5.5 V supply current 85 100 115 mA total power dissipation − 500 633 mW

VIF input voltage sensitivity

−1 dB video at output − 50 100 µV

(RMS value) maximum input signal voltage

(RMS value) internal IF amplitudedifference

between picture and sound

1 dB video at output; note 2

within AGC range; ∆f = 4.5 MHz

110 −−mV

− 0.7 1 dB

carrier VIF gain control range see Fig.3 65 69 − dB lower limit −3 dB VIF

− 15 25 MHz

bandwidth upper limit −3 dB VIF

70 100 − MHz

bandwidth differential input resistance note 3 1.7 2.2 2.7 kΩ differential input capacitance note 3 1.2 1.7 2.5 pF DC input voltage − 3.35 − V

maximum oscillator frequency

f=2f

120 140 − MHz

for carrier regeneration vision carrier operating

frequencies

see Table 2 − 38.0 − MHz

− 38.9 − MHz

− 45.75 − MHz

− 58.75 − MHz

VIFfrequency window of digital

referenced to f

VIF

−±2.38 − MHz

acquisition help acquisition time BL = 70 kHz; note 5 −−30 ms VIF input voltage sensitivity at

pins 1 and 2 (RMS value)

for PLL to be locked maximum IF gain − 30 70 µV for C/N = 10 dB notes 6 and 7 − 100 140 µV

maximum source current of

− 17 −µA

phase detector output

; measurements

2000 Nov 22 10

Philips Semiconductors Product speciﬁcation

Alignment-free multistandard vision and

TDA9880T

FM sound IF-PLL demodulator

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

o(sink)(PD)(max)

o(source)(DAH)

o(sink)(DAH)

W(min)(DAH)

O(VIF)

D(VIF)

Video output signal and sound carrier trap (pin 13; sound carrier off)

o(v)(p-p)

sync

v(clu)

v(cll)

bias(int)

o(source)(max)

o(sink)(max)

∆V

o(bl)

dif

v(−3dB)(trap)

maximum sink current of

− 17 −µA

phase detector output output source current of digital

− 23 −µA

acquisition help output sink current of digital

− 23 −µA

acquisition help minimum pulse width of digital

− 64 −µs

acquisition help current VCO steepness ∆f phase detector steepness

∆I18/∆ϕ

VIF

video output signal voltage

VIF

/∆V

− 20 − MHz/V

− 23 −µA/rad

see Fig.9 1.7 2.0 2.3 V

(peak-to-peak value) sync pulse voltage level see Fig.9 1.15 1.35 1.55 V zero carrier voltage level see Fig.9 3.27 3.57 3.87 V upper video clipping voltage

VP− 1.1 VP− 1 − V

level lower video clipping voltage

− 0.7 1.0 V

level output resistance note 3 −−30 Ω internal DC bias current for

2.0 2.5 − mA

emitter-follower maximum AC and DC output

2.4 −−mA

source current maximum AC and DC output

1.4 −−mA

sink current deviation of CVBS output

signal voltage

50 dB gain control −−0.5 dB

30 dB gain control −−0.1 dB black level tilt −−1% differential gain differential phase

−3 dB video bandwidth including sound carrier trap

“NTC-7 Composite”

CL< 20 pF; RL>1kΩ;

AC load; note 8

= 4.5 MHz

trap

− 25%

− 2 4 deg

3.95 4.05 − MHz

(M/N standard) f

= 5.5 MHz

trap

4.90 5.00 − MHz

(B/G standard)

= 6.0 MHz

trap

5.2 5.50 − MHz

(I standard) f

= 6.5 MHz

trap

5.5 5.95 − MHz

(D/K standard)

2000 Nov 22 11

Philips Semiconductors Product speciﬁcation

Alignment-free multistandard vision and

TDA9880T

FM sound IF-PLL demodulator

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

SC1

SC1(60 kHz)

SC2

SC2(60 kHz)

d(g)(CC)

S/N

αd

blue

αd

yellow

∆V

r(vc)(rms)

H(sup)

H(spur)

PSRR

trap attenuation at ﬁrst sound carrier

M/N standard 30 36 − dB

B/G standard 30 36 − dB

I standard 26 32 − dB

D/K standard 26 32 − dB trap attenuation at ﬁrst sound

carrier f

SC1

±60 kHz

M/N standard 21 27 − dB

B/G standard 24 30 − dB

I standard 20 26 − dB

D/K standard 20 26 − dB trap attenuation at second

sound carrier

M/N standard 21 27 − dB

B/G standard 21 27 − dB

I standard 12 18 − dB

D/K standard 18 24 − dB trap attenuation at second

sound carrier f

SC2

±60 kHz

M/N standard 15 21 − dB

B/G standard 15 21 − dB

I standard 10 15 − dB

D/K standard 13 18 − dB group delay at chrominance

carrier frequency

3.58 MHz at

M/N standard

4.43 MHz at B/G standard 110 180 250 ns

4.43 MHz at I standard − 90 160 ns

4.28 MHz at D/K standard − 60 130 ns

weighted signal-to-noise ratio weighted in accordance

with

“CCIR 567”

;

see Fig.5; note 9 unweighted signal-to-noise

note 9 47 51 − dB ratio

intermodulation attenuation at ‘blue’

f = 0.92 MHz; see Fig.6;

note 10

f = 2.76 MHz; see Fig.6;

note 10 intermodulation attenuation at

‘yellow’

f = 0.92 MHz; see Fig.6;

note 10

f = 2.76 MHz; see Fig.6;

note 10 residual vision carrier

(RMS value) harmonics suppression in

video signal spuriouselementssuppression

fundamental wave and

harmonics

CL< 20 pF; RL>1kΩ;

AC load; note 11a

note 11b 40 −−dB in video signal

powersupply ripple rejectionat pin 13

= 70 Hz; video

ripple

signal; grey level;

see Fig.8

110 180 250 ns

56 60 − dB

58 64 − dB

60 66 − dB

59 65 − dB

− 25mV

35 40 − dB

25 28 − dB

2000 Nov 22 12

+ 28 hidden pages