Philips tda9880t DATASHEETS
INTEGRATED CIRCUITS
DATA SH EET
TDA9880T
Alignment-freemultistandardvision
and FM sound IF-PLL demodulator
Product specification
Supersedes data of 1999 Jul 21
File under Integrated Circuits, IC02
2000 Nov 22
Philips Semiconductors Product specification
Alignment-free multistandardvisionand
FM sound IF-PLL demodulator
FEATURES
• 5 V supply voltage
• Gain controlled wide-band Vision Intermediate
Frequency (VIF) amplifier (AC-coupled)
• True synchronous demodulation with active carrier
regeneration (very linear demodulation, good
intermodulation figures, reduced harmonics and
excellent pulse response)
• Fully integrated VIF Voltage Controlled Oscillator
(VCO), alignment-free
• Digital acquisition help, VIF frequencies of 38.0, 38.9,
45.75 and 58.75 MHz
• 4 MHz reference frequency input [signal from
Phase-Locked Loop (PLL) tuning system] or operating
as crystal oscillator
• VIF Automatic Gain Control (AGC) detector for gain
control, operating as peak sync detector, fast reaction
time
TDA9880T
• Precise fullydigital Automatic Frequency Control (AFC)
detector with 4-bit digital-to-analog converter
• Fully integrated sound carrier trap for 4.5, 5.5,
6.0 and 6.5 MHz, controlled by reference signal
• Alignment-freeselectiveFM-PLL demodulator with high
linearity and low noise
• Digital frequency control, sound carrier frequencies
4.5, 5.5, 6.0 and 6.5 MHz
• Stabilizer circuit for ripple rejection and to achieve
constant output signals
• Electrostatic discharge (ESD) protection for all pins.
GENERAL DESCRIPTION
The TDA9880T is an integrated circuit for multistandard
vision IF signal processing and FM demodulation in TV
and VTR sets.
ORDERING INFORMATION
TYPE NUMBER
NAME DESCRIPTION VERSION
TDA9880T SO20 plastic small outline package; 20 leads; body width 7.5 mm SOT163-1
PACKAGE
2000 Nov 22 2
Philips Semiconductors Product specification
Alignment-free multistandard vision and
TDA9880T
FM sound IF-PLL demodulator
QUICK REFERENCE DATA
SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT
V
P
I
P
V
i(sens)(VIF)(rms)
G
VIF(cr)
f
VIF
∆f
VIF
V
o(v)(p-p)
G
dif
ϕ
dif
B
v(−3dB)(trap)
α
SC1
S/N
W
PSRR
13
B
v(−1dB)
I
ch(max)(20)
I
dch(max)(20)
I
sink(14)
AFC
stps
I
o(source)(19)
I
o(sink)(19)
V
o(intc)(rms)
supply voltage note 1 4.5 5.0 5.5 V
supply current 85 100 115 mA
VIF input voltage sensitivity
−1 dB video at output − 50 100 µV
(RMS value)
VIF gain control range see Fig.3 65 69 − dB
VIF frequencies see Table 2 − 38.0 − MHz
− 38.9 − MHz
− 45.75 − MHz
− 58.75 − MHz
VIF frequency window of digital
referenced to f
VIF
−±2.38 − MHz
acquisition help
video output signal voltage
(peak-to-peak value)
sound carrier off; see Fig.9 1.7 2.0 2.3 V
trap bypass mode;
0.95 1.10 1.25 V
see Fig.9
differential gain
differential phase
−3 dB video bandwidth including
sound carrier trap
“NTC-7 Composite”
“NTC-7 Composite”
CL< 20 pF; RL>1kΩ;
AC load; note 2
f
= 4.5 MHz
trap
− 25%
− 2 4 deg
3.95 4.05 − MHz
(M/N standard)
f
= 5.5 MHz
trap
4.90 5.00 − MHz
(B/G standard)
trap attenuation at first sound carrier M/N standard 30 36 − dB
B/G standard 30 36 − dB
weighted signal-to-noise ratio of
see Fig.5; note 3 56 60 − dB
video signal
power supply ripple rejection at
pin 13
−1 dB video bandwidth CL< 20 pF; RL>1kΩ;
f
= 70 Hz; video signal;
ripple
grey level; see Fig.8
25 28 − dB
56−MHz
AC load; trap bypass mode
AGC maximum charge current at
6810µA
pin 20
AGC maximum discharge current at
7.5 10 12.5 µA
pin 20
sink current of tuner AGC at pin 14 maximum tuner gain
450 600 750 µA
reduction; V14=1V;
see Fig.3
AFC steepness ∆I19/∆f 0.85 1.05 1.25 µA/kHz
AFC output source current at pin 19 160 200 240 µA
AFC output sink current at pin 19 160 200 240 µA
intercarrier output voltage
(RMS value)
V
i(SC)
-------------V
i(PC)
note 4
24 dB;–=
− 49 − mV
2000 Nov 22 3
Philips Semiconductors Product specification
Alignment-free multistandard vision and
TDA9880T
FM sound IF-PLL demodulator
SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT
B
intc(−3dB)(ul)
V
o(AF)(8)(rms)
THD
8
B
AF(−3dB)
S/N
W(AF)
α
AM(sup)
PSRR
8
∆f
FM
f
ref(15)
V
ref(15)(rms)
upper limit −3 dB intercarrier
7.5 9.0 − MHz
bandwidth
audio output signal voltage at pin 8
(RMS value)
25 kHz FM deviation;
75 µs de-emphasis
400 500 600 mV
total harmonic distortion at pin 8 − 0.15 0.5 %
−3 dB audio frequency bandwidth without de-emphasis;
100 120 − kHz
dependent on loop filter at
pin 4
weighted signal-to-noise ratio of
audio signal
black picture 50 56 − dB
white picture 45 51 − dB
6 kHz sine wave
40 46 − dB
(black-to-white modulation)
sound carrier
35 40 − dB
subharmonics;
f = 2.25 MHz ±3 kHz
AM suppression of FM demodulator 75 µs de-emphasis;
40 46 − dB
AM: f = 1 kHz; m = 0.3
referenced to 25 kHz
FM deviation
power supply ripple rejection at pin 8 f
frequency window of digital
= 70 Hz; see Fig.8 14 20 − dB
ripple
−±225 − kHz
acquisition help for FM demodulator
frequency of reference signal at
− 4.0 − MHz
pin 15
amplitude of referencesignal source
operation as input terminal 80 − 400 mV
at pin 15 (RMS value)
Notes
1. Values of video and sound parameters can be decreased at VP= 4.5 V.
2. The sound carrier frequencies (depending on TV standard) are attenuated by the integrated sound carrier traps
(see Figs 12 to 17); H (s) is the absolute value of transfer function.
3. S/N is the ratio of black-to-white amplitude to the black level noise voltage (RMS value, pin 13). B = 4.2 MHz
(M/N standard) or B = 5.0 MHz (B/G, I and D/K standard) weighted in accordance with
“CCIR 567”
.
4. The intercarrier output signal at pin 11 can be calculated by the following formula taking into account the internal
video signal with 1.1 V (p-p) as a reference:
V
iSC()
dB()6 dB 3 dB±+
--------------V
iPC()
V
o(intc)(rms)
1.1 V (p-p)
1
× 10
---------- 22
--------------------------------------------------------------- -
×=
20
where:
1
= correction term for RMS value, = sound-to-picture carrier ratio at VIF input (pins 1 and 2) in dB,
---------- 22
V
iSC()
--------------V
iPC()
dB()
6 dB = correction term of internal circuitry and ±3 dB = tolerance of video output and intercarrier output amplitude
V
o(intc)(rms)
.
2000 Nov 22 4
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2000 Nov 22 5
book, full pagewidth
BLOCK DIAGRAM
Philips Semiconductors Product specification
Alignment-free multistandard vision and
FM sound IF-PLL demodulator
VIF1
VIF2
external reference
or 4 MHz crystal
R
TOP
C
VAGC
TAGC
14 3 20 15 19 12
1
2
TOP
AGC
VAGC
RC VCO
VIF-PLL
DIGIT AL VCO CONTROL AFC DETECTOR
REF
SOUND TRAPS
trap disable
switch
AFC
4.5 to 6.5 MHz
TDA9880T
SUPPL Y
VPLLVPGND
sound
intercarrier
output
SIO
LOGIC
911181617
S1S0
NARROW-BAND FM-PLL DETECTOR
FAGC
C
FMPLL DEEM AFD
FAGC
C
DEEM
C
TR
TR
CVBS
13
8
AUD
645710
C
AFD
video output 2 V (p-p)
[1.1 V (p-p) without trap]
audio output
VIF-PLL
filter
FM-PLL
filter
Fig.1 Block diagram.
de-emphasis decoupling
MHB506
TDA9880T
Philips Semiconductors Product specification
Alignment-free multistandard vision and
FM sound IF-PLL demodulator
PINNING
SYMBOL PIN DESCRIPTION
VIF1 1 VIF differential input 1
VIF2 2 VIF differential input 2
TOP 3 tuner AGC TakeOver Point (TOP)
FMPLL 4 FM-PLL filter
DEEM 5 de-emphasis capacitor
AFD 6 AF decoupling capacitor
FAGC 7 FM-PLL AGC capacitor
AUD 8 audio output
S0 9 switch input S0
S1 10 switch input S1
SIO 11 sound intercarrier output
TR 12 trap control
CVBS 13 video output
TAGC 14 tuner AGC output
REF 15 4 MHz crystal or reference input
GND 16 ground supply
V
P
VPLL 18 VIF-PLL filter
AFC 19 AFC output
VAGC 20 VIF-AGC capacitor
17 supply voltage (+5 V)
handbook, halfpage
VIF1
1
VIF2
2
TOP
3
FMPLL
4
DEEM
5
6
7
8
9
10
TDA9880T
MHB106
AFD
FAGC
AUD
S0
S1
Fig.2 Pin configuration.
TDA9880T
VAGC
20
19
AFC
18
VPLL
V
17
P
16
GND
15
REF
TAGC
14
CVBS
13
TR
12
SIO
11
2000 Nov 22 6
Philips Semiconductors Product specification
Alignment-free multistandard vision and
FM sound IF-PLL demodulator
FUNCTIONAL DESCRIPTION
Figure 1 shows the simplified block diagram of the
integrated circuit. The integrated circuit comprises the
following functional blocks:
1. VIF amplifier
2. Tuner-AGC and VIF-AGC
3. VIF-AGC detector
4. Frequency Phase-Locked Loop (FPLL) detector
5. VCO and Travelling Wave Divider (TWD)
6. Digital acquisition help and AFC
7. Video demodulator and amplifier
8. Sound carrier trap
9. Intercarrier mixer
10. FM demodulator and acquisition help
11. Audio amplifier
12. Internal voltage stabilizer.
VIF amplifier
The VIF amplifier consists of three AC-coupled differential
amplifier stages. Each differential stage comprises a
feedback network controlled by emitter degeneration.
Tuner-AGC and VIF-AGC
The AGC capacitor voltage is converted to an internal VIF
gaincontrol signal, and is fedto the tuner AGC togenerate
the tuner AGC output current at pin TAGC (open-collector
output). The tuner AGC takeover point can be adjusted
with R
filter in order to achieve the optimum IF input level.
VIF-AGC detector
The AGC detector generates the required VIF gain control
voltage for constant video output by charging or
discharging the AGC capacitor. Gain control is performed
by sync level detection. The newly developed AGC circuit
provides fast reaction time to cope with ‘aeroplane
fluttering’. The time constants for decreasing or increasing
gain are nearly equal.
. This allows the tuner to be matchedto the SAW
TOP
TDA9880T
After frequency lock-in the phase detector produces a DC
current proportional to the phase difference between the
VCO and the input signal. The DC current of either the
frequency detector or the phase detector is converted into
aDCvoltagevia the VIF-PLL filter, which controls the VCO
frequency.
VCO and Travelling Wave Divider (TWD)
The Resistor Capacitor (RC) VCO operates as an
integrated relaxation oscillator atdouble the picture carrier
frequency.The control voltage required totunethe VCO to
actually double the picture carrier frequency is generated
by the FPLL detector and fed via the loop filter to the VCO
control input terminal.
The oscillator signal is divided-by-two with a TWD which
generatestwo differential output signals witha 90 degrees
phase difference independent of the frequency.
Digital acquisition help and AFC
The integrated relaxation oscillator has a very wide
frequency range from approximately 30 to 70 MHz (after
the TWD). To prevent false locking of the FPLL and with
respect to the catching range of the frequency detector of
maximum ±2.5 MHz, the Digital Acquisition Help (DAH)
provides current into the loop filter until the VCO is in a
frequency window of ±2.3 MHz around the wanted VIF
frequency. In this case the analog operating FPLL willlock
the VCO to the VIF carrier and the acquisition help does
not provide any current to the loop filter.
The principle of the digital acquisition help is as follows:
the VCO is connected to a downcounter, which is preset
depending on the required VIF frequency. The counting
time, as well as the counter control, is derived from a
4 MHz reference signal. This signal can be supplied from
the internal 4 MHz crystal oscillator or from the 4 MHz
reference oscillator of an external tuning system.
The counting result after a counting cycle corresponds to
the actual VCO frequency.
The digital AFC is also derived from the counting result
after a counting cycle by digital-to-analog converting the
last four bits of the counter.
Frequency Phase-Locked Loop (FPLL) detector
The VIF amplifier output signal is fed into a Frequency
Detector(FD) and into a PhaseDetector (PD) via a limiting
amplifier. During acquisition the frequency detector
produces a DC current proportional to the frequency
difference between the input and the VCO signal.
2000 Nov 22 7
Video demodulator and amplifier
The video demodulator is realized by a multiplier which is
designedforlowdistortionandlargebandwidth.Thevision
IF input signal is multiplied with the ‘in phase’ signal of the
travelling wave divider output.
Philips Semiconductors Product specification
Alignment-free multistandard vision and
FM sound IF-PLL demodulator
The demodulator output signal is fed via an integrated
low-pass filter for attenuation of the carrier harmonics to
the video amplifier. The video amplifier is realized by an
operational amplifier with internal feedback and high
bandwidth. A low-pass filter is integrated to achieve an
attenuation of the carrier harmonics. The video signal of
1.1 V (p-p) for nominal vision IF modulation is fed
internally to the integrated sound carrier trap as well as to
the VIF-AGC detector. The second stage of the video
amplifier converts and amplifies the differential output
signal from the sound carrier trap to the single-ended
CVBS output signal at pin 13 with a 2 V (p-p) amplitude.
Noise clipping is provided. Furthermore the trap can be
bypassed by the implemented input switch of the second
amplifier stage, forced by connecting pin 12 to ground.
Sound carrier trap
The sound carrier trap consists of a reference filter, a
phase detector and the sound trap itself.
A sound carrier reference signal is fed into the reference
low-pass filter and is shifted by a nominal 90 degrees.
The phasedetectorcomparestheoriginalreferencesignal
with the signal shiftedby the reference filter and produces,
at the external capacitor CTR, a DC voltage by charging or
discharging the capacitor with a current proportional to the
phase difference between both signals, respectively to the
frequency error of the integrated filters. The DC voltage is
converted to currents which control the frequency position
of the reference filter and the sound trap.
The sound trap itselfis constructed of three separate traps
to realize sufficient suppression of the first and second
sound carrier. The right frequency position of the different
standards is set by the sound carrier reference signal.
Intercarrier mixer
The intercarrier mixer is realized by a multiplier, operating
inquadraturemodeforsuppressionoflowfrequencyvideo
signals. The VIF amplifier output signal is fed to the
intercarrier mixer and converted to an intercarrier
frequency by the regenerated 90 degree picture carrier
from the VCO. The mixer output signal is fed via a
band-pass filter and amplifier for attenuation of the high
frequency video signal components and carrier harmonics
to the output pin 11. The intercarrier signal is fed also to
the integrated FM demodulator.
TDA9880T
FM demodulator and acquisition help
The FM demodulator is realized as a narrow-band PLL
with external loop filter, which provides the necessary
selectivity. To achieve good selectivity, a linear phase
detector and constant input level are required. The
intercarrier signal from the intercarrier mixer is fed via a
gain controlled amplifier to the phase detector and it’s
output signal controls (via the loop filter) the integrated
relaxation oscillator. The possible frequency range is from
4 to 7 MHz. As a result of locking the oscillator frequency
tracks with the FM modulation of the input signal;
therefore,theoscillator control voltage is superimposed by
the AF voltage. In this way the FM-PLL operates as an
FM demodulator. The AF voltage is present at the loop
filter and is fed via a buffer with 0 dB gain to the audio
amplifier.
The digital acquisition help operates in the same way as
described in Section “Digital acquisition help and AFC”.
Audio amplifier
The audio amplifier consists of two parts:
1. The AF preamplifier is an operational amplifier with
internal feedback, high gain and high common mode
rejection. The AF voltage from the PLL demodulator,
by principle a small output signal, is amplified by
30 dB. A DC operating point control circuit (pin 6)
decouples the AF amplifier from the DC voltage of the
PLL. The low-pass characteristic of the amplifier
reduces the harmonics of the intercarrier signal at the
sound output terminal. If required, a de-emphasis
network can be realized by the amplifier output
resistance and an external capacitor.
2. The AF output amplifier (10 dB) provides the required
output level by a rail-to-rail output stage. This amplifier
makes use of an input selector for switching to mute
state, automatically controlled by the mute switching
voltage from the digital acquisition help in order to
avoid lock-in noise. During normal operation the
automatic audio mute function is not active.
Application of a 2.2 kΩ resistor between the
intercarrier output (pin 11) and ground will activate the
automatic audio mute function.
Internal voltage stabilizer
The band gap circuit internally generates a voltage of
approximately 2.4 V, independent of the supply voltage
and the temperature. Avoltage regulator circuit, controlled
by this voltage, produces a constant voltage of 3.55 V
which is used as an internal reference voltage.
2000 Nov 22 8
Philips Semiconductors Product specification
Alignment-free multistandard vision and
TDA9880T
FM sound IF-PLL demodulator
LIMITING VALUES
In accordance with the Absolute Maximum Rating System (IEC 60134).
SYMBOL PARAMETER CONDITIONS MIN. MAX. UNIT
V
P
V
n
t
sc
T
stg
T
amb
V
es
Notes
1. Charge device model class A; machine model: discharging a 200 pF capacitor via a 0.75 µH inductance.
2. Charge device model class B; human body model: discharging a 100 pF capacitor via a 1.5 kΩ series resistor.
supply voltage IP= 115 mA; T
=70°C; at
amb
− 5.5 V
maximum chip temperature of 125 °C
voltage at
pins 1 to 4, 6 to 10, 12 and 17 to 20 0 V
P
V
pin 14 0 13.2 V
short-circuit time to ground or V
P
− 10 s
storage temperature −25 +150 °C
ambient temperature −20 +70 °C
electrostatic handling voltage for all
pins
note 1 −250 +250 V
note 2 −3000 +3000 V
THERMAL CHARACTERISTICS
SYMBOL PARAMETER CONDITIONS VALUE UNIT
R
th(j-a)
thermal resistance from junction to ambient in free air 85 K/W
2000 Nov 22 9
Philips Semiconductors Product specification
Alignment-free multistandard vision and
TDA9880T
FM sound IF-PLL demodulator
CHARACTERISTICS
VP=5V; T
PC/SC = 10 dB) is used for specification; V
1 : 1; DSB video modulation; 10% residual carrier; video signal in accordance with
taken in test circuit of Fig.18; unless otherwise specified.
SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT
Supply (pin 17)
V
P
I
P
P
tot
VIF amplifier (pins 1 and 2)
V
i(sens)(VIF)(rms)
V
i(max)(rms)
∆V
int
G
VIF(cr)
B
VIF(−3dB)(ll)
B
VIF(−3dB)(ul)
R
i(dif)
C
i(dif)
V
I
FPLL and true synchronous video demodulator; note 4
f
VCO(max)
f
VIF
∆f
VIF
t
acq
V
i(sens)(VIF)(rms)
SIGNAL AT PIN 18
I
o(source)(PD)(max)
=25°C; see Table 2 for input frequencies; M standard (fPC= 45.75 MHz; fSC= 41.25 MHz;
amb
i(VIF)(rms)
= 10 mV (sync level); IF input from 50 Ω via broadband transformer
“NTC-7 Composite”
supply voltage note 1 4.5 5 5.5 V
supply current 85 100 115 mA
total power dissipation − 500 633 mW
VIF input voltage sensitivity
−1 dB video at output − 50 100 µV
(RMS value)
maximum input signal voltage
(RMS value)
internal IF amplitudedifference
between picture and sound
1 dB video at output;
note 2
within AGC range;
∆f = 4.5 MHz
110 −−mV
− 0.7 1 dB
carrier
VIF gain control range see Fig.3 65 69 − dB
lower limit −3 dB VIF
− 15 25 MHz
bandwidth
upper limit −3 dB VIF
70 100 − MHz
bandwidth
differential input resistance note 3 1.7 2.2 2.7 kΩ
differential input capacitance note 3 1.2 1.7 2.5 pF
DC input voltage − 3.35 − V
maximum oscillator frequency
f=2f
PC
120 140 − MHz
for carrier regeneration
vision carrier operating
frequencies
see Table 2 − 38.0 − MHz
− 38.9 − MHz
− 45.75 − MHz
− 58.75 − MHz
VIFfrequency window of digital
referenced to f
VIF
−±2.38 − MHz
acquisition help
acquisition time BL = 70 kHz; note 5 −−30 ms
VIF input voltage sensitivity at
pins 1 and 2 (RMS value)
for PLL to be locked maximum IF gain − 30 70 µV
for C/N = 10 dB notes 6 and 7 − 100 140 µV
maximum source current of
− 17 −µA
phase detector output
; measurements
2000 Nov 22 10
Philips Semiconductors Product specification
Alignment-free multistandard vision and
TDA9880T
FM sound IF-PLL demodulator
SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT
I
o(sink)(PD)(max)
I
o(source)(DAH)
I
o(sink)(DAH)
t
W(min)(DAH)
K
O(VIF)
K
D(VIF)
Video output signal and sound carrier trap (pin 13; sound carrier off)
V
o(v)(p-p)
V
sync
V
zc
V
v(clu)
V
v(cll)
R
o
I
bias(int)
I
o(source)(max)
I
o(sink)(max)
∆V
o
∆V
o(bl)
G
dif
ϕ
dif
B
v(−3dB)(trap)
maximum sink current of
− 17 −µA
phase detector output
output source current of digital
− 23 −µA
acquisition help
output sink current of digital
− 23 −µA
acquisition help
minimum pulse width of digital
− 64 −µs
acquisition help current
VCO steepness ∆f
phase detector steepness
∆I18/∆ϕ
VIF
video output signal voltage
VIF
/∆V
18
− 20 − MHz/V
− 23 −µA/rad
see Fig.9 1.7 2.0 2.3 V
(peak-to-peak value)
sync pulse voltage level see Fig.9 1.15 1.35 1.55 V
zero carrier voltage level see Fig.9 3.27 3.57 3.87 V
upper video clipping voltage
VP− 1.1 VP− 1 − V
level
lower video clipping voltage
− 0.7 1.0 V
level
output resistance note 3 −−30 Ω
internal DC bias current for
2.0 2.5 − mA
emitter-follower
maximum AC and DC output
2.4 −−mA
source current
maximum AC and DC output
1.4 −−mA
sink current
deviation of CVBS output
signal voltage
50 dB gain control −−0.5 dB
30 dB gain control −−0.1 dB
black level tilt −−1%
differential gain
differential phase
−3 dB video bandwidth
including sound carrier trap
“NTC-7 Composite”
“NTC-7 Composite”
CL< 20 pF; RL>1kΩ;
AC load; note 8
f
= 4.5 MHz
trap
− 25%
− 2 4 deg
3.95 4.05 − MHz
(M/N standard)
f
= 5.5 MHz
trap
4.90 5.00 − MHz
(B/G standard)
= 6.0 MHz
f
trap
5.2 5.50 − MHz
(I standard)
f
= 6.5 MHz
trap
5.5 5.95 − MHz
(D/K standard)
2000 Nov 22 11
Philips Semiconductors Product specification
Alignment-free multistandard vision and
TDA9880T
FM sound IF-PLL demodulator
SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT
α
SC1
α
SC1(60 kHz)
α
SC2
α
SC2(60 kHz)
t
d(g)(CC)
S/N
W
S/N
UW
αd
blue
αd
yellow
∆V
r(vc)(rms)
α
H(sup)
α
H(spur)
PSRR
13
trap attenuation at first sound
carrier
M/N standard 30 36 − dB
B/G standard 30 36 − dB
I standard 26 32 − dB
D/K standard 26 32 − dB
trap attenuation at first sound
carrier f
SC1
±60 kHz
M/N standard 21 27 − dB
B/G standard 24 30 − dB
I standard 20 26 − dB
D/K standard 20 26 − dB
trap attenuation at second
sound carrier
M/N standard 21 27 − dB
B/G standard 21 27 − dB
I standard 12 18 − dB
D/K standard 18 24 − dB
trap attenuation at second
sound carrier f
SC2
±60 kHz
M/N standard 15 21 − dB
B/G standard 15 21 − dB
I standard 10 15 − dB
D/K standard 13 18 − dB
group delay at chrominance
carrier frequency
3.58 MHz at
M/N standard
4.43 MHz at B/G standard 110 180 250 ns
4.43 MHz at I standard − 90 160 ns
4.28 MHz at D/K standard − 60 130 ns
weighted signal-to-noise ratio weighted in accordance
with
“CCIR 567”
;
see Fig.5; note 9
unweighted signal-to-noise
note 9 47 51 − dB
ratio
intermodulation attenuation at
‘blue’
f = 0.92 MHz; see Fig.6;
note 10
f = 2.76 MHz; see Fig.6;
note 10
intermodulation attenuation at
‘yellow’
f = 0.92 MHz; see Fig.6;
note 10
f = 2.76 MHz; see Fig.6;
note 10
residual vision carrier
(RMS value)
harmonics suppression in
video signal
spuriouselementssuppression
fundamental wave and
harmonics
CL< 20 pF; RL>1kΩ;
AC load; note 11a
note 11b 40 −−dB
in video signal
powersupply ripple rejectionat
pin 13
f
= 70 Hz; video
ripple
signal; grey level;
see Fig.8
110 180 250 ns
56 60 − dB
58 64 − dB
58 64 − dB
60 66 − dB
59 65 − dB
− 25mV
35 40 − dB
25 28 − dB
2000 Nov 22 12
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