MOTOROLA MC33033 User Manual

T

40° t

85°C

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The MC33033 is a high performance second generation, limited feature,
monolithic brushless dc motor controller which has evolved from Motorola′s
full featured MC33034 and MC33035 controllers. It contains all of the active
functions required for the implementation of open loop, three or four phase
motor control. The device consists of a rotor position decoder for proper
commutation sequencing, temperature compensated reference capable of
supplying sensor power, frequency programmable sawtooth oscillator, fully
accessible error amplifier, pulse width modulator comparator, three open
collector top drivers, and three high current totem pole bottom drivers ideally
suited for driving power MOSFETs. Unlike its predessors, it does not feature
separate drive circuit supply and ground pins, brake input, or fault output
signal.

Included in the MC33033 are protective features consisting of
undervoltage lockout, cycle–by–cycle current limiting with a selectable time
delayed latched shutdown mode, and internal thermal shutdown.

Typical motor control functions include open loop speed, forward or
reverse direction, and run enable.The MC33033 is designed to operate
brushless motors with electrical sensor phasings of 60°/300° or 120°/240°,
and can also efficiently control brush dc motors.

Order this document by MC33033/D



BRUSHLESS DC

MOTOR CONTROLLER

SEMICONDUCTOR

TECHNICAL DATA

20

1

P SUFFIX

PLASTIC PACKAGE

CASE 738

• 10 to 30 V Operation

• Undervoltage Lockout

• 6.25 V Reference Capable of Supplying Sensor Power

• Fully Accessible Error Amplifier for Closed Loop Servo Applications

• High Current Drivers Can Control External 3–Phase MOSFET Bridge

• Cycle–By–Cycle Current Limiting

• Internal Thermal Shutdown

• Selectable 60°/300° or 120°/240° Sensor Phasings

• Also Efficiently Control Brush DC Motors with External MOSFET

H–Bridge

ORDERING INFORMATION

Operating

Device

MC33033DW
MC33033P

Temperature Range

°

A

= –

o +

°

Package

SO–20L

Plastic DIP

20

PLASTIC PACKAGE

PIN CONNECTIONS

Top Drive

Output

Sensor

Inputs

Reference Output

Non Inverting Input

Inverting Input

B

T

A

T

S

A

S

B

S

C

Oscillator

Error Amp
Error Amp

1

DW SUFFIX

CASE 751D

(SO–20L)

1
2
3

4
5
6

7
8
9

10

20

C

T

19

Output Enable

18

°

/120°SelectFwd/Rev

60
A

17

B

16
15
14
13
12
11

Bottom

B

Drive

B

Outputs

C

B

V

CC

Gnd
Current Sense

Non Inverting Input
Error Amp Out/
PWM Input

(Top View)

 Motorola, Inc. 1996 Rev 3

MOTOROLA ANALOG IC DEVICE DATA

1

FWR/REV

60°/120

Enable

Speed
Set

R

T

C

T

°

V

Faster

CC

Reference

Regulator

Error Amp

Oscillator

PWM

MC33033

Representative Schematic Diagram

Rotor

Position

Decoder

Undervoltage

Lockout

Thermal

Shutdown

R

Q

S
S

Q

R

V

M

Output

Buffers

N

SS

N

Motor

This device contains 266 active transistors.

Current Sense

2

MOTOROLA ANALOG IC DEVICE DATA

MC33033

MAXIMUM RATINGS

Rating Symbol Value Unit

Power Supply Voltage V
Digital Inputs (Pins 3, 4, 5, 6, 18, 19) – V

Oscillator Input Current (Source or Sink) I
Error Amp Input Voltage Range

(Pins 9, 10, Note 1)

Error Amp Output Current

(Source or Sink, Note 2)
Current Sense Input Voltage Range V
Top Drive V oltage (Pins 1, 2, 20) V
Top Drive Sink Current (Pins 1, 2, 20) I
Bottom Drive Output Current

(Source or Sink, Pins 15,16, 17)
Power Dissipation and Thermal Characteristics

P Suffix, Dual–In–Line, Case 738

Maximum Power Dissipation @ TA = 85°C P
Thermal Resistance, Junction–to–Air R

DW Suffix, Surface Mount, Case 751D

Maximum Power Dissipation @ TA = 85°C P

Thermal Resistance, Junction–to–Air R
Operating Junction Temperature T
Operating Ambient Temperature Range T
Storage Temperature Range T

CC

OSC
V

IR

I

Out

Sense

CE(top)

Sink(top)

I

DRV

D

θJA

D

θJA

J

A

stg

–0.3 to V

–0.3 to 5.0 V

–40 to +85 °C

–65 to +150 °C

30 V

ref

30 mA

ref

10 mA

40 V
50 mA

100 mA

867 mW

75 °C/W

619 mW
105 °C/W

150 °C

V

V

ELECTRICAL CHARACTERISTICS (V

Characteristic

REFERENCE SECTION

Reference Output Voltage (I

TA = 25°C
TA = –40° to + 85°C

Line Regulation (VCC = 10 V to 30 V, I
Load Regulation (I
Output Short–Circuit Current (Note 3) I
Reference Under Voltage Lockout Threshold V

ERROR AMPLIFIER

Input Offset Voltage (TA = –40° to + 85°C) V
Input Offset Current (TA = –40° to + 85°C) I

Input Bias Current (TA = –40° to + 85°C) I
Input Common Mode Voltage Range V
Open Loop Voltage Gain (VO = 3.0 V, RL = 15 k) A
Input Common Mode Rejection Ratio CMRR 55 86 – dB
Power Supply Rejection Ratio (VCC = 10 V to 30 V) PSRR 65 105 – dB
Output Voltage Swing

High State (RL = 15 k to Gnd)
Low State (RL = 17 k to V

NOTES: 1. The input common mode voltage or input signal voltage should not be allowed to go negative by more than 0.3 V.

2.The compliance voltage must not exceed the range of –0.3 to V

3.Maximum package power dissipation limits must be observed.

= 1.0 mA to 20 mA) Reg

ref

= 1.0 mA)

ref

)

ref

= 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.)

CC

Symbol Min Typ Max Unit

V

= 1.0 mA) Reg

ref

ref

ref

line

load

SC

th

IO

IO
IB

ICR

VOL

V

OH

V

OL

.

5.9

5.82
– 1.5 30 mV

– 16 30 mV

40 75 – mA

4.0 4.5 5.0 V

– 0.4 10 mV
– 8.0 500 nA

– –46 –1000 nA

70 80 – dB

4.6
–

6.24
–

(0 V to V

5.3

0.5

6.5

6.57

ref)

–

1.0

V

V

V

MOTOROLA ANALOG IC DEVICE DATA

3

MC33033

ELECTRICAL CHARACTERISTICS

Characteristic

OSCILLATOR SECTION

Oscillator Frequency f
Frequency Change with Voltage (VCC = 10 V to 30 V) ∆f
Sawtooth Peak Voltage V
Sawtooth Valley Voltage V

LOGIC INPUTS

Input Threshold Voltage (Pins 3, 4, 5, 6, 18, 19)

High State
Low State

Sensor Inputs (Pins 4, 5, 6)

High State Input Current (VIH = 5.0 V)
Low State Input Current (VIL = 0 V)

Forward/Reverse, 60°/120° Select and Output Enable
(Pins 3, 18, 19)

High State Input Current (VIH = 5.0 V)
Low State Input Current (VIL = 0 V)

CURRENT–LIMIT COMPARATOR

Threshold Voltage V
Input Common Mode Voltage Range V

Input Bias Current I

OUTPUTS AND POWER SECTIONS

Top Drive Output Sink Saturation (I
Top Drive Output Off–State Leakage (VCE = 30 V) I
Top Drive Output Switching Time (CL = 47 pF, RL = 1.0 k)

Rise Time
Fall Time

Bottom Drive Output Voltage

High State (VCC = 30 V, I
Low State (VCC = 30 V, I

Bottom Drive Output Switching Time (CL = 1000 pF)

Rise Time
Fall Time

Under Voltage Lockout

Drive Output Enabled (VCC Increasing)
Hysteresis

Power Supply Current I

source

sink

= 50 mA)

(continued) (VCC = 20 V, RT = 4.7 k, CT = 10 nF, TA = 25°C, unless otherwise noted.)

= 25 mA) V

Sink

DRV(leak)

= 50 mA)

Symbol Min Typ Max Unit

OSC

/∆V – 0.01 5.0 %

OSC
OSC(P)
OSC(V)

V

IH

V

IL

I

IH

I

IL

I

IH

I

IL

th

ICR

IB

CE(sat)

t

r

t

f

V

OH

V

OL

t

r

t

f

V

th(on)

V

H

CC

22 25 28 kHz

– 4.1 4.5 V

1.2 1.5 – V

3.0
–

–150
–600

–75

–300

85 101 115 mV

– 3.0 – V
– –0.9 –5.0 µA

– 0.5 1.5 V
– 0.06 100 µA

–
–

(VCC – 2.0)–(VCC – 1.1)

–
–

8.2

0.1
– 15 22 mA

2.2

1.7

–70

–337

–36

–175

107

26

1.5

38
30

8.9

0.2

–

0.8

–20

–150

–10
–75

300
300

–

2.0

200
200

10

0.3

V

µA

µA

ns

V

ns

V

4

MOTOROLA ANALOG IC DEVICE DATA

MC33033

Figure 1. Oscillator Frequency versus

100

10

OSCILLA TOR FREQUENCY (kHz)

CT = 100 nF

,

OSC

f

0

1.0

Figure 3. Error Amp Open Loop Gain and

56
48
40
32

24
16

VCC = 20 V

8.0

VO = 3.0 V
RL = 15 k

0

CL = 100 pF

–8.0

, OPEN–LOOP VOLTAGE GAIN (dB)

TA = 25

–16

VOL

A

–24

1.0 k

Timing Resistor

CT = 10 nF

RT, TIMING RESISTOR (kΩ)

Phase versus Frequency

Gain

°

C

f, FREQUENCY (Hz)

VCC = 20 V

TA = 25

CT = 1.0 nF

Phase

Figure 2. Oscillator Frequency Change

versus T emperature

4.0

°

C

100010010

2.0

0

–2.0

OSCILLA T OR FREQUENCY CHANGE (%)

,

OSC

–4.0

f

∆

–55

VCC = 20 V
RT = 4.7 k

CT = 10 nF

TA, AMBIENT TEMPERATURE (°C)

125

1007550250–25

Figure 4. Error Amp Output Saturation

V oltage versus Load Current

40
60
80
100

120
140
160
180

EXCESS PHASE (DEGREES)

,

200

φ

220
240

10M1.0 M100 k10 k

– 0.8

–1.6

, OUTPUT SA TURATION VOLTAGE (V)

sat

V

1.6

0.8

0

0

V

ref

Source Saturation

(Load to Ground)

Sink Saturation

Gnd

1.0 2.0
IO, OUTPUT LOAD CURRENT (mA)

(Load to V

ref

VCC = 20 V

TA = 25

)

°

C

5.04.03.00

Figure 5. Error Amp Small–Signal

Transient Response

3.05

3.0

, OUTPUT VOL TAGE (V)

O

V

2.95

µ

s/DIV

1.0

MOTOROLA ANALOG IC DEVICE DATA

AV = +1.0

No Load

°

TA = 25

Figure 6. Error Amp Large–Signal

Transient Response

AV = +1.0

No Load
TA = 25

°

C

, OUTPUT VOL TAGE (V)
V

O

4.5

3.0

1.5

5.0 µs/DIV

C

5

MC33033

Figure 7. Reference Output V oltage Change

versus Output Source Current

0

–4.0

–8.0

– 12

– 16

0

VCC = 20 V

°

C

TA = 25

I

, REFERENCE OUTPUT SOURCE CURRENT (mA)

ref

–20

REFERENCE OUTPUT VOL TAGE CHANGE (mV)

–24

ref,

V

∆

Figure 9. Reference Output Voltage

versus T emperature

40

20

0

–20

–40

NORMALIZED REFERENCE VOLTAGE CHANGE (mV)

ref,

V

∆

–25

–55 0

TA, AMBIENT TEMPERATURE (

°

C)

VCC = 20 V

No Load

Figure 8. Reference Output V oltage versus

Supply V oltage

7.0

6.0

5.0

4.0

3.0

2.0

REFERENCE OUTPUT VOLTAGE (V)

1.0

ref,

V

0

605040302010

0

VCC, SUPPLY VOLTAGE (V)

No Load
TA = 25

°

C

40302010

Figure 10. Output Duty Cycle versus

PWM Input Voltage

100

80

60

40

20

OUTPUT DUTY CYCLE (%)

125100755025

0

0

VCC = 20 V

RT = 4.7 k

CT = 10 nF

°

C

TA = 25

PWM INPUT VOLTAGE (V)

5.04.03.02.01.0

Figure 11. Bottom Drive Response T ime versus

Current Sense Input Voltage

250

200

150

100

50

, BOTTOM DRIVE RESPONSE TIME (ns)

HL

t

0

1.0 2.0 3.0 4.0 5.0 7.0 8.0 10
V

, CURRENT SENSE INPUT VOLTAGE (NORMALIZED TO Vth)

Sense

VCC = 20 V
RL =
CL = 1.0 nF
TA = 25

6.0 9.0

6

Figure 12. Top Drive Output Saturation Voltage

versus Sink Current

1.2
VCC = 20 V

°

C

1

, OUTPUT SA TURATION VOLTAGE (V)V

sat

0.8

0.4

0

°

C

TA = 25

040302010

I

, SINK CURRENT (mA)

Sink

MOTOROLA ANALOG IC DEVICE DATA

MC33033

OUTPUT VOLTAGE (%)

Figure 13. Top Drive Output Waveform

100

VCC = 20 V

RL = 1.0 k

0

CL = 15 pF

°

C

TA = 25

50 ns/DIV

Figure 15. Bottom Drive Output Waveform

VCC = 20 V
CL = 15 pF

°

C

TA = 25

100

OUTPUT VOLTAGE (%)

Figure 14. Bottom Drive Output Waveform

100

0

50 ns/DIV

Figure 16. Bottom Drive Output Saturation

V oltage versus Load Current

–1.0

–2.0

0

VCC = 20 V

TA = 25

V

CC

°

C

VCC = 20 V
CL = 1.0 nF

°

C

TA = 25

Source Saturation

(Load to Ground)

OUTPUT VOLTAGE (%)

2.0

0

50 ns/DIV

, OUTPUT SA TURATION VOLTAGE (V)
V

sat

1.0
Gnd

0

0

IO, OUTPUT LOAD CURRENT (mA)

40

Sink Saturation

(Load to VCC)

806020

Figure 17. Supply Current versus V oltage

20
18
16
14
12

8.0

6.0

4.0

, POWER SUPPLY CURRENT (mA)

CC

2.0

I

10

0

0

VCC, SUPPLY VOLTAGE (V)

RT = 4.7 k
CT = 10 nF

Pins 3–6, 12, 13 = Gnd

Pins 18, 19 = Open

°

C

TA = 25

30252015105.0

MOTOROLA ANALOG IC DEVICE DATA

7

MC33033

PIN FUNCTION DESCRIPTION

Pin Symbol Description

1, 2, 20 BT, AT, C

3 Fwd//Rev The Forward/Reverse Input is used to change the direction of motor rotation.

4, 5, 6 SA, SB, S

7 Reference Output This output provides charging current for the oscillator timing capacitor CT and a

8 Oscillator The Oscillator frequency is programmed by the values selected for the timing

9 Error Amp Noninverting Input This input is normally connected to the speed set potentiometer.
10 Error Amp Inverting Input This input is normally connected to the Error Amp Output in open loop applications.
11 Error Amp Out/PWM Input This pin is available for compensation in closed loop applications.
12 Current Sense Noninverting Input A 100 mV signal, with respect to Pin 13, at this input terminates output switch conduction

13 Gnd This pin supplies a separate ground return for the control circuit and should be

14 V

15, 16, 17 CB, BB, A

18 60°/120° Select The electrical state of this pin configures the control circuit operation for either 60°

19 Output Enable A logic high at this input causes the motor to run, while a low causes it to coast.

T

C

CC

B

These three open collector Top Drive Outputs are designed to drive the external upper
power switch transistors.

These three Sensor Inputs control the commutation sequence.

reference for the Error Amplifier . It may also serve to furnish sensor power.

components, RT and CT.

during a given oscillator cycle. This pin normally connects to the top side of the current
sense resistor.

referenced back to the power source ground.
This pin is the positive supply of the control IC. The controller is functional over a V

range of 10 to 30 V .
These three totem pole Bottom Drive Outputs are designed for direct drive of the external

bottom power switch transistors.

(high state) or 120° (low state) sensor electrical phasing inputs.

CC

8

MOTOROLA ANALOG IC DEVICE DATA

MC33033

INTRODUCTION

The MC33033 is one of a series of high performance
monolithic dc brushless motor controllers produced by
Motorola. It contains all of the functions required to
implement a limited–feature, open loop, three or four phase
motor control system. Constructed with Bipolar Analog
technology, it offers a high degree of performance and
ruggedness in hostile industrial environments.The MC33033
contains a rotor position decoder for proper commutation
sequencing, a temperature compensated reference capable
of supplying sensor power, a frequency programmable
sawtooth oscillator, a fully accessible error amplifier, a pulse
width modulator comparator, three open collector top drive
outputs, and three high current totem pole bottom driver
outputs ideally suited for driving power MOSFETs.

Included in the MC33033 are protective features
consisting of undervoltage lockout, cycle–by–cycle current
limiting with a latched shutdown mode, and internal thermal
shutdown.

Typical motor control functions include open loop speed
control, forward or reverse rotation, and run enable. In
addition, the MC33033 has a 60°/120
configures the rotor position decoder for either 60° or 120°
sensor electrical phasing inputs.

° select pin which

FUNCTIONAL DESCRIPTION

A representative internal block diagram is shown in
Figure 18, with various applications shown in Figures 34, 36,
37, 41, 43, and 44. A discussion of the features and function
of each of the internal blocks given below and referenced to
Figures 18 and 36.

Rotor Position Decoder

An internal rotor position decoder monitors the three
sensor inputs (Pins 4, 5, 6) to provide the proper sequencing
of the top and bottom drive outputs. The Sensor Inputs are
designed to interface directly with open collector type Hall
Effect switches or opto slotted couplers. Internal pull–up
resistors are included to minimize the required number of
external components. The inputs are TTL compatible, with
their thresholds typically at 2.2 V. The MC33033 series is
designed to control three phase motors and operate with four
of the most common conventions of sensor phasing. A
60°/120
affords the MC33033 to configure itself to control motors
having either 60°, 120°, 240° or 300° electrical sensor
phasing. With three Sensor Inputs there are eight possible
input code combinations, six of which are valid rotor
positions. The remaining two codes are invalid and are
usually caused by an open or shorted sensor line. With six
valid input codes, the decoder can resolve the motor rotor
position to within a window of 60 electrical degrees.

direction of motor rotation by reversing the voltage across the
stator winding. When the input changes state, from high to
low with a given sensor input code (for example 100), the
enabled top and bottom drive outputs with the same alpha
designation are exchanged (AT to AB, BT to BB, CT to CB). In

° Select (Pin 18) is conveniently provided which

The Forward/Reverse input (Pin 3) is used to change the

effect the commutation sequence is reversed and the motor
changes directional rotation.

Motor on/off control is accomplished by the Output Enable
(Pin19). When left disconnected, an internal pull–up resistor
to a positive source enables sequencing of the top and
bottom drive outputs. When grounded, the T op Drive Outputs
turn off and the bottom drives are forced low, causing the
motor to coast.

The commutation logic truth table is shown in Figure 19. In
half wave motor drive applications, the T op Drive Outputs are
not required and are typically left disconnected.

Error Amplifier

A high performance, fully compensated Error Amplifier
with access to both inputs and output (Pins 9, 10, 11) is
provided to facilitate the implementation of closed loop motor
speed control. The amplifier features a typical dc voltage gain
of 80 dB, 0.6 MHz gain bandwidth, and a wide input common
mode voltage range that extends from ground to V
open loop speed control applications, the amplifier is
configured as a unity gain voltage follower with the
Noninverting Input connected to the speed set voltage
source. Additional configurations are shown in Figures 29
through 33.

Oscillator

The frequency of the internal ramp oscillator is
programmed by the values selected for timing components
RT and CT. Capacitor CT is charged from the Reference
Output (Pin 7) through resistor RT and discharged by an
internal discharge transistor. The ramp peak and valley
voltages are typically 4.1 V and 1.5 V respectively . To provide
a good compromise between audible noise and output
switching efficiency , an oscillator frequency in the range of 20
to 30 kHz is recommended. Refer to Figure 1 for component
selection.

Pulse Width Modulator

The use of pulse width modulation provides an energy
efficient method of controlling the motor speed by varying the
average voltage applied to each stator winding during the
commutation sequence. As CT discharges, the oscillator sets
both latches, allowing conduction of the Top and Bottom
Drive Outputs. The PWM comparator resets the upper latch,
terminating the Bottom Drive Output conduction when the
positive–going ramp of CT becomes greater than the Error
Amplifier output. The pulse width modulator timing diagram is
shown in Figure 20. Pulse width modulation for speed control
appears only at the Bottom Drive Outputs.

Current Limit

Continuous operation of a motor that is severely
over–loaded results in overheating and eventual failure.
This destructive condition can best be prevented with the
use of cycle–by–cycle current limiting. That is, each
on–cycle is treated as a separate event. Cycle–by–cycle
current limiting is accomplished by monitoring the stator
current build–up each time an output switch conducts, and
upon sensing an over current condition, immediately turning
off the switch and holding it off for the remaining duration of

. In most

ref

MOTOROLA ANALOG IC DEVICE DATA

9

Sensor Inputs

Foward/Reverse

60°/120°Select

Output Enable

Reference Output

Noninv. Input

Faster

R

T

Error Amp Out
PWM Input

C

T

Sink Only
Positive True

=

Logic With
Hysteresis

MC33033

Figure 18. Representative Block Diagram

V

M

A

B

Bottom

B

Drive

B

Outputs

C

B

Current Sense

Input

Top
Drive
Outputs

20 k

40 k

PWM

20 k

40 k

Undervoltage

8.9 V

4.5 V

Rotor

Position

Decoder

Thermal

Shutdown

Latch

R
S

Latch

S

R

13

Lockout

Q

Q

Gnd

I

Limit

100 mV

4

S

A

5

S

B

20 k

6

S

C

3

18

7

Error Amp

9

8

40 k

Reference

Regulator

Oscillator

19
14

V

CC

10
11

20

2

1

17

16

15

12

A

T

B

T

C

T

10

MOTOROLA ANALOG IC DEVICE DATA

MC33033

Figure 19. Three Phase, Six Step Commutation Truth Table (Note 1)

Inputs (Note 2) Outputs (Note 3)

Sensor Electrical Phasing (Note 4) Top Drives Bottom Drives

60°

S

S

A

1
1
1
0
0
0

1
1
1
0
0
0

1

0
V V V V V V X 0 X 1 1 1 0 0 0 (Note 7)
V V V V V V X 1 1 1 1 1 0 0 0 (Note 8)

NOTES: 1. V = Any one of six valid sensor or drive combinations.

S

B

C

0

0

1

0

1

1

1

1

0

1

0

0

0

0

1

0

1

1

1

1

0

1

0

0

0

1

1

0

X = Don’t care.

2.The digital inputs (Pins 3, 4, 5, 6, 18, 19) are all TTL compatible. The current sense input (Pin 12) has a 100 mV threshold with respect to Pin 13. A
logic 0 for this input is defined as < 85 mV, and a logic 1 is > 115 mV.

3.The top drive outputs are open collector design and active in the low (0) state.

4.With 60°/120
for 120° sensor electrical phasing inputs.

5.Valid 60° or 120° sensor combinations for corresponding valid top and bottom drive outputs.

6.Invalid sensor inputs; All top and bottom drives are off.

7.Valid sensor inputs with enable = 0; All top and bottom drives are off.

8.Valid sensor inputs with enable and current sense = 1; All top and bottom drives are off.

° (Pin 18) in the high (1) state, configuration is for 60° sensor electrical phasing inputs. With Pin 18 in the low (0) state, configuration is

120°

S

S

A

1
1
0
0
0
1

1
1
0
0
0
1

1
0

S

B

0
1
1
1
0
0

0
1
1
1
0
0

1
0

F/R Enable Sense ATB

C

0
0
0
1
1
1

0
0
0
1
1
1

1
0

1
1
1
1
1
1

0
0
0
0
0
0

X
X

Current

CTA

T

1
1
1
1
1
1

1
1
1
1
1
1

X
X

0
0
0
0
0
0

0
0
0
0
0
0

X
X

0

1
1
1
1
1
0

1
1
0
0
1
1

1
1

1

0

1

0

1

1

0

1

0

1

1

1

0

1

0

1

1

1

1

0

1

0

1

1

1

1

1

B

B

0
0
1
1
0
0

1
0
0
0
0
1

0
0

C

B

B

0

1

0

1

0

0

0

0

1

0

1

0

0

0

1

0

1

0

0

1

0

1

0

0

0

0

0

0

(Note 5)

F/R = 1

(Note 5)

F/R = 0

(Note 6)

oscillator ramp–up period. The stator current is converted to
a voltage by inserting a ground–referenced sense resistor R
(Figure 34) in series with the three bottom switch transistors
(Q4, Q5, Q6). The voltage developed across the sense
resistor is monitored by the current sense input (Pin 12), and
compared to the internal 100 mV reference. If the current
sense threshold is exceeded, the comparator resets the
lower latch and terminates output switch conduction. The
value for the sense resistor is:

RS+

0.1

I

stator(max)

The dual–latch PWM configuration ensures that only one
single output conduction pulse occurs during any given
oscillator cycle, whether terminated by the output of the Error
Amplifier or the current limit comparator.

Reference

The on–chip 6.25 V regulator (Pin 7) provides charging
current for the oscillator timing capacitor, a reference for the
Error Amplifier, and can supply 20 mA of current suitable for
directly powering sensors in low voltage applications. In
higher voltage applications it may become necessary to
transfer the power dissipated by the regulator off the IC. This
is easily accomplished with the addition of an external pass

transistor as shown in Figure 21. A 6.25 V reference level
was chosen to allow implementation of the simpler NPN

S

circuit, where V

– VBE exceeds the minimum voltage

ref

required by Hall Effect sensors over temperature. With
proper transistor selection, and adequate heatsinking, up to
one amp of load current can be obtained.

Undervoltage Lockout

A dual Undervoltage Lockout has been incorporated to
prevent damage to the IC and the external power switch
transistors. Under low power supply conditions, it guarantees
that the IC and sensors are fully functional, and that there is
sufficient Bottom Drive Output voltage. The positive power
supply to the IC (VCC) is monitored to a threshold of 8.9 V.
This level ensures sufficient gate drive necessary to attain
low R

when interfacing with standard power MOSFET

DS(on)

devices. When directly powering the Hall sensors from the
reference, improper sensor operation can result if the
reference output voltage should fall below 4.5 V. If one or
both of the comparators detects an undervoltage condition,
the top drives are turned off and the Bottom Drive Outputs
are held in a low state. Each of the comparators contain
hysteresis to prevent oscillations when crossing their
respective thresholds.

MOTOROLA ANALOG IC DEVICE DATA

11

MC33033

Capacitor C
Error Amp Out/

PWM Input

Current Sense

Input

Latch “Set”

Inputs

Top Drive

Outputs

Bottom Drive

Outputs

T

Figure 20. PWM Timing Diagram

Figure 21. Reference Output Buffers

UVLO

UVLO

36

0.1

14

REF

7

To

Control

Circuitry

6.25 V

14

REF

7

V

in

MPS

U01A

Sensor

Power

≈

5.6 V

V

in

MPS
U51A

To Control Circuitry

and Sensor Power

6.25 V

The NPN circuit is recommended for powering Hall or opto sensors, where the
output voltage temperature coefficient is not critical. The PNP circuit is slightly
more complex, but also more accurate. Neither circuit has current limiting.

Figure 22. High V oltage Interface with

NPN Power Transistors

2

Rotor

Position

Decoder

Transistor Q1 is a common base stage used to level shift from VCC to the high
motor voltage, VM. The collector diode is required if VCC is present while V
is low.

A

1

B

20

C

17

16

15

V

T

T

T

CC

Q

1

V

M

Q

2

Q

3

Load

Q

4

Figure 23. High V oltage Interface with

N–Channel Power MOSFETs

VCC = 12 V

2

Rotor

Position

Decoder

M

1

20

17

16

15

1.0 k

A

T

1

1.0 M

2

B

T

4.7 k

C

T

MOC8204

Optocoupler

Boost

5

6

4

1N4744

VM = 170 VV

Load

12

MOTOROLA ANALOG IC DEVICE DATA

MC33033

Figure 24. Current Waveform Spike Suppression Figure 25. MOSFET Drive Precautions

R

17

16

15

12

100 mV

The addition of the RC filter will eliminate current–limit instability caused
by the leading edge spike on the current waveform. Resistor RS should
be a low inductance type.

R

C

R

S

100 mV

Series gate resistor Rg will damp any high frequency oscillations caused
by the MOSFET input capacitance and any series wiring induction in the
gate–source circuit. Diode D is required if the negative current into the
Bottom Drive Outputs exceeds 50 mA.

17

16

15

12

D = 1N5819

Figure 26. Bipolar Transistor Drive Figure 27. Current Sensing Power MOSFETs

g

D

R

g

D

R

g

D

C

17

C

16

C

15

I

12

100 mV

The totem pole output can furnish negative base current for
enhanced transistor turn–off, with the addition of capacitor C.

B
+
0

–

Base Charge
Removal

Figure 28. High V oltage Boost Supply

VM + 12

VC = 12 V

8

6

5

2

1

MC1455

0.001

This circuit generates V

R
S

18 k

4

7

Q

3

Boost

VM + 8.0

Voltage (V)

Boost

VM + 4.0

V

1.0 µ/200 V

1N5352A

for Figure 23.

20

Boost Current (mA)

*

VM = 170 V

* = MUR115

D

SENSEFET

S

17

16

15

12

t

100 mV

13

Gnd

Virtually lossless current sensing can be achieved with the
implementation of SENSEFET power switches.

R

S

G

K

M

Power Ground:
To Input Source Return

V

Pin

If : SENSEFET = MPT10N10M
RS = 200

Then :

RS@

[

9

r

DM(on)

Ω

V

[

9

Pin

I

@

pk

, 1/4 W

0.75 I

R

DS(on)

)

R

pk

S

Figure 29. Differential Input Speed Controller

REF

7

19

R

1

40

60

*

22

V

Boost

V

A

R

V

B

V

11

Pin

9

R

2

3

10
11

R

4

R3)

+

V

ǒ

A

)

R

1

40 k

EA

PWM

R

R

4

Ǔ

R

2

R

2

4

–

V

ǒ

Ǔ

R

3

B

R

3

MOTOROLA ANALOG IC DEVICE DATA

13

MC33033

Figure 30. Controlled Acceleration/Deceleration Figure 31. Digital Speed Controller

5.0 V

16

11

REF

7

Enable

R

1

Increase
Speed

Resistor R1 with capacitor C sets the acceleration time constant while R
controls the deceleration. The values of R1 and R2 should be at least ten times
greater than the speed set potentiometer to minimize time constant variations
with different speed settings.

R

2

C

19

9

10

11

40 k

EA

PWM

V

CC

12

P3

13
14

15

P2
P1
P0

8

SN74LS145

Gnd

BCD

Inputs

2

The SN74LS145 is an open collector BCD to One of Ten decoder. When
connected as shown, input codes 0000 through 1001 steps the PWM in
increments of approximately 10% from 0 to 90% on–time. Input codes 1010
through 11 1 1 will produce 100% on–time or full motor speed.

166 k

Q

9

10

145 k

Q

8

126 k

9

Q

7

108 k

7

Q

6

92.3 k

6

Q

5

77.6 k

5

Q

4

4

63.6 k

Q

3

51.3 k

3

Q

2

2

40.4 k

Q

1

1

Q

0

100 k

7

19

9

10
11

REF

40 k

EA

PWM

Figure 32. Closed Loop Speed Control

REF

7

To Sensor

Input (Pin 4)

0.01

10 k

0.1

The rotor position sensors can be used as a tachometer. By differentiating the
positive–going edges and then integrating them over time, a voltage
proportional to speed can be generated. The error amp compares this voltage
to that of the speed set to control the PWM.

10 k

100 k

1.0 M

0.22

Increase
Speed

10 M

19

9

10
11

40 k

EA

PWM

Drive Outputs

The three Top Drive Outputs (Pins 1, 2, 20) are open
collector NPN transistors capable of sinking 50 mA with a
minimum breakdown of 30 V. Interfacing into higher voltage
applications is easily accomplished with the circuits shown in
Figures 22 and 23.

The three totem pole Bottom Drive Outputs (Pins 15, 16,

17) are particularly suited for direct drive of N–Channel
MOSFETs or NPN bipolar transistors (Figures 24, 25, 26,
and 27). Each output is capable of sourcing and sinking up
to 100 mA.

Thermal Shutdown

Internal thermal shutdown circuity is provided to protect
the IC in the event the maximum junction temperature is
exceeded. When activated, typically at 170°C, the IC acts
as though the regulator was disabled, in turn shutting down
the IC.

SYSTEM APPLICATIONS

Three Phase Motor Commutation

The three phase application shown in Figure 34 is an open
loop motor controller with full wave, six step drive. The upper

Figure 33. Closed Loop T emperature Control

R3)

R

R

V

+

V

11

Pi

n

V

+

B

§§

R

3

This circuit can control the speed of a cooling fan proportional to the difference
between the sensor and set temperatures. The control loop is closed as the
forced air cools the NTC thermistor. For controlled heating applications,
exchange the positions of R1 and R2.

ǒ

ref

V

ref

R

5

)

ǒ

R

6

R6ø

R

4

Ǔ

)

R

R

2

1

1

Ǔ

R

5

6

R

6

R

2

4

–

V

ǒ

Ǔ

R

3

R

R

B

R

3

1

3

R

19

T

R

2

10
11

4

REF

7

40 k

9

EA

PWM

power switch transistors are Darlington PNPs while the lower
switches are N–Channel power MOSFETs. Each of these
devices contains an internal parasitic catch diode that is used
to return the stator inductive energy back to the power supply .
The outputs are capable of driving a delta or wye connected
stator, and a grounded neutral wye if split supplies are used.
At any given rotor position, only one top and one bottom
power switch (of different totem poles) is enabled. This
configuration switches both ends of the stator winding from
supply to ground which causes the current flow to be
bidirectional or full wave. A leading edge spike is usually
present on the current waveform and can cause a
current–limit error. The spike can be eliminated by adding an
RC filter in series with the Current Sense Input. Using a low
inductance type resistor for RS will also aid in spike reduction.
Figure 35 shows the commutation waveforms over two
electrical cycles. The first cycle (0° to 360°) depicts motor
operation at full speed while the second cycle (360° to 720°)
shows a reduced speed with about 50% pulse width
modulation. The current waveforms reflect a constant torque
load and are shown synchronous to the commutation
frequency for clarity.

14

MOTOROLA ANALOG IC DEVICE DATA

MC33033

Figure 34. Three Phase, Six Step, Full Wave Motor Controller

V

M

FWR/REV

60°/120

Enable

V

M

Speed
Set

R

T

C

T

°

Faster

4

5

6

3

18

19
14

7

9

10
11

8

Reference

Regulator

Error Amp

Oscillator

PWM

Rotor

Position

Decoder

Undervoltage

Lockout

Thermal

Shutdown

R

Q

S

S

Q

R

I

Limit

2

1

20

17

16

15

12

Q

1

Q

2

N

S

A

S

N

B

Q

3

C

Motor

Q

4

Q

5

Q

6

R

C

R

S

MOTOROLA ANALOG IC DEVICE DATA

13

Gnd

15

MC33033

Figure 35. Three Phase, Six Step, Full Wave Commutation W aveforms

Rotor Electrical Position (Degrees)

Sensor Inputs

60°/120

Select Pin

Open

Sensor Inputs

60°/120

Select Pin
Grounded

Top Drive

Outputs

480420360300240180120600

S

A

S

B

°

S

C

Code

S

°

Code

100

A

S

B

S

C

100 110 001011 001011110100010 010 101101

A

T

B

T

100

00000101 1111110

011111110

720660600540

000001

Bottom Drive

Outputs

Conducting

Power Switch

Transistors

Motor Drive

Current

C

T

A

B

B

B

C

B

6

Q2 + Q

Q1 + Q

+

A

O
–
+
O

B

–
+

C

O
–

Q2 + Q4Q3 + Q4Q3 + Q5Q1 + Q5Q1 + Q

6

FWD/REV = 1

Q2 + Q6Q2 + Q4Q3 + Q4Q3 + Q

6

Reduced Speed (≈ 50% PWM)Full Speed (No PWM)

5

Q1 + Q

5

16

MOTOROLA ANALOG IC DEVICE DATA

MC33033

Figure 36 shows a three phase, three step, half wave motor
controller. This configuration is ideally suited for automobile
and other low voltage applications since there is only one
power switch voltage drop in series with a given stator

Figure 36. Three Phase, Three Step, Half Wave Motor Controller

4

5

Rotor

Position

Decoder

Lockout

Thermal

Shutdown

R
S

S
R

Q

Q

FWR/REV

60°/120

Enable

R

T

C

T

°

V

M

Speed
Set

Faster

6

3

18

19
14

7

9

10
11

8

Undervoltage

Reference

Regulator

Error Amp

PWM

Oscillator

winding. Current flow is unidirectional or half wave because
only one end of each winding is switched. The stator flyback
voltage is clamped by a single zener and three diodes.

Motor

2

N

SS

N

I

Limit

1

20

17

16

15

12

V

M

MOTOROLA ANALOG IC DEVICE DATA

13

Gnd

17

MC33033

Three Phase Closed Loop Controller

The MC33033, by itself, is capable of open loop motor
speed control. For closed loop speed control, the MC33033
requires an input voltage proportional to the motor speed.
Traditionally this has been accomplished by means of a
tachometer to generate the motor speed feedback voltage.
Figure 37 shows an application whereby an MC33039,
powered from the 6.25 V reference (Pin 7) of the MC33033,
is used to generate the required feedback voltage without
the need of a costly tachometer. The same Hall sensor
signals used by the MC33033 for rotor position decoding are
utilized by the MC33039. Every positive or negative going
transition of the Hall sensor signals on any of the sensor
lines causes the MC33039 to produce an output pulse of
defined amplitude and time duration, as determined by the
external resistor R1 and capacitor C1. The resulting output

Figure 37. Closed Loop Brushless DC Motor Control

With the MC33033 Using the MC33039

train of pulses present at Pin 5 of the MC33039 are
integrated by the Error Amplifier of the MC33033 configured
as an integrator, to produce a dc voltage level which is
proportional to the motor speed. This speed proportional
voltage establishes the PWM reference level at Pin 1 1 of the
MC33033 motor controller and completes or closes the
feedback loop. The MC33033 ouputs drive a TMOS power
MOSFET 3–phase bridge. High current can be expected
during conditions of start–up and when changing direction of
the motor.

The system shown in Figure 37 is designed for a motor
having 120/240 degrees Hall sensor electrical phasing. The
system can easily be modified to accommodate 60/300
degree Hall sensor electrical phasing by removing the
jumper (J1) at Pin 18 of the MC33033.

10 k

0.01

Speed

Faster

100 k

F/R

5.1 k

1
2
3

4

1
2
3
4
5

6
7
8

9

10

MC33039

MC33033

1.0 M

0.1

Close Loop

8

7
6
5

1.0 k

1.0 k

20
19
18
17
16
15
14
13
12
11

4.7 k

J

1

1.0 M
R

1

750 pF

C

1

TP1

Enable

1.1 k 1.1 k

1.0 k

1N5819

VM (18 to 30 V)

1.1 k

330

470
470
470

0.11N4742

0.1

0.1

33

1000

100

TP2

0.05/1.0 W

S

Motor

N

S

N

18

MOTOROLA ANALOG IC DEVICE DATA

MC33033

Sensor Phasing Comparison

There are four conventions used to establish the relative
phasing of the sensor signals in three phase motors. With six
step drive, an input signal change must occur every 60
electrical degrees, however, the relative signal phasing is
dependent upon the mechanical sensor placement. A
comparison of the conventions in electrical degrees is shown
in Figure 38. From the sensor phasing table (Figure 39), note
that the order of input codes for 60° phasing is the reverse of
300°. This means the MC33033, when the 60°/120
(Pin 18) and the FWD/REV (Pin 3) both in the high state
(open), is configured to operate a 60° sensor phasing motor
in the forward direction. Under the same conditions a 300°
sensor phasing motor would operate equally well but in the
reverse direction. One would simply have to reverse the
FWD/REV switch (FWD/REV closed) in order to cause the
300° motor to also operate in the same direction. The same
difference exists between the 120° and 240° conventions.

Figure 38. Sensor Phasing Comparison

Rotor Electrical Position (Degrees)

S

A

60°

S

B

S

C

S

A

120°

S

B

S

C

S

A

S

240°

Sensor Electrical Phasing

300°

B

S

C

S

A

S

B

S

C

Figure 39. Sensor Phasing T able

Sensor Electrical Phasing (Degrees)

60° 120° 240° 300°

SASBSCSASBSCSASBSCSASBS

1 0 0 1 0 1 1 1 0 1 1 1

1 1 0 1 0 0 1 0 0 1 1 0
1 1 1 1 1 0 1 0 1 1 0 0
0 1 1 0 1 0 0 0 1 0 0 0
0 0 1 0 1 1 0 1 1 0 0 1
0 0 0 0 0 1 0 1 0 0 1 1

° select

720660600540480420360300240180120600

C

In this data sheet, the rotor position has always been given
in electrical degrees since the mechanical position is a
function of the number of rotating magnetic poles. The
relationship between the electrical and mechanical position is:

#Rotor Poles

Electrical Degrees+Mechanical Degrees

ǒ

2

An increase in the number of magnetic poles causes more
electrical revolutions for a given mechanical revolution.
General purpose three phase motors typically contain a four
pole rotor which yields two electrical revolutions for one
mechanical.

Two and Four Phase Motor Commutation

The MC33033 configured for 60° sensor inputs is capable
of providing a four step output that can be used to drive two or
four phase motors. The truth table in Figure 40 shows that by
connecting sensor inputs SB and SC together, it is possible to
truncate the number of drive output states from six to four.
The output power switches are connected to BT, CT, BB, and
CB. Figure 41 shows a four phase, four step, full wave motor
control application. Power switch transistors Q1 through Q
are Darlington type, each with an internal parasitic catch
diode. With four step drive, only two rotor position sensors
spaced at 90 electrical degrees are required. The
commutation waveforms are shown in Figure 42.

Figure 43 shows a four phase, four step, half wave motor
controller. It has the same features as the circuit in Figure 36,
except for the deletion of speed adjust.

Figure 40. T wo and Four Phase, Four Step,

Commutation Truth Table

MC33033 (60°/120° Select Pin Open)

Inputs Outputs

Sensor Electrical

Spacing* = 90°

S

A

1
1
0
0

1
1
0
0

*With MC33033 sensor input SB connected to S

S

B

0
1
1
0

0
1
1
0

F/R B

Top Drives Bottom Drives

C

T

1
1
1
1

0
0
0
0

1
0
1
1

1
1
1
0

T

1
1
0
1

0
1
1
1

C

B

C

B

0
0
0
1

0
1
0
0

B

1
0
0
0

0
0
1
0

Ǔ

8

MOTOROLA ANALOG IC DEVICE DATA

19

MC33033

S

N

1

Q

N

S

A

B

C

Motor

D

5

Q

2

Q

M

V

3

Q

4

Q

6

Q

S

7

Q

8

Q

R

R

C

2

1

20

17

16

15

12

Limit

I

Figure 41. Four Phase, Four Step, Full Wave Controller

20

Rotor

Position

Decoder

Lockout

Undervoltage

Thermal

Shutdown

Q

S

R

Q

R

S

13 Gnd

PWM

Regulator

Reference

3

4

5

6

18

FWR/REV

19

Enable

14

V

M

7

Error Amp

9

10

11

T

R

Oscillator

8

C

T

MOTOROLA ANALOG IC DEVICE DATA

Sensor Inputs

60°/120

Select Pin

Open

Top Drive

Outputs

Bottom Drive

Outputs

Conducting

Power Switch

Transistors

MC33033

Figure 42. Four Phase, Four Step, Full Wave Commutation W aveforms

Rotor Electrical Position (Degrees)

180 270 360 450 540 630 720090

S

A

°

S

B

Code

B

T

C

B

B

C

T

B

Q3 + Q

5

Q4 + Q

Q1 + Q

6

Q2 + Q

7

Q3 + Q

8

Q4 + Q

5

Q1 + Q

6

0001111000011010

Q2 + Q

7

8

Motor Drive

Current

+

A

O

–
+

B

O

–

+

C

O

–
+

D

O

–

Full Speed (No PWM)

FWD/REV = 1

MOTOROLA ANALOG IC DEVICE DATA

21

MC33033

S

N

S

N

M

V

Motor

S

R

R

C

2

Figure 43. Four Phase, Four Step, Half Wave Motor Controller

4

Rotor

Position

1

Decoder

20

Lockout

Undervoltage

17

16

Thermal

R

Shutdown

15

12

Limit

I

Q

S

Q

R

S

13 Gnd

PWM

Regulator

Reference

3

5

6

18

FWR/REV

19

Enable

14

V

M

7

Error Amp

9

10

11

T

R

Oscillator

8

C

T

22

MOTOROLA ANALOG IC DEVICE DATA

MC33033

Brush Motor Control

Though the MC33033 was designed to control brushless
dc motors, it may also be used to control dc brush–type
motors. Figure 44 shows an application of the MC33033
driving a H–bridge affording minimal parts count to operate a
brush–type motor. Key to the operation is the input sensor
code [100] which produces a top–left (Q1) and a bottom–right
(Q3) drive when the controller’s Forward/Reverse pin is at
logic [1]; top–right (Q4), bottom–left (Q2) drive is realized
when the Forward/Reverse pin is at logic [0]. This code
supports the requirements necessary for H–bridge drive
accomplishing both direction and speed control.

The controller functions in a normal manner with a pulse
width modulated frequency of approximately 25 kHz. Motor
speed is controlled by adjusting the voltage presented to the
noninverting input of the Error Amplifier establishing the
PWM′s slice or reference level. Cycle–by–cycle current
limiting of the motor current is accomplished by sensing the
voltage (100 mV threshold) across the RS resistor to ground
of the H–bridge motor current. The over current sense circuit
makes it possible to reverse the direction of the motor, on the

Figure 44. H–Bridge Brush–T ype Controller

fly, using the normal Forward/Reverse switch, and not have to
completely stop before reversing.

LAYOUT CONSIDERATIONS

Do not attempt to construct any of the motor control

circuits on wire–wrap or plug–in prototype boards. High

frequency printed circuit layout techniques are imperative to
prevent pulse jitter. This is usually caused by excessive noise
pick–up imposed on the current sense or error amp inputs.
The printed circuit layout should contain a ground plane with
low current signal and high drive and output buffer grounds
returning on separate paths back to the power supply input
filter capacitor VM. Ceramic bypass capacitors (0.01 µF)
connected close to the integrated circuit at VCC, V
error ampliflier noninverting input may be required depending
upon circuit layout. This provides a low impedance path for
filtering any high frequency noise. All high current loops
should be kept as short as possible using heavy copper runs
to minimize radiated EMI.

ref

and

FWR/REV

Enable

+12 V

10 k

10 k

0.005

0.1

Faster

4

5

6

3

18

19
14

7

9

10

11

8

Reference

Regulator

Error Amp

Oscillator

PWM

Rotor

Position

Decoder

Undervoltage

Lockout

Thermal

Shutdown

R

Q

S

S

Q

R

I

Limit

2

1

20

17

16

15

12

0.001

DC Brush

Motor

22

1.0 k

1.0 k

Q1*

Q2*

22

M

1.0 k

+12 V

Q4*

Q3*

R

S

MOTOROLA ANALOG IC DEVICE DATA

13

Gnd

23

OUTLINE DIMENSIONS

–A–

1120

110

–T–

SEATING
PLANE

E

GF

D

–A–

1120

–B–

110

20 PL

D

0.010 (0.25) T A B

M

S S

C

G 18 PL

K

B

N

20 PL

0.25 (0.010) T A

P 10 PL

0.010 (0.25)

–T–

SEATING
PLANE

MC33033

P SUFFIX

PLASTIC PACKAGE

CASE 738–03

ISSUE E

C

K

M M

DW SUFFIX

PLASTIC PACKAGE

CASE 751D–04

(SO–20L)

ISSUE E

M M

B

J

F

M

L

J 20 PL

0.25 (0.010) T B

R X 45°

M

M M

NOTES:

1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.

2. CONTROLLING DIMENSION: INCH.

3. DIMENSION L TO CENTER OF LEAD WHEN
FORMED PARALLEL.

4. DIMENSION B DOES NOT INCLUDE MOLD
FLASH.

INCHES MILLIMETERS

MIN MINMAX MAX

DIM

A
B
C
D
E
F

G

J
K
L

M

N

NOTES:

1. DIMENSIONING AND TOLERANCING PER
ANSI Y14.5M, 1982.

2. CONTROLLING DIMENSION: MILLIMETER.

3. DIMENSIONS A AND B DO NOT INCLUDE
MOLD PROTRUSION.

4. MAXIMUM MOLD PROTRUSION 0.150
(0.006) PER SIDE.

5. DIMENSION D DOES NOT INCLUDE
DAMBAR PROTRUSION. ALLOWABLE
DAMBAR PROTRUSION SHALL BE 0.13
(0.005) TOTAL IN EXCESS OF D DIMENSION
AT MAXIMUM MATERIAL CONDITION.

DIM

A
B
C
D

F

G

J
K
M
P
R

1.070

1.010

0.240

0.150

0.015

0.050 BSC

0.050

0.100 BSC

0.008

0.110

0.300 BSC

°

0

0.020

MILLIMETERS INCHES

MIN MINMAX MAX

12.65

7.40

2.35

0.35

0.50

1.27 BSC 0.050 BSC

0.25

0.10
0

°

10.05

0.25

0.260

0.180

0.022

0.070

0.015

0.140

0.040

12.95

7.60

2.65

0.49

0.90

0.32

0.25
7

10.55

0.75

15°

°

25.66

6.10

3.81

0.39

1.27 BSC

1.27

2.54 BSC

0.21

2.80

7.62 BSC

°

0

0.51

0.499

0.510

0.292

0.299

0.093

0.104

0.014

0.019

0.020

0.035

0.010

0.012

0.004

0.009

0

°

0.395

0.010

0.415

0.029

27.17

6.60

4.57

0.55

1.77

0.38

3.55
15

1.01

7

°

°

Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty , representation or guarantee regarding
the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and
specifically disclaims any and all liability, including without limitation consequential or incidental damages. “T ypical” parameters which may be provided in Motorola
data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals”
must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights of
others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other
applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury
or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola
and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees
arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that
Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal
Opportunity/Affirmative Action Employer.

How to reach us:

USA/EUROPE/Locations Not Listed: Motorola Literature Distribution; JAPAN: Nippon Motorola Ltd.; Tatsumi–SPD–JLDC, 6F Seibu–Butsuryu–Center,

P.O. Box 20912; Phoenix, Arizona 85036. 1–800–441–2447 or 602–303–5454 3–14–2 Tatsumi Koto–Ku, Tokyo 135, Japan. 03–81–3521–8315

MFAX: RMF [e-mail] – TOUCHT ONE 602–244–6609 ASIA/ PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park,

INTERNET: http://Design–NET.com 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852–26629298

24

◊

MOTOROLA ANALOG IC DEVICE DATA

MC33033/D

*MC33033/D*