1 Front panel. __-___---___-_____-___________________ 1
2 Front pane1 Controls. ________--______-____________ 3
3 Rear Panel Controls. - 3
4 shunt Method Measurement, -----------------__------ 4
5 Effect of Shunt capacitance. ---------------------- 4
6 Compensation for Shunt Capacitance. --------------- 5
6b Extended Frequency Response. ---------------------- 5
7 Fee&a& Method. _--__-_-__________-_______________ 6
8 Input Voltage N&se. -------------___-------------- 6
9 Bandwidrh of Feedback System. --------------------- 7
9b Effect of filter on Noise spectrum. -------------- 7
9, Effect of Input Capacitance on Noise. ------------- 7
10 Frequency Compensafian. ---------_____--_-__------- 7
11 Plot of Noise-Improvement Contours.
12 Block Diagram of a High-Speed Current Amplifier, -- 12
RANGE: 10’ to 10” volts/ampere in eight decade ranges.
(10-13 ampere resolution to 10.” ampere full output).
OUTPUT: *10 volts at up to 3 milliamperes.
OUTPUT RESISTANCE: Less than 10 ohms dc to 30 kHz.
OUTPUT ACCURACY: 12% of reading to the lo9 vattsl
ampere range, +4% of reading on the 1O’O and 10”
volts/ampere ranges exclusive of noise. drift and current
offset.
RISE TIME (10% to 90%): Adjustable in lx and 3.3x steps
from “Fast Rise Time” listed below to 330 rnsec.
NOISE VS. RISE TIME’:
I
FAST RISE TlML
MODEL 427
STABILITY: Current offset doubles per 10°C above 25°C.
Voltage drift is less than 0.005% per “C and less than
0.005% ,,er da” of full outDut after l.hour warmur,.
OFFSET CURRENT: Less than lQLz am&e at 25”C’and up
CURRENT SUPPRESSION: lo-lo ampere to 10-a ampere in
OVERLOAD INDICATION: Lamp indicates pre-filter or post.
CONNECTORS: Input: (Front) ENC. Output: (Front and
DIMENSIONS; WEIGHT: Style M 3%” half.rack, overall bench
,-
to 7001, relative humidity.
eight decade ranges with 0.1% resolution (lO.turn poten.
tiometer). Stability is +O.Zo/. of suppressed value per “C
bO.Z% per day.
INPUT VOLTAGE DROP: Less than 400 /.IV for fullaxle
output on the 10” to 10” volts/ampere ranges when
properly zeroed.
EFFECTIVE INPUT RESISTANCE: Less than 15 ohms on the
10” and 105 volts/ampere ranges. increasing to less than
4 megohms on the 10” volts/ampere range.
MAXIMUM INPUT OVERLOAD: Transient: 1000 volts on any
range for up to 3 seconds using a Keithley (or other 10
mA-limited) highaoltags supply. Continuous: 500 volts
on the 10” to 1O’voltsjampere ranges, decreasing to ‘ZOO
an the 10”. 70 on the lo5 and 20 volts on the 10’ volts,
ampere ranges.
filter overload.
DYNAMIC RESERVE: 10 (20 dB).
Rear) BNC.
POWER: 90.125 or 180.250volts (switch selected), 50.60 Hr.
l-1. GENERAL; The Model 427 Current Amplifier is a
high-speed, feedback-type amplifier with particular
features useful for automated semiconductor testing,
mass spectrometry, and gas chromatography applications.
l-2. FEATURES.
a. Wide Dynamic Range. Selectable rise times permit
low-noise operation important when resolving small
current levels.
b. High Speed.
out of a 10sSZpere signal with a 100 microsecond
rise time.
Typical resolution is 20 picoamperes
GENERAL DESCRIPTION
C. Built-in Current Suppression.
the signal level can be measured since large ambient
current levels can be easily suppressed.
d. Overload Indication.
assured since overloads are automatically indicated.
e. Variable Cain. The GAIN Switch is designated
in eight gain positions from lo4 to 1011 volts per
ampere - therefore gain adjustment is straight forward.
f. Variable Kise Time. Optimum response can be
selected for each gain setting since a separate RISE
TIME switch is provided on the front panel.
Small changes in
Accurate measurements are
0471
1
GENERAL DESCRIPTION
MODEL 427
TABLE 1-l.
Front Panel Controls and Terminals
PUSH Power Switch (S302)
GAIN Switch (5201)
RISE TIME (5101)
SUPPRESSION
MAX AMPERES Switch (S303)
FINE Control (R333)
POLARITY Switch (5304)
ZERO ADJ Control (R235)
INPUT
Receptacle
OUTPUT Receptacle (5102)
~ OVERLOAD Indicator (DS302)
(5202)
Functional Description
Controls power to instrument.
sets gain in Volts per ampere.
Sets
rise time Fn milliseconds.
Sets maximum suppression.
Adjusts suppression.
Sets polarity of suppression.
Adjusts output zero.
Input source connection.
Output connectFon.
Indicates overload condition.
Rear Panel Controls and Terminals
TABLE 1-2.
Paragraph
2-4, al
2-4, a2
2-4, a3
2-4, a4
2-4, a5
2-4, a6
2-4, a7
2-3, a
2-3, b
2-5, d
Control or Terminal Functional Description Paragraph
Line Switch (5301)
Power Receptacle
Fuse (F301)
0lJTPuT Receptacle
(P305)
(5103) Output connection.
Sets instrument for 117V or 23411.
Connection to line power.
Type 3AG Slow-Blow, 117V @ l/4 A (w-17)
234V @ l/S A (w-20)
WARNING
Using a Line Power Cord other than the one supplied
with your instrument may result in an electrical
shock hazard. If the Line Power cord is lost or
damaged,
replace only with Keithley Part No. CO-7.
2-4, b
2-3, c
2-3, b
0878
MODEL 427
GAIN
SWITC
S20
,----SUPPRESSION-,
FINE
ADJUST
GENERAL DESCRIPTION
POLARITY
SWITCH
INPUT
5202
ZERO ADJ
R235
FIG"RF 2.
OVERIDAD Power
.
DS302 S302
want Panel Controls.
P
OUTFW
5102
I
0471
FIGURE 3.
Rear Panel Controls.
OPERATION
MODEL 427
SECTION 2.
MEASUREMENT CONSIDERATIONS.
2-1.
a. Current-Detection Devices.
‘small electrical c~rrent8 has been the basis for a
number of instrumental methods used by the analyst.
Ion chambers, high-impedance electrodes, many forms
of ch=“metog=aphic detectors, phototubes and multipliers are coaronly-used t=ansduce=a which eequire the
measurement of small currents. Devices used for this
measurement a=e often called electraaeters.
b.. In any measure-
ment, if e”“=ce noise greatly exceeds that added by
the inst=“mentatian, optimization of instrumenteti””
is unimportant.
ical minimum, optimization of instrumentation charac-
teristics becomes imperative. TO determine the category into which this meas”=ement falls. the researcher
needs t” be familiar with the characteristics which
impoee theoretical and practical limitations on his
me*surement .
theoretical limitations present in voltage measueements
The noise inceeases with 8”“=ce realstance, and the
familiar equation for the mean-square noise voltage is
q = 4kTRAf Eq. 1
When source noise approaches theoret-
Most researchers a=e familiar with the
The DleasUrement of
OPERATION
Prom this equation it is irmnediately apparent that the
m%QB”rement of emall current =equi=es large values of
R, i.e., high impedance levels. Howwee, thfe gives
difficulties for meas”=ements requiring wide bandwidths
because of the RC time constant associated with a
high-megohm resistor and even a few picofarads of cir-
cuit capacitance.
generating a voltage across a parallel RC. The frequency response of this current measurement is limited
by the RC time constant.
end the -3 dB p”int “CC”=B at a frequency
Lor* noise and high
requirements.
techniques must be used which obtain high speed “sing
high-impedance devices.
C. Hiah Speed Methods.
1. High epeed can, af c”“=se, be obtained in .
shunt-type meae”=eme”t by “sing a low value for the
shunt resist”=.
resistor value int=ad”ces excessive noise into the
meQ8”rement.
Figure 4
speed,
TO optimize a current-measuring system,
As pointed ““t above, such a srmll
shows a c”==ent s”“=ce
Figure 5
therefore, a=e contradictory
shows this response
whe=e k is the Boltzma”” Constant, T ia the absolute
temperature of the s”“=ce resistance R, and
noise bendwidth( 3
single RC rolloff.) In the case of cureent measure-
ments it Is more appropriate to consider the noise
current generated by the ~l”“=ce and load resistances.
The mean squaee noise c”==ent generated by a resistor
is given by Eq. 2.
FIGURE 4.
In the shunt method c”=re”t is measured by
the voltage drop ac=“ee a resistor.
times the 3 dB bandwidth for a
Af
is the
2. A second method to achieve bandwidth is to
keep R large, to accept the frequency roll-off
starting at F”, and t” change the frequency eesponae
of the voltage amplifier a8 ehown in Figure 6a. The
combined effects of the RC time c”“sta”c folloved
by this amplifier is shown in Pigure 6b and it is
seen that the frequency response of the c”==ent
measurement has been extended to Pl. The frequency
at which the amplifier gain sta=‘ts to increase must
be exactly equal t” the frequency F” determined by
the RC time c”nstant in order for this approach t”
result in a flat frequency respanse. Therefore,
FO
FIGURE 5. The frequency respanse of the shunt method
1s limited by omnipresent ahunt capacitance.
LOG FREQUENCY
I
0471
MODEL 427
OPERATION
this oethad is ueeful only far application* where
the shunt capacitance C is constant. Aaide from
thin drawback this is * 1eSitimste approach which
is being wed in low-noise, high-speed current-
meesuring applicatians. In addition to current noise
in the *hunt and in the amplifier input stage, B
maJor source of noise in this system *ri*** from
the voltage-noise generator ssaociated with thb input atage (reflected a* current noise in the shunt
resistor) caused by the high-frequency peeking in
the following stages of amplification. More will be
said about this in the discussion on noise behavior.
3. A third method used for speeding up * current
measurement asas guarding techniques to eliminate
the effects of capacit*nces. Unfortunately only
certain type* of capacitance*, such ** cable cap=-
itances, can be conveniently eliminated in this
manner.
itences associated with the *ource itself became*
very cumbersome and m*y not be feasible in many in-
stsnces.
*re identical to those mentioned in the second
system.
4. A fourth circuit configuration combines the
capability of low-noise and high-speed performance
with tolerance for varying input C and eliminate*
need for separate guard by making the ground plane
*n effective guard. This is the current-feedback
technique.
ment of 3 over shunt technique*. Again, the major
sources of noise are identical to those mentioned
in the second system.
d. Noise in Current Measurements. Noise forms *
b*aic limitation in *nv hinh-speed current-measurinn
system. The shunt *y&m give; the simplest curren;
measurement but does not give low-noise performance.
A properly designed feedback *y*tem gives superior
noise - bandwidth performance. Noise in these two
systems will be discussed next.
1. Noise Behavior of the Shunt System. High
speed end low noise *r* contradictory requirements
in any current meesurement because *orw capacitance
is always present. The theoretical performance
limftetion of the shunt *yetem c*n be calculated **
To eli,r,inate the effect of parasitic c*p*c-
The major *ourc** of noise in this *“*tern
This technique gives * typical improve-
The rms thermal noise current (in) generated by *
resistance R is given by
Eq. 4
The equivalent noise bandwidth (.f) of * parallel SC
combination is Af = 1/(4RC) snd the eignal handwidth (3 dB bandwidth) F, = 1/(2nRC). For practical
purposes peak-to-peak noise is taken 88 5 times the
ml* value. The peak-to-peak noise current can now
be written a*
i
UPP =
In practice, e typical value for shunt cape.cit*nce
is 100 picofarads.
rule-of-thumb is obtained. The lowest ratio of
detectable current divided by signal bandwidth using
*hunt-techniques is 2-10-14 ampere/Hertz for B peakto-peak signal-to-noise ratio equal to 1. A coroll-
ary far this rule-of-thumb expresses the noise cur-
rent in term* of obtainable risetime (lo-SO% risetime tr = 2.2 RC). The lowest product of detectable
current and risetime using shunt technique* is 7 x
lo-l5 ampere seconds.
assumed that the voltage amplifier does not contribute noise to the measurement.
2. Noise Behavior of the Feedback System. There
are three *ource* of noise in the feedback system
that have to be looked at closely. The firat two,
input-stage shot noise and current noise from the
mea*urinS resistor, are rather straight-forward. The
third, voltage noise from the input device of the
amplifier, cau*e* *ome peculiar difficulties in the
measurement. Any resistor connected to the input
injects white current noise (Eq. 4). In the circuit
of Figure 7 the only resistor that is connected to
the input is the feedback resistor R. As in the
shunt system, R must be made large for lowest noi*e.
Beceuse this noise is white, the total contribution
can be calculated by equ.,ting Af to the equivalent
noise bandwidth of the system. The second *ource of
noise is the current noise from the amplifier input.
This component is essentially the shot noise asaociared with the gate leakage current (io) of the input
device. Its rms value equals . . .
2 x 10-9 F,
With this value the following
F
In this derivation it has been
Eq. 5
FIGURE 6.
0471
LOG FREWENCY
FO
ny tailoring the frequency response of the
amplifier (Pig. 6a) the frequency response
of the shunt method c*n be extended.
F>
FIGURE 6b.
FO
Extended frequency response.
LOG FREQUENCY
F,
OPERATION
MODEL 427
T;; = J-zTp-
where e is the electronic charge. The contribution
of this noise generator is also white. N*t only do
these two noise sources generate white current noise,
the noise in a given bandwidth is also independent
of the input capecitence C. The mejor source of
noise in e feedback current meesurement is the noise
contribution aseocisted with the voltage noise of
the input amplifier. The voltage noise ten be rep-
resented by a VOltage noise generator (0,) et the
emplifier input es shown in Figure 8. This wise
generator itself is assumed to be white. However,
its total noise contribution to the current-measuring
system is not white.
reveal that et low frequencies P large em*u*t of feedbeck ie applied around the voltage noise source {en).
However, the SC combination ettenuetes the high-
frequency components of V,,t so that no feedback is
present et high frequencies. Thus, the noise con-
tribution to the output voltage V,,t from the valtage noise source a* is no longer independent of
frequency. The noise is “colored” and increases in
intensity for ell frequencies higher than F,. The
resulting noise spectrum is shown in Figure 9b. The
tote1 system noise is related to the are* under
this curve.
plotted on the horizontal axis, the eree under the
curve et higher frequencies represents e significantly larger amount of noise then e similar eree
*t low frequencies.
the frequency response of the current measuring
system.
interesting et this point to compare this noise
spectrum with the frequency response of the voltage
amplifier in Figure 4 es shown in Figure 6a. A voltage noise eouec.e et the input of the amplifier would
generate a noise spectrum according to the amplifier
frequency response as shown in Figure 6a. The noise
spectrum of such e system, then, is identical to the
noise spectrum of the feedback system as given in
Figure 9h.
that signal-to-noise performance of a measurement
cen**t be improved by feedback techniques. At the
high-frequency end the voltege noise is limited by
the frequency FA which is the high-frequency roll-
off point of the operational amplifier. It should
Because the logarithm of frequency is
Figure 9e ia identical to Figure 6b. It is
This illustrates the well-known fact
Inspection of Figure 6 will
For comparison, Figure 9a show
he noted that even though the useful bandwidth of
the system extends only t* Fl, there era noise com-
ponents of higher frequency present. To obtain
best widebend-noise performance, these high-frequency
noise components have to be removed. This ca* be
achieved by adding a low-pass filter section follow-
ing the feedback input stage. If the band-pass of
thin low-pass filter is made adjuetable this filter
can nerve the dual purpose of removing high-frequency
noise end of limiting the signal bandwidth of the
system.
2-2. THEORY OF OPERATION.
8. Current Feedback Technique. The basic circuit
configuration used in the current-feedback technique
is shown in Figure 7.
current-measuring resistor R is placed in the feedback
loop of e* inverting emplifier with a gain of A*. The
frequency response obtained with this circuit is identical to thet s+nvn in Figure 6b. F* agein is the
frequency associated with the RC time constant:
F, =
The frequency response of the syetem is extended t* a
frequency fl where
F
, = AoF,
Note that the frequency rerponse is automatically flat
without heving to match break points. However, the
total bandwidth of the system (Fl) is still limited
by the value of the ahunt capacitance C across the
input.
back technique avoids the use of low values for R
which could generate exceesive current noise.
difficulty of the feedback system ariees from shunt
capacitence esaociated with the high-megohm resiaeor R
in the feedheck path.
the resistor is CFr then the bandwidth (FF) of the
system is determined by the time COnstent RCF:
This improved frequency response of the feed-
b. Refinements of the Feedback System. A major
In this configuration the
SE Eq. 6
Eq. 7
.
If the shunt cepacitence acroes
FIGURE 7.
6
Beslc circuit configuration for the feedback method.
FIGURE 8.
The voltage noise associeted with the amplifier input device is en important eourc~
of noise in the high-speed feedback syatew
0471
MODEL 427 OPERATION
FIGURE 9.
FIGURE 9b.
The bendwidth of the high-speed feedback
system (Fig. 9a) ten he limited by using
e filter with either e -6 dB/actave or a
-12 dB/octave roll-off. The effect of the
filter on the noise spectrum is showwin
Fig. 9h.
Effect of input capacitance on
noise is shown in Fig..9c.
Effect of filter on noise spectrum.
FIGURE 10.
Frequency compensation.
FF = 1
2 nllcp
Eq.
A slight modification of the feedback loop can correct
this problem es shown in Figure 10. If the time constant RlCl is made equal to the time constent R.CF,
it CB* be shown that the circuit within the dotted
line behaves exactly es a resistance R. The matching
of time constants in this cese does not become e drawbeck because the copscitances involved era all constant
and not effected by input impedance.
C. -12 dB/actave Filter.
1. Theory. To obtain optimum widehand noise per-
fomence e filter with e single high-frequency rolloff (i.e.,
dB/octeve is required.
-6 dB/octave) is not sufficient end -12
The effect of e -6 dB filter
is shown in Figure 9a end h. The filter is used to
limit the system bandwidth to a frequency F2, smaller
then Fl. The effect af this filter on the noise
spectrum is shown in Figure 9b. It ten be seen that
there ace egain high-frequency noise components above
F2, the useable bandwidth of the system. These can
he eliminated by using e filter with e -12 dB/octave
roll-off. The result of such .a filter on noise per-
formance is also shown in Figure 9b.
FIGURE 9c.
0471
Effect of input capacitance on noise.
2. Model 427. The input smplifier 18 followed by
en adjustable low-pass filter having e -12 dB/octeve
roll-off end a valtage gain of 10X. The voltage
gain in the low-pass filter avoids premature over-
loading in the input amplifier which ten be seen es
fallows. The maximum output voltage V,,t is $10
volts.
The maximum signal level et the input of the
low-pass filter is, therefore, +l volt. At this
point in the circuit, wide-band noise could still be
present end exceed the l-Volt signal level. The
voltege gain of 10 in the filter allows the total
pre-filter wide-hand noise to exceed the full scale
signal by e factor of 10 (20 dB). The frequency re-
sponse of this filter is edjustahle for variable
“damping” control.
7
OPERATION
2-3.
CONNECTIONS,
MODEL 427
2-5. OPERATING CONSIDERATIONS.
8.
Input.
type which metes with coaxial cables such es Keithley
Models 8201 end 8202.
high.
(5102 on the front, 5103 on the reer panel). These
era BNC type* where the inner contact is output high
end the outer shell is chassis ground.
rear panel is a 3-prong connector which metes with
Keithley pare number CO-6 line cord.
2-4. CONTROLS.
The outer shell is low or chassis ground.
b. Output.
C.
Power Input. The power receptacle (P305) on the
a. Front Panel.
1. Power Switch “PUSH ON” (5302). This switch
controls the line power to the instrument. ‘The
switch is a special pushbutton type with “Power On”
indicated by a self-contsined pilot lamp.
2. GAIN (VOLTS PER AMPERE) (S201). This switch
sets the overall gain in eight positions from 104
to loll.
ment of zero offsets.
3. RISE TIME Switch (5101). This switch sets
the lo-90% rise time in 10 positions from .Ol to
300 milliseconds(for the filter section only).
4. SUPPRESSION (MAX) Switch (S303). This switch
sets the maximum current suppression in eight pasitions from lo-10 to 10-3 A. When the switch
to “OFF” the current suppression circuit is disabled.
5. SUPPRESSION (FINE) control (~333). This con-
trol permits adjustment of suppression with 0.1%
resolution.
6. SUPPRESSION (POLARITY) Switch (S304). This
switch set* the polarity of the current suppression
(referred to the input).
7. ZERO ADJUST Control (R235). This control per-
mits adjustment of zero offset through the u*e of the
OVERLOAD indicator.
b. Rear Panel.
1. Line Voltage Switch (S301). Sets instrument
for either 117 or 234 V operation.
The input receptacle (5202) is e SNC
The inner contact is circuit
Two outp,ut receptacles *re provided
A “ZERO CHECK” position permits adjust-
Fuse RequirP.ment* 3AG, Sla-Slo
117V: 1/4A
234V: l/SA
Keithley No. F”17
Keithley No. F”-20
is
set
8. Gain. The gein of the Model 427 is defined in
terms of volts per *“pare. Since the output level is
10 volts for e full scale input, the gain could also
be expressed e* sensitivity in emperes referred to the
input BS in Table 2-1. Vout = - (Iin x GAIN)
Gain or Sensitivity Referred to the Input
GAIN
Setting Resistor
b. Rise Time. The rise time for each gain setting
is listed in the specifications a* “FAST RISE TIME”.
These rise times are obtained when the RISE TIME
switch is set to the positions indicated in Table 2-2.
GAIN
Setti”g
104
105
106
107
1 10;
1oy
1010
loll
c. Suppressian. Current suppression is provided in
the Model 427 for suppression of input currents up to
10e3 amperes.
variations in e larger signal can be observed. Currents
of either polarity can be suppressed. To suppress an
input current the SUPPRESSION should be *et to supply
e current of apposite polarity. The FINE control permits
adjustment up to 1.5 times the MAX setting.
d. Overloads,
en overload et two places in the circuit: before end
after the “RISE TIME” filter circuit. The OVERmAD
lamp (DS302) will indicate whenever the voltsge sensed
ia greater then full scale regardless of the RISE TIME
setting or the frequency.
a. Zero Adjust. The ZERO CHECK po*ition grounds the
the input of the instrument and co”“ert* the cuerent
amplifier to a high-gain voltage amplifier. The ampli-
fied offset voltage will turn on the OVERLOAD indicator
whenever the input voltage offset exceeds 5100 t0l.
Therefore the ZERO control should be adjusted so that
the OVERLOAD indicator is off when in ZERO CHECK mode,
yielding the specified input voltage drop.
Feedback
Switch Settings for “FAST RISE TIME”
Rise
Time
15 ps
15 us
15 I*8
40 us
60 ps .03 ms 800
220
400
1.5 1 ms 100
TABLE 2-l.
Full Scale
sensitivity Output
(Amperes)
103
104
105
106
107
108
109
1010
&Is
“S ps
By suppressing background currents, smell
The overload sensing circuit detects
1
x 10-3
1 x 10-4
1 x 10-5
I x 10-6
1 x 10‘7
1 x 10-g
1
x 10-9
1 x 10-10
TABLE 2-2.
RISE TIME
Setti”g*
.Ol “S
.Ol ms
.Ol “S
.03 “9
.l “S 400
.3 ms 200
Eq. 9
Full Scale
(Volts)
10
10
10
10
10
10
10
10
DYlWl”iC
Range
2000
2000
2000
2000
J
8
MODEL 427
APPLIChTIONS
SECTION 3. APPLICATIONS
3-1. CURRENT~MEASURING SYSTEM. The typical current
meaeuring system consists of a current source, a current amplifier, and a monitoring device, The current
source could include an ion chamber, photomultiplier,
or other high-impedance device,
such as the Model 427 provides sufficient gain to drive
a monitoring device such as a chart recorder or other
readout. The Model 427 in this case provides an output voltage which is calibrated in volts per ampere
a.3 in equation 10.
- (V,,t I GAIN)
Example :
3-2.
trates the trade-off between fast rise time and dynamic
range.
a.s the ratio of maximum peak-to-peak current to peakto-peak current noise.
taken as 5-times the rms current noise. The maximum
peak-to-peak current is 2-times the maximum full scale
current.
When using current suppression the current-suppres-
sion resistor should be considered as an additional
current-noise generator. The values given in Table
3-l do not include the contribution of the suppression resistor. Therefore the selected suppression
resistor Rs, should be as large as possible to min-
imize the contribution to current noise.
Iin =
GAIN = 106 voltslampe~e
” O”t = +500 In”
The input current Iin would be:
lin = - (5x10-~vo1ts/106vo1ts per ampere)
Iin = - 5 x 10-7
NOISE BANDWIDTH CONSIDERATIONS.
For this application dynamic range is defined
Peak-to-peak current noise is
NOTE
The current amplifier
Eq. 10
amperes
Table 3-l illus-
3-3. NOISE-IMPROVEMENT CONTOURS. The sensitivity
and speed of the Model 427 (for either d-c or a-c
measurements) can be compared to the best perfarm-
ante obtainable with the shunt method of measuring
current. The best “noise-risetime” product that
can be achieved for d-c measurements (with 100 pF
shunt capacitance) in a shunt system is 7 x lo-15
ampere-seconds.
2 x lo-l5 ampere-seconds (also with 100 pF shunt
capacitance).
(lock-in, etc.) the-degree of improvement is a func-
tion of shunt capacitance and operating frequency.
The achieveable imprownene over the shunt method
can be plotted in a graph similar to a set of noise
contours. Figure 11 shows the measured impravemene
(negative dB) that can be obtained with the Model
427 at a given frequency and shunt capacitance when
compared to an ideal (noiseless) amplifier Fn a shunt
system.
,
I
FIGURE 11. Plot of noise-improvement contours.
However the feedback system achieves
When used in a-c narrowband systems
FREOUENCY IHI1
RMS’Noise Current (Typical)1 as a Function of Gain and Rise-Time Setting
TABLE 3-l.
,vL.. I,.,“,.,
PULL SCALE
GAIN
VIA
104
105
106
107
108
109
1010
1011
1
With up to 100 pP input shunt capacitance.
KEY :
x = Filter Bandwidth is greater than current-amplifier bandwidth.
* = larger Rise Times are useful for increased filtering of the signal arid noise inherent in the source.
0471
CURRENT
AMPERES 300 100 30
10-3
10-4
10-5
m-6
10-7
104’
10-9
lo-1o *
They do not further improve the instrument noise contribution except when the input shunt capacitance
exceeds 100 DF.
* * * *
*
* * *
:
*
2x10-15 4x10-15 1x10-14 4x10-14 1x10-13 4x10-13 x
*
* *
*
1x1:-14
*
*
*x1:-14
Noise increases aa input shunt capacitance increases.
RISE TIME SETTING
10 3 1 .3
*
* * *
* *
* *
*
2do-13 2d0-13 5do-13 2~0-12 5x10-12 x x
5~0-14 2do-13 ~0-13 2do-12 x
MO-12 2x10-l2 5x10-12 1x10-11
lx&
*
1x10-8
1x10-9 1.2x10-9 4x10-9
1x10-10
1.5x10-11
.l .03 .Ol
1.2x10-8 4x10-8 1x10-7
1.2x10-10 4x10-10 1x10-9
2x10-11 1x10-10 x
4x10-11
x
x x
x x
1x10-B
x
9
ACCESSORIES
MODEL 427
SECTION 4.
4-l. GENERAL.
be used with the Model 427 eo provide additional convenience and versatility.
Description:
The Model 1007 is a dual rack mounting kit with over-
all dimensions 3-l/2 in. (64 mm) high and 19 in. (483
mm) wide.
of two Angle Brackets, one Mounting Clamp, and extra
mounting BCreWS.
The following Keithley accesaaries can
Model 1007 Rack Mounring hit
The hardware included in this kit consists
ACCESSORIES
OPERATING INSTRUCTIONS. A separate Instruction
4-2.
Manual is supplied with each accessory giving complete
operating information.
Application:
The Model 1007 co""erts any half-rack, style "M"
instrument from bench mounting to rack mounting in
a standard 19-inch rack.
for rack mounting 19-inch full rack width insfru-
ltE"tS.
The Model 1007 Rack Mounting Kit can be used to m"u"t
instruments of 11 inch or 14 inch depth.
should decide the position af the i"~tr"me"ts to be
rack mounted.
instruments positioned as shown and identified as
instrument “A” and "B".
The Assembly Inaeructions refer co
The kit may also be used
The user
10
Parts List:
Item
NO.
DWCl+ltiO”
22 Angle Bracket
23 Screw, 16-32 x
Phillips Pa" Hd
24 Mounting Clamp
25 Screw, %6-32 x
Phillips Pa" Hd
26 Kep Nut 116-32
27 Screw, 116-32 X
Phillips Pa" Hd
28 Screw, 116-32 x
Phillips Pa" Hd
5/8,
1,
l/2,
718,
VY
Keq'd
2
6
1 247988
1
3
2
1
Keithley
Part No.
27410B
-_
__
_-
__
__
0877
MODEL 427
Assembly Instructions:
ACCESSORIES
Model 1007 Dual Rack MountinS Kit
1. Before assembling the rack kit, determine the
pasition of each instrwnent. Since the inserumenfs
can be mounted in either location, their position
should be determined by the user’s meas”rement. The
following instructions refer to instruments “n” and
UB”
positio”ed as shorvn. For mounfinS 19-inch full
rack Width instruments, disregard steps 2 through 5.
2. Once the position of each instrument has been
determined, ebe “side dress” panels on both sides of
each instrument should be removed. Renxwal is
accomplished by looseninS the screwy (Item 8, oriSinal hardware) in two places. Slide the “side dress”
panels co the rear of the instrument to remove.
3. The mountinS clamp is installed on instrument
“A” using the oriSina1 hardware (Item 8). With the
screws removed, insert the “mounting clamp” behind
the “corner bracket” (Item 7) and replace the screws
to hold the mounting clamp in place.
4. Tighten the screwy (Item 8) on instrument “B”.
Insert the “mounting clamp” behind the “corner
bracket” (Item 7) an instrument “8” a8 shown.
5. When mounting instruments having the same depth,
a screw (Item 25) and kep nut (Item 26) are required
to secure the two instruments together. When ,,,ouneing instruments of different depth, da not use kep
nut (Item 26) but substitute shorter screw (Item 28).
6. Attach an “anSle bracket” (Item 22) on each
instrument using hardware (Item 23) in place of the
original hardware (Item 8). For 14 in. long instru-
ments use 116-32 x 518 Phillips screw (Item 23) with
116-32 kep “uf (Item 26).
7. The bottom cover feet and tilt bail assemblies
may be removed if necessary.
8. The original hardware, side dress panels, feet
and tilt bail assemblies should be retained for fut-
ure conversion back to bench mountine.
0777
11
CIRCUIT DESCRIPTION
MODEL 427
SECTION 6. CIRCUIT DESCRIPTION
5-1.
GENERAL.
beck amplifier, e X10 gain filter section, suppression
.“d power supply circuits ee show” in Figure 12. The
feedback emplifier is located an the “Amplifier Beerd”,
PC-289.
Board”, PC-291, PC-292.
located on the “Mother Board”, PC-290. justment. Resistor R307 serves as a current limit de-
5-2.
fier is composed of e high-gain amplifier connected ee
e feedback emmeter.
R227 are set by the GAIN Switch (SZOl). The high-gain
emplffier is composed of a dual FET input stage (Q20IA
end B), e differential amplifier (QAZOl), end en output
stage (9203 end Q204).
resistor R201 to the cutput stage et Q203 end Q204.
Potentiometers R232, R233, and R234 ere internal frequency compensetion controls for leg, lOlo, end 1011
gains respectively.
AD., cantrol.
emplifier is 1 volt.
5-3.
of e high-gain amplifier connected aa e 12 dB/octave
low pass filter es sham in Figure 13. The amplifier
consists of intel(rated circuit QAlOl end ~“tp”t stege
(QlOl end Q102).The gain is established et X10 by resistors RllO end
R112 + R113.
adjustment.
adjustment.
The filter circuitry is located on the “Pilter
FEEDBACK AMPLIFIER (PC-289). The feedback empli-
PILTBR (PC-292).
The Made1 427 is composed of a feed-
The power supply circuitry is alit. Potentiometer R304 is a” internal voltage ed-
The feedbeck resietors R22o through
The feedback is connected from
Potentiometer R235 is the ZBRO
The full scale output of the feedback
The filter circuit ie composed
Full scale output ie 10 ;olts. -
Potentilnwtel: RlOS is en internal zero
Potentiometer R113 is en interns1 gain
a. +15 ” Reguletor.
secondary of transformer T301. The ec ia rectified by
P full-weve bridge rectifier (D301). Trensistor Q301
is the series pees reguletor. Integrated circuit
301 is . self-conteined reference end regulating cir-
vice.
b. -15 ” Regulator.
secondary of trenaformer T301. The ec is rectified by
P full-wave bridge rectifier (D302). Trensietee Q302
is the series pees reguletor.
302 is e self-contained reference end regulating cir-
cuit. Potentiometer R309 is en internal voltage ad-
,ustment.
vice.
5-5.
suppression is applied et the input es show” in Figure
15.
suppression in decade steps from lo-3 te lo-lo *Slp.3=.3*
(Resistors R325 through R332). Potentiometer R333 is
the FINE Control which provides adjustment frnn 0 to
1.5 times the WAX setting. Switch S304 eete the polarity (either + end - 15 volt eource). Current suppresaionis e function of V,,&S,
where “cS = Voltage et the wiper of R333.
Exemple: If MAX AMPEP.Rs = 10-b
Resistor R307 mrves as a current limit de-
CURRKNT SUPPRESSION CIRCUITRY (PC-290). The
The N&X AMPERES Switch (5303) sets the current
IQS = Series Resistor (R325 through R332).
AC power ia tapped from one
QA
AC power is tapped from one
Integrated circuit QA-
--
POWER S"PPLY (E-290).
5-4.
+15 V dc et up to 70 mA for the amplifier circuits.
The regulator circuits ere composed of identicel camponents end are connected ee shown in Figure 14.
The pewer supply provides
GAIN
III
r-5
I I
2!5
SUPPRESSION
FIGURE 12. Block die‘rr of l hi‘h-‘peed current l mplifier
12
end if “cS = cl5 ”
the* Its = +15v = +1.5 x 10-G amperes
107n
RISE TIME
FILTER
0471
Cl01
I,
RIOI
r--------1
0
RI16
0471
FIGURE 16.
component Layout - PC-291.
13
COMI
14
1
FIGURE 17.
Component Layout - PC-290.
MODEL 427
COMPONENT LAYOUTS
?
FTGURE 18.
component Layout - PC-289.
FIGURE 19.
component Layout - PC-292.
0471
15
COMFUNENT L4YOoTS
MODEL 427
PC-290
16
FIGURE 20.
Chaaais - Top View.
0471
MODEL 427
SECTION 6.
REPLACEABLE PARTS LIST: This section contains
6-l.
a list of components used in this instr"ment for user
reference.
individual parts giving Circuit Designation, Description, Suggested Manufacturer (Code Number), Manufac-
A
Cb"ar
cem
cefr* Ceramic Tubular
Cer Trimmer ceramic Trin!mer
camp Composition
DCb
twsig.
EAL
ETB
ETT
The Replaceable Parts List describes the applicable. The complete name and address of each
Abbreviations and Symbols
ampere
Carbon Variable
ceramic Disc
Deposited Carbon
Designation
Electrolytic, Aluminum
Elecrrolytic, Tubular
Electrolytic, Tantalum
REPLACEABLE PARTS
F
Fig
GCb
k
I-I
M
Mfr.
MeF Metal Film
MY
NO.
turer's Part Number, and the Keithley Part Number
Also included is a Figure Reference Number where
Manufacturer is listed in the CODE-TO-NAME Listing
following the parts list.
TABLE 6-l.
farad n ohm
Figure
Glass enclosed Carbon Printed Circuit
kilo (103)
micro
~~~ (106)
Manufacturer
Mylar w watt
Number
(10-6)
&
P0ly Polystyrene
Ref.
TCU
v volt
w/l
WW"ar
pica (10-12)
Keference
Tinner Copperweld
WiR?WO"nd
Wirewound Variable
6-2. ELECTRICAL SCHEMATICS AND DIAGRAMS. Schematics
and diagrams are included to describe the electrical
circuits as discussed in Section 5. Table 6-2 idenc-
ifies all schematic part numbers included.
HOW TO USE THE REPLACEABLE PARTS LIST. This
6-3.
Parts List is arranged such that the individual types
of components are listed in alphabetical order. Main
Chassis parts are listed followed by printed circuit
boards and other subassemblies.
Front Panel Overlay
Rear Panel
Side Exerusion Left
Side Extrusion Right
corner Bracket
Screw, Socket, 6-32 x 114
Screw, Phillips, 6-32 x l/4
Clip for Side Dress
Side Dress Panel
Tap Cover Assembly
Top CO"er
Screw, Socket, 6-32 x 5116
Bottom Cover Assembly 24763B
Bottom cover
Screw, Socket, 6-32 x 5/16
Feet Assembly
Feet
Ball
Tilt Bail
Screw, Phillips, 6-32
Kep Nut, 6-32
f,k -\U'&
TABLE 6-4.
Mechanical Parts Lise
Qty. Per Assembly Keithley Part No. Figure NC
PC-291
PC-292
PC-289
PC-290
PC-290
PC-290
1
4
1
1
1
1
2
4
4
2
2
1
4
1
4
4
4
1
4
4
247566
24758B
247608
24754C
24754C
247458
FA-101
24755B
24732C
2473X
243228
FE-6
171478
20
20
21
23
23
23
21
22
18
WARNING
Using a Line Power Cord other than the one suppLied
with your
shock hazard.
damaged, replace only
instrument
If the Line Power cord is lost or
may result in an electrical
with
Keithley Part No. CO-7.
0878
MODEL 427
REPLACEABLE PARTS
0471
FIGURE 21. Chassis Assembly-Exploded View.
FIGURE 22.
Bottom Cover Assemblv.
REPLACEABLE PARTS
HOOEL 427
circuit
Ilesig. Value
Cl01
Cl02 680 ;i
Cl03
Cl04 6800 pF
Cl05 .022 @
Cl06
Cl07
Cl08
c109*
c110*
Cl11
Cl12
c115*
Cl16 .033
Cl17
Cl18 .33
c119s 1
c120* 3.3
150 oF
.0022 p
.068 uF
.22
'b
.68 p
2.2 pP
6.8 @
68 pF
330 DF
.Ol
.l
Rating
-
500 v
500 "
500 v
500 v
200 "
100 " MY
200 v MY
200 v MY
200 v MY
200 v MY
500 v P0ly
500 v Poly
500 " Poly
500 " Poly
200 " Poly
7-1.
checking the instrument to verify operation within
specifications. The procedures and adjustments should
be performed in the exact sequence given to obtain
satisfactory results.
7-2. TEST EQUIPMENT.
in Table 7-1.
tuced provided the accuracy tolerances are equal to or
better than the equipment specified.
The Suppression Max. Amperes switch will be left
in the E posirion unless stated otherwise.
PKOCED”RES .
7-3.
a. Preliminary Calibration.
1. Power Supplies.
a).
point and chassis and adjust the f15 volt poten-
tiometer R309 for +15 Volts t10 "". "Sing the
oscilloscope check for less than 1 m" peak-topeak ripple.
b). Connect Model 163 between the -15 volt test
point and chassis and adjust the -15 volt poten-
tiometer R304 for -15 volts ?lO mV. Check for less
than 1 mV peak-to-peak ripple.
This section contains procedurea for
Use the test equipment specified
Equivalent instruments may be substi-
NOTE
Connect Model 163 between the +15 volt test
2. Line Regulation.
Plug the Model 427 line cord in to a "ariac
a).
with Line Monitor.
Check the il5 volt supplies with the "ariac
b).
adjusted for 90 and 125 volts. The voltages should
be i-15V +20 m" with less than 1 mV peak-to-peak
ripple.
3. 234 Volt Operation.
Set the 117-234 volt switch to the 234
a).
volt position and plug the 42, line cord into the
234 volt line.
b). Check the 215 volt supplies. They should
read i15 volts ?1O mV with less than 1 mV peak-
to-peak ripple.
4. Overload Circuit Check.
Connect Model 163 to the Model 427 output.
a) f
Set the Model 163 to the 10 volt range.
Set the Model 427 controls as fallows:
b).
GAlN : 106 "olts/amperes
SUPPRESSION: (-1 10-5 amperes
RlSE TIME: 300 Ins
c). Turn the Suppression Fine control to obtain
a reading of approximately t9.5 V on the Model
163.
The Model 427 overload light should be off.
1nStr”ment Type
I-
Picoampere source
Digital Voltmeter
Oscilloscope
Function Generator
Microvolt-*meter
Variable Transformer
Line Voltage Monitor
True RMS "TVM
Keithley, Model 261
Keithley,,,~Model 163
Tektronix, Mod'+,~~ or 5618 ,,~
Wavetek, Model 111 or 130
Keithleiy, Model l?i
variac ',l_
--
Ballantine, Model 320
~/,'
-I
1072
MODEL 427
CALIBRATION
d). Slovly t”rn the Suppression Fine control
CW until the overload light comes on. ~,,is
should occur between +10 and +11 volts.
e). Set the Model 427 Suppression Polarity
switch ta (+) and repeat steps & and c, Readings
on the DVM will now be negative.
5. current Amplifier Zero.
a). Set the Model 427 gain switch to zero check,
suppression to E and Rise Time to 30” ms.
b). Turn the 427 front panel zero control ccw
until overload light comes an. Then very slowly
turn the zero control cw until light goes off.
C”“ti”“e turning c0*tr01 cw until light comes on
again. Then slowly turn control ccw and set in
region where overload light stays off.
6. Filter Amplifier Zero and Gain.
a). Set the Model 427 gain to lo4 V/A and Rise
Time to 300 me. Connect the Model 163 DW to the
Model 427 output. Set the Filter Amplifier zero
pot (F.108) for 0 ilm” at the Model 427 output.
Set the 427 Gain to lo5 V/A and cmmect a
b).
DVM (1V range) to the OUtPUt Of the first stage amplifier (QA201, Q203, 4204) at location on PC-290
(mother baard) at jumper found directly below pot-
entiometers R232 and R233.
set the Suppression to
10” amperes and adjust the front mnel pot R333 for
a reading of l.OOOV.
connect DVM (1OV range) CO
output of 427 and adjust Filter Amplifier gain
pot (R113) for a reading of 10.00 volts.
Set the Model 261 to N6 ampere and the
a).
Model 427 gain to 10’ V/A and connect the test
set up as shown in Figure 23 using a BNC TEE
connector on the Model 427 input.
b). With no input connected set up, the Model
153 for CENTER ZERO and VOLT K-21%. Zero on the
100 pV range then set the range to 1. mV.
c). >ir&t$ Model 261 output OFF increase
the -1 153 $ensftivity to 300 v” range while
mai”camCig~ a “0” Indication on the Model 153
using the Model 427 front panel zero control.
Correct drift with the Model 427 zero co”trol as
needed during checks.
d). Switch the Model 261 between OFF and (+)
,..~as\p,eeded to obtain a steady reading on the Model
! 153.’ me reading should be leSS tha
P-
300 pv.,
e). Repeat step $ but witch befw:&,FF~%“d
(-) on tiy Model 261. The reading should be
less thqh +300 u”. Re-zero the Model 427.
0877
FIGURE 23.
Measurement of Input Voltage Drop.
27
CALIBRATION
MODEL 427
TABLE 7-2.
427
GAIN V/A RISE TINE FREQUENCY
11
;;10
109
108
107
106
105
104
8. Amplifier Rise Time.
Connect Function Generator to the Model
a).
427 input and connect the Model 427 rear panel
output t" the Oscilloscope Using the test set up
shar" in Figure 24.
Adjust the 10' through 1011
b).
the specified 10% to 90% rise time using the triangular wave frequency and adjustment listed in
the table. Adlust the Function Generator as
needed to obtain a 10 volt peak-to-peak output
from the Model 427.
rangea for the specified rise times. There should
be no overshoot on any of the ranges.
Check the 10 through lOti
427 WAVETEK
1.0 ms 100 Hz
.3 me 500 Hz
.l ma
.03 ma 2 kHz
.03 me 10 kHz
.Ol m 10 kliz
.Ol me 10 kH*
.Ol r@E 10 kliz
ranges within
1 kHz
MAX 10-90x
RISE TIME
1.50 "Is Slider 6 Pot
0.40 m
0.22 la8 Pot
0.60 me None
0.40 me
0.015 Ins NO"=
0.015 ms Ncme
0.015 ms NO"=
9. Amplifier Noise.
a) .
427 input high end ground.
rear panel output and check the Model 427 BMS
output noise for all settings in Table 7~3.
10. Filter Rise Time.
Connect B 1OOpF capacitor between Model
Connect the TRMS VTVM to the Model 427
b).
Set the oscilloscope controls as follows:
4.
VERTICAL INPUT: ZV/Di".
COUPLING: DC'
TRIGGER:
COGPLING: AC
Ext.
RISE TIME
ADJUSTMENT
Slider 6 pot
NO"=
Shielded
/
- r ,I,,,1
PUNCTION
GENERATOR
- L-- J
GAIN V/A
(427)
11
;;10
109
1oS
107
106
105
104
i
, CAPA
_ I
I ,
FIGURE 24. Measurement of Rise Time,
TABLE 7-3.
RISE TIME
(427) T
1.0 ms
.3 In*
.l ms
.03 me
.03 me
.Ol ma
.Ol ma
.Ol m
TRUE
MS
100
"I"
30 mv
10 mv
10 mv
3 mv
3 mv
3 mv
3 rev 2 mv
I I
MAX. RMS
NOISE
40 mv
20 mv
10 mv
5 mv
2 nlv
2 mv
2 mv
28
0574
>
MODEL 427
CALIBRATION
TABLE 7-4.
10 !a
10 pa
.l Ins
.l nla
1 ms
1 me
10 me
1.0 tn.5
FUNCTION
GENERATOR
Wavetek
Frequency
10 kHz .Ol Ins .015 In*
1 kHz .03 me .040 me
1 kHz .l In* .15 ms
100 HZ .3 me .37 ma
100 Hz 1 me 1.1 Ins
10 H7. 3 Ins 3.7 Ins
10 "7. 10 Ills 11 m
10 HZ 30 Ilie 37 me
SERIES
RESISTOR MODEL 427
1om
FIGURE 25. Measurement of Filter Rise Time.
427 Rise Time
setting
CURRENT
AMPLIFIER
Max lo-90%
OSCILLOSCOPE
RfSe Time
Set the Model 427 gain to lo4 V/A.
b).
the series resistor (104) and the square wave frequency listed, check the filter amplifier lo-90%
rise time.
as needed to obtain a 10 volt peak-to-peak ""tput
from the Model 427.
a combination of both should not exceed t 10%.
Trigger the Oscilloscope from the Function Generator sync output.
Set the Function Generator amplitude
The overshoot and dipping or
“*“etek
OSCillO*COpe
.l eec 1 HZ 100 me 110 Ins
.l set 1 HZ
Frequency Setting Rise Time
L
"sing
TABLE 7-5.
the Function Generator for 1 volt out of the
Model 427.
below check the lo%-90% rise time of the filter
amplifier.
427 Rise Time Max lo-90%
300 tns 370 Ills
"sing the square wave frequency listed
Set the Oscilloscope for .2V/Div and set
c) .
0574
29
CALIBRATION
MODEL 427
b. Final Calibration.
1. Gain Accuracy.
Connect the Model 261 Picoampere Source to
4.
the input of the Model 427 and connect the Model
163 to the Model 427 output.
Tima Co"sta"t to 300 Ins.
Set the Model 163 on the 1 volt range and
b).
step the Model 261 and Model 427 through the ranges
in Table 7-6.
range given.
age OUtpUt is negative.
261
-
2. Offset current 4. Drift.
The DVM readings must be within the
For positive current inputs the volt-
TABLE 7-6.
427 Gain
Set the Model 427
Model 163
.98V to 1.02V
.98V to 1.02v
.98V to 1.02v
.98V to 1.02V
.98V to 1.02V
.98V to 1.02V
.96V to 1.04V
.96V to 1.04V
4.
through the positions in Table 7-7. The readings
on the Model 163 should be within the tolerance
polarity switch in the (-) position. The Model
163 readings will now be positive.
Step the Suppression and Cain switches
TABLE 7-7.
SUPPRESSION
LO-lo
10-9
10-8
lo-7
lo-6
10-z
IO-3
10
Repeat stepa a and c with the suppression
d)
-lov t10 mv
-lOV -i600 mV
-lOV i-600 mV
-10" i600 mV
-lOV t600 mV
-lOV f600 mV
-lOV C600 mV
-lov i-3 "
MODEL 163
Re-check the current amplifier and filter
a).
amplifier zero. Place a CAP-18 on the Model 427
input and sat the Model 427 Cain to 1011 V/A and
Rise Tim2 to 300 ma.
b). Connect the Model 163 to the Model 427 out-
put and set it to the 1 volt range. The reading
on the Model 163 should be less than 100 mV.
3. current suppression.
a). Place a CAP-18 an the Model 427 input and
set the gain to lo11 V/A. Connect Model 163 to
the Model 427 output and set it to the 10 volt
range.
Set the Model 427 Suppression switch to
b/6
lo- , set the Polarity to (+) and the Fine co"tral to obtain a -10 volt i10 m" reading on the
Model 163.
Set the Model 427 controls as follows:
4.
GAIN: LO5 V/A
SUPPRESSION: 1O-7 ampere
RISE TINE: 1 ms
POLARITY:
*POLARITY is (+) for setting recorder
printer left of zero and (-) for setting
printer right of zero.
Set the recorder sensitivity to 10 mV full
b).
scale and "sing the suppression FINE control set
the recorder printer to a convenient spot for
recording drift of the Model 427.
After a 1 hour warm-up the Model 427
c) .
should drift no more than t500 u" (five minor
divisions) in any subsequent 24 h&r period
*500 lJV/"C.
(+) or c-j*
30
0574
-
I ’
/ ’
:
0
ip
IT-----3-----J
A
I
I
Y
SERVICE FORM
Model No.
Name
Serial No.
P-0. No. Date
Phone
Company
Address
City
State
Zip
List all control settings and describe problem.
(Attach additional sheets as necessary.)
Show a block diagram of your measurement system including all instruments connected (whether power
is turned on or not). Also describe signal source.
Where is the measurement being performed? (factory, controlled laboratory, out-of-doors, etc.)
What power line voltage is used?
Frequency?
Variation?
Ambient Temperature?
OF. Rel. Humidity?
Variation?
OF.
Other?
Any additional information. (If special modifications have been made by the user, please describe below.)
*Be sure to include your name and phone number on this service form.
Addendum
29103-C-l
u/a/a3
Instruction Manual Addendum
Model 427 Current Amplifier
The following change information is provided as a supplement to thk manual in order to provide the
user with the latest improvements and changes to the manual in the least amount of time. It is recommended that this information be incorporated into the appropriate places in the manual immediately.
Replace the information contained in step 8, page 28, under Amplifier Rise Time, with the following
procedure:
8. Amplifier Rise Time
a. Connect the Function Generator to the Model 427 input and connect the Modal 427 rear panel
output to the oscilloscope using the test setup shown in Figure 24.
b. Adjust the 109 through 101’ rangas within the specified lo%-90% rise time using the triangular
wave frequency and adjustment listed in Table 7-2. Adjust the Function Generator, as needed, to
obtain a 10 Volt p-p output from the Model 427.
c. Without altering the test sat-up, verify that the 10 through to8 ranges meet the rise time
specifications in Table 7-2. Adjust the Function Generator, as required to obtain a 10 Volt p-p out-
put from the Modal 427. There should be no overshoot on any range.
d. Remove the 1OOpF capacitor from the test set-up and connect the Function Generator directly to
the Modal 427 input. Verify the 101 through 106 10% -90% rise time, using the square wave fraquency. per Table 7-2. There should be no overshoot on any range except for the 104 V/A which
should be lass than 10% overshoot.
. .
m INSTRUMENTS
Model 427 Current Amplifier Addendum
INTRODUCTION
This addendum to the Model 427 Current Amplifier Instruction Manual is being provided in order to supply
you with the latest information in the least possible time. Please incorporate this information into the manual
immediately.
Page 3; Note that in Figure 2 the dials on the knobs are now black.
R76-10
Rl-IM
R88-1 OOk
R88-23.2k
R88-22.1 k
R88-IOk
R94-18.2k
R88-IOk
R88-12.1 k
R88-499
R88-499
R88-10
R76-470
R88-10k
R78-470
R76-10
R76-10
Rl -270k
R94-100
RI 2-900
R94-10k
R94-100k
R94-1 M
Rl3-IOM
Rl4-IO8
18
18
18
18
18
18
18
18
18
18
1:
18
18
::
29103-c-2 I 7.90
Page 24; Replace Table with the following:
ClrCUlt
De&g.
D306
D309
D310
0311
D312
CkUlf
De&g.
J301
J302
QA301
DA302
QA303
5301
5302
5303
Q301
Q302
Q303
5304
F301
F301
T301
P30.5
DS-301
DS-302
MOTHER BOARD
TYPe
Silicon
Silicon
Silicon
Silicon
Silicon
TYPO
Connector, Mini-PV
Connector, Mini-PV
Integrated Circuit, Voltage Regulator
Integrated Circuit, Voltage Regulator
Integrated Circuit
Switch, Line Voltage
Switch, “PUSH ON’ Power with lamp
Switch. CURRENT SUPPRESS
Knob Amperes
Transistor
Transistor
Transistor. Silicon, NPN. TO-92 Case
Switch POLARITY
Fuse. tt7V. .25a, Slo-Blo.3AG
Fuse, 234V, IIBA. Slo-Blo, 3AG
Transformer
Receptacle, AC
Line cord. mates with P305
Pilot lamp, neon (replacement for 5302)