Keithley 427 Service manual

INSTRUCTION MANUAL
MODEL 427
CURRENT AMPLIFIER
0 1975, KEITHLEY INSTRUMENTS, INC.
CLEVELAND, OHIO, U.S.A.
DOCUMENT NUMBER 29103
CONTENTS
1. GF,Ng3,&.L DESCRIPT~ON-------------------------------.-------- 1
2.
OPERATION-------------------------------------------------- 4
MODEL 427
3. APPLICATIONS----------------------------------------------- 9
ACCESSORIES------------------------------------------------ 10
4.
5. ClRC"IT DESCRIPTION---------------------------------------- 12
6. REp~Cp‘&LE PARTS------------------------------------------ 17
7. CALIBRATION------------------------------------------------ 26
SCNEMATICS---------------------------------------------------- 33
1074
MODEL 427
ILLUSTRATIONS
ILLUSTRATIONS
Figure No. Title
1 Front panel. __-___---___-_____-___________________ 1 2 Front pane1 Controls. ________--______-____________ 3 3 Rear Panel Controls. - 3 4 shunt Method Measurement, -----------------__------ 4 5 Effect of Shunt capacitance. ---------------------- 4 6 Compensation for Shunt Capacitance. --------------- 5 6b Extended Frequency Response. ---------------------- 5 7 Fee&a& Method. _--__-_-__________-_______________ 6 8 Input Voltage N&se. -------------___-------------- 6 9 Bandwidrh of Feedback System. --------------------- 7 9b Effect of filter on Noise spectrum. -------------- 7
9, Effect of Input Capacitance on Noise. ------------- 7 10 Frequency Compensafian. ---------_____--_-__------- 7 11 Plot of Noise-Improvement Contours. 12 Block Diagram of a High-Speed Current Amplifier, -- 12
__- _____ -__-__
Page
9
13 Filter circuit. ------_______--_-__-_______________ 13 14 power s”pp~y Regulator. --------------------------- 13 15 current suppression. ------------__---------------- 13 lb COmpOnent Layout - PC-291. ------------------------ 13 17 component Layout - pc-290, -----------------___---- 14 18 component Layout ­19 COmpOnenf Layout ­20 chassis - Top vie”. ------------___--------------- 16 21 Chassis Assembly - Exploded “few. ----------------- 19 22 Bottom CO”er Assembly. -------------------------- 19 23 Measurement of Input Voltage Drop. ---------------- 27 24 Measurement of Rise Time. -------_--_____-___-_____ 28 25 Measurement of Filter Rise Time. ------------------ 29
pc-2?39. P&292.
---------_------___-____ 15
---------------__------ 15
1074
iii
SPECIFICATIONS
SPECIFICATIONS
RANGE: 10’ to 10” volts/ampere in eight decade ranges.
(10-13 ampere resolution to 10.” ampere full output). OUTPUT: *10 volts at up to 3 milliamperes. OUTPUT RESISTANCE: Less than 10 ohms dc to 30 kHz. OUTPUT ACCURACY: 12% of reading to the lo9 vattsl
ampere range, +4% of reading on the 1O’O and 10”
volts/ampere ranges exclusive of noise. drift and current
offset.
RISE TIME (10% to 90%): Adjustable in lx and 3.3x steps
from “Fast Rise Time” listed below to 330 rnsec.
NOISE VS. RISE TIME’:
I
FAST RISE TlML
MODEL 427
STABILITY: Current offset doubles per 10°C above 25°C.
Voltage drift is less than 0.005% per “C and less than
0.005% ,,er da” of full outDut after l.hour warmur,.
OFFSET CURRENT: Less than lQLz am&e at 25”C’and up CURRENT SUPPRESSION: lo-lo ampere to 10-a ampere in
OVERLOAD INDICATION: Lamp indicates pre-filter or post.
CONNECTORS: Input: (Front) ENC. Output: (Front and
DIMENSIONS; WEIGHT: Style M 3%” half.rack, overall bench
,-
to 7001, relative humidity.
eight decade ranges with 0.1% resolution (lO.turn poten.
tiometer). Stability is +O.Zo/. of suppressed value per “C bO.Z% per day.
INPUT VOLTAGE DROP: Less than 400 /.IV for fullaxle
output on the 10” to 10” volts/ampere ranges when
properly zeroed.
EFFECTIVE INPUT RESISTANCE: Less than 15 ohms on the
10” and 105 volts/ampere ranges. increasing to less than
4 megohms on the 10” volts/ampere range.
MAXIMUM INPUT OVERLOAD: Transient: 1000 volts on any
range for up to 3 seconds using a Keithley (or other 10 mA-limited) highaoltags supply. Continuous: 500 volts on the 10” to 1O’voltsjampere ranges, decreasing to ‘ZOO an the 10”. 70 on the lo5 and 20 volts on the 10’ volts, ampere ranges.
filter overload.
DYNAMIC RESERVE: 10 (20 dB).
Rear) BNC.
POWER: 90.125 or 180.250volts (switch selected), 50.60 Hr.
5 watts. size4’~highx8%‘widex12L/a”deep(100x217 x310 mm).
Net weight, 7 Ibs. (3.0 kg).
i”
1074
MODEL 427
GENERAL DESCRIPTION
SECTION 1.
l-1. GENERAL; The Model 427 Current Amplifier is a high-speed, feedback-type amplifier with particular features useful for automated semiconductor testing,
mass spectrometry, and gas chromatography applications.
l-2. FEATURES.
a. Wide Dynamic Range. Selectable rise times permit low-noise operation important when resolving small current levels.
b. High Speed. out of a 10sSZpere signal with a 100 microsecond rise time.
Typical resolution is 20 picoamperes
GENERAL DESCRIPTION
C. Built-in Current Suppression. the signal level can be measured since large ambient current levels can be easily suppressed.
d. Overload Indication. assured since overloads are automatically indicated.
e. Variable Cain. The GAIN Switch is designated in eight gain positions from lo4 to 1011 volts per ampere - therefore gain adjustment is straight forward.
f. Variable Kise Time. Optimum response can be selected for each gain setting since a separate RISE
TIME switch is provided on the front panel.
Small changes in
Accurate measurements are
0471
1
GENERAL DESCRIPTION
MODEL 427
TABLE 1-l.
Front Panel Controls and Terminals
PUSH Power Switch (S302) GAIN Switch (5201) RISE TIME (5101) SUPPRESSION
MAX AMPERES Switch (S303)
FINE Control (R333)
POLARITY Switch (5304)
ZERO ADJ Control (R235)
INPUT
Receptacle
OUTPUT Receptacle (5102)
~ OVERLOAD Indicator (DS302)
(5202)
Functional Description
Controls power to instrument. sets gain in Volts per ampere.
Sets
rise time Fn milliseconds.
Sets maximum suppression.
Adjusts suppression.
Sets polarity of suppression.
Adjusts output zero.
Input source connection.
Output connectFon.
Indicates overload condition.
Rear Panel Controls and Terminals
TABLE 1-2.
Paragraph
2-4, al 2-4, a2
2-4, a3
2-4, a4 2-4, a5 2-4, a6 2-4, a7 2-3, a 2-3, b
2-5, d
Control or Terminal Functional Description Paragraph
Line Switch (5301)
Power Receptacle
Fuse (F301)
0lJTPuT Receptacle
(P305)
(5103) Output connection.
Sets instrument for 117V or 23411. Connection to line power. Type 3AG Slow-Blow, 117V @ l/4 A (w-17)
234V @ l/S A (w-20)
WARNING
Using a Line Power Cord other than the one supplied
with your instrument may result in an electrical
shock hazard. If the Line Power cord is lost or damaged,
replace only with Keithley Part No. CO-7.
2-4, b 2-3, c
2-3, b
0878
MODEL 427
GAIN
SWITC
S20
,----SUPPRESSION-,
FINE
ADJUST
GENERAL DESCRIPTION
POLARITY
SWITCH
INPUT
5202
ZERO ADJ
R235
FIG"RF 2.
OVERIDAD Power
.
DS302 S302
want Panel Controls.
P
OUTFW
5102
I
0471
FIGURE 3.
Rear Panel Controls.
OPERATION
MODEL 427
SECTION 2.
MEASUREMENT CONSIDERATIONS.
2-1.
a. Current-Detection Devices.
‘small electrical c~rrent8 has been the basis for a
number of instrumental methods used by the analyst. Ion chambers, high-impedance electrodes, many forms of ch=“metog=aphic detectors, phototubes and multipli­ers are coaronly-used t=ansduce=a which eequire the measurement of small currents. Devices used for this measurement a=e often called electraaeters.
b.. In any measure-
ment, if e”“=ce noise greatly exceeds that added by
the inst=“mentatian, optimization of instrumenteti”” is unimportant. ical minimum, optimization of instrumentation charac-
teristics becomes imperative. TO determine the cate­gory into which this meas”=ement falls. the researcher needs t” be familiar with the characteristics which
impoee theoretical and practical limitations on his me*surement .
theoretical limitations present in voltage measueements
The noise inceeases with 8”“=ce realstance, and the
familiar equation for the mean-square noise voltage is
q = 4kTRAf Eq. 1
When source noise approaches theoret-
Most researchers a=e familiar with the
The DleasUrement of
OPERATION
Prom this equation it is irmnediately apparent that the m%QB”rement of emall current =equi=es large values of R, i.e., high impedance levels. Howwee, thfe gives difficulties for meas”=ements requiring wide bandwidths because of the RC time constant associated with a high-megohm resistor and even a few picofarads of cir-
cuit capacitance. generating a voltage across a parallel RC. The fre­quency response of this current measurement is limited
by the RC time constant.
end the -3 dB p”int “CC”=B at a frequency
Lor* noise and high
requirements. techniques must be used which obtain high speed “sing
high-impedance devices.
C. Hiah Speed Methods.
1. High epeed can, af c”“=se, be obtained in .
shunt-type meae”=eme”t by “sing a low value for the shunt resist”=. resistor value int=ad”ces excessive noise into the
meQ8”rement.
Figure 4
speed,
TO optimize a current-measuring system,
As pointed ““t above, such a srmll
shows a c”==ent s”“=ce
Figure 5
therefore, a=e contradictory
shows this response
whe=e k is the Boltzma”” Constant, T ia the absolute
temperature of the s”“=ce resistance R, and noise bendwidth( 3
single RC rolloff.) In the case of cureent measure-
ments it Is more appropriate to consider the noise
current generated by the ~l”“=ce and load resistances. The mean squaee noise c”==ent generated by a resistor
is given by Eq. 2.
FIGURE 4.
In the shunt method c”=re”t is measured by
the voltage drop ac=“ee a resistor.
times the 3 dB bandwidth for a
Af
is the
2. A second method to achieve bandwidth is to keep R large, to accept the frequency roll-off starting at F”, and t” change the frequency eesponae of the voltage amplifier a8 ehown in Figure 6a. The combined effects of the RC time c”“sta”c folloved by this amplifier is shown in Pigure 6b and it is seen that the frequency response of the c”==ent
measurement has been extended to Pl. The frequency
at which the amplifier gain sta=‘ts to increase must be exactly equal t” the frequency F” determined by the RC time c”nstant in order for this approach t” result in a flat frequency respanse. Therefore,
FO
FIGURE 5. The frequency respanse of the shunt method
1s limited by omnipresent ahunt capacitance.
LOG FREQUENCY
I
0471
MODEL 427
OPERATION
this oethad is ueeful only far application* where the shunt capacitance C is constant. Aaide from thin drawback this is * 1eSitimste approach which is being wed in low-noise, high-speed current-
meesuring applicatians. In addition to current noise
in the *hunt and in the amplifier input stage, B
maJor source of noise in this system *ri*** from
the voltage-noise generator ssaociated with thb in­put atage (reflected a* current noise in the shunt resistor) caused by the high-frequency peeking in the following stages of amplification. More will be said about this in the discussion on noise behavior.
3. A third method used for speeding up * current
measurement asas guarding techniques to eliminate
the effects of capacit*nces. Unfortunately only
certain type* of capacitance*, such ** cable cap=-
itances, can be conveniently eliminated in this
manner.
itences associated with the *ource itself became*
very cumbersome and m*y not be feasible in many in-
stsnces.
*re identical to those mentioned in the second
system.
4. A fourth circuit configuration combines the capability of low-noise and high-speed performance with tolerance for varying input C and eliminate* need for separate guard by making the ground plane *n effective guard. This is the current-feedback technique. ment of 3 over shunt technique*. Again, the major sources of noise are identical to those mentioned
in the second system.
d. Noise in Current Measurements. Noise forms *
b*aic limitation in *nv hinh-speed current-measurinn
system. The shunt *y&m give; the simplest curren;
measurement but does not give low-noise performance.
A properly designed feedback *y*tem gives superior
noise - bandwidth performance. Noise in these two
systems will be discussed next.
1. Noise Behavior of the Shunt System. High speed end low noise *r* contradictory requirements in any current meesurement because *orw capacitance is always present. The theoretical performance limftetion of the shunt *yetem c*n be calculated **
To eli,r,inate the effect of parasitic c*p*c-
The major *ourc** of noise in this *“*tern
This technique gives * typical improve-
The rms thermal noise current (in) generated by * resistance R is given by
Eq. 4
The equivalent noise bandwidth (.f) of * parallel SC combination is Af = 1/(4RC) snd the eignal hand­width (3 dB bandwidth) F, = 1/(2nRC). For practical
purposes peak-to-peak noise is taken 88 5 times the ml* value. The peak-to-peak noise current can now
be written a*
i
UPP =
In practice, e typical value for shunt cape.cit*nce
is 100 picofarads. rule-of-thumb is obtained. The lowest ratio of
detectable current divided by signal bandwidth using
*hunt-techniques is 2-10-14 ampere/Hertz for B peak­to-peak signal-to-noise ratio equal to 1. A coroll-
ary far this rule-of-thumb expresses the noise cur-
rent in term* of obtainable risetime (lo-SO% rise­time tr = 2.2 RC). The lowest product of detectable current and risetime using shunt technique* is 7 x
lo-l5 ampere seconds. assumed that the voltage amplifier does not contri­bute noise to the measurement.
2. Noise Behavior of the Feedback System. There
are three *ource* of noise in the feedback system
that have to be looked at closely. The firat two,
input-stage shot noise and current noise from the mea*urinS resistor, are rather straight-forward. The
third, voltage noise from the input device of the amplifier, cau*e* *ome peculiar difficulties in the measurement. Any resistor connected to the input
injects white current noise (Eq. 4). In the circuit of Figure 7 the only resistor that is connected to
the input is the feedback resistor R. As in the
shunt system, R must be made large for lowest noi*e. Beceuse this noise is white, the total contribution can be calculated by equ.,ting Af to the equivalent noise bandwidth of the system. The second *ource of noise is the current noise from the amplifier input. This component is essentially the shot noise asaoci­ared with the gate leakage current (io) of the input device. Its rms value equals . . .
2 x 10-9 F,
With this value the following
F
In this derivation it has been
Eq. 5
FIGURE 6.
0471
LOG FREWENCY
FO
ny tailoring the frequency response of the amplifier (Pig. 6a) the frequency response of the shunt method c*n be extended.
F>
FIGURE 6b.
FO
Extended frequency response.
LOG FREQUENCY
F,
OPERATION
MODEL 427
T;; = J-zTp-
where e is the electronic charge. The contribution
of this noise generator is also white. N*t only do
these two noise sources generate white current noise, the noise in a given bandwidth is also independent
of the input capecitence C. The mejor source of
noise in e feedback current meesurement is the noise
contribution aseocisted with the voltage noise of
the input amplifier. The voltage noise ten be rep-
resented by a VOltage noise generator (0,) et the emplifier input es shown in Figure 8. This wise generator itself is assumed to be white. However, its total noise contribution to the current-measuring
system is not white.
reveal that et low frequencies P large em*u*t of feed­beck ie applied around the voltage noise source {en).
However, the SC combination ettenuetes the high-
frequency components of V,,t so that no feedback is present et high frequencies. Thus, the noise con-
tribution to the output voltage V,,t from the valt­age noise source a* is no longer independent of
frequency. The noise is “colored” and increases in intensity for ell frequencies higher than F,. The resulting noise spectrum is shown in Figure 9b. The tote1 system noise is related to the are* under this curve. plotted on the horizontal axis, the eree under the
curve et higher frequencies represents e signifi­cantly larger amount of noise then e similar eree
*t low frequencies. the frequency response of the current measuring system.
interesting et this point to compare this noise spectrum with the frequency response of the voltage amplifier in Figure 4 es shown in Figure 6a. A volt­age noise eouec.e et the input of the amplifier would generate a noise spectrum according to the amplifier
frequency response as shown in Figure 6a. The noise
spectrum of such e system, then, is identical to the
noise spectrum of the feedback system as given in
Figure 9h.
that signal-to-noise performance of a measurement cen**t be improved by feedback techniques. At the
high-frequency end the voltege noise is limited by
the frequency FA which is the high-frequency roll-
off point of the operational amplifier. It should
Because the logarithm of frequency is
Figure 9e ia identical to Figure 6b. It is
This illustrates the well-known fact
Inspection of Figure 6 will
For comparison, Figure 9a show
he noted that even though the useful bandwidth of
the system extends only t* Fl, there era noise com-
ponents of higher frequency present. To obtain best widebend-noise performance, these high-frequency noise components have to be removed. This ca* be
achieved by adding a low-pass filter section follow-
ing the feedback input stage. If the band-pass of
thin low-pass filter is made adjuetable this filter can nerve the dual purpose of removing high-frequency
noise end of limiting the signal bandwidth of the
system.
2-2. THEORY OF OPERATION.
8. Current Feedback Technique. The basic circuit configuration used in the current-feedback technique is shown in Figure 7. current-measuring resistor R is placed in the feedback loop of e* inverting emplifier with a gain of A*. The frequency response obtained with this circuit is iden­tical to thet s+nvn in Figure 6b. F* agein is the frequency associated with the RC time constant:
F, =
The frequency response of the syetem is extended t* a
frequency fl where
F
, = AoF,
Note that the frequency rerponse is automatically flat without heving to match break points. However, the total bandwidth of the system (Fl) is still limited by the value of the ahunt capacitance C across the
input. back technique avoids the use of low values for R which could generate exceesive current noise.
difficulty of the feedback system ariees from shunt capacitence esaociated with the high-megohm resiaeor R
in the feedheck path.
the resistor is CFr then the bandwidth (FF) of the
system is determined by the time COnstent RCF:
This improved frequency response of the feed-
b. Refinements of the Feedback System. A major
In this configuration the
SE Eq. 6
Eq. 7
.
If the shunt cepacitence acroes
FIGURE 7.
6
Beslc circuit configuration for the feed­back method.
FIGURE 8.
The voltage noise associeted with the am­plifier input device is en important eourc~
of noise in the high-speed feedback syatew
0471
MODEL 427 OPERATION
FIGURE 9.
FIGURE 9b.
The bendwidth of the high-speed feedback
system (Fig. 9a) ten he limited by using e filter with either e -6 dB/actave or a
-12 dB/octave roll-off. The effect of the filter on the noise spectrum is showwin Fig. 9h.
Effect of input capacitance on
noise is shown in Fig..9c.
Effect of filter on noise spectrum.
FIGURE 10.
Frequency compensation.
FF = 1
2 nllcp
Eq.
A slight modification of the feedback loop can correct
this problem es shown in Figure 10. If the time con­stant RlCl is made equal to the time constent R.CF, it CB* be shown that the circuit within the dotted line behaves exactly es a resistance R. The matching
of time constants in this cese does not become e draw­beck because the copscitances involved era all constant and not effected by input impedance.
C. -12 dB/actave Filter.
1. Theory. To obtain optimum widehand noise per-
fomence e filter with e single high-frequency roll­off (i.e., dB/octeve is required.
-6 dB/octave) is not sufficient end -12 The effect of e -6 dB filter
is shown in Figure 9a end h. The filter is used to limit the system bandwidth to a frequency F2, smaller then Fl. The effect af this filter on the noise spectrum is shown in Figure 9b. It ten be seen that
there ace egain high-frequency noise components above F2, the useable bandwidth of the system. These can he eliminated by using e filter with e -12 dB/octave
roll-off. The result of such .a filter on noise per-
formance is also shown in Figure 9b.
FIGURE 9c.
0471
Effect of input capacitance on noise.
2. Model 427. The input smplifier 18 followed by
en adjustable low-pass filter having e -12 dB/octeve
roll-off end a valtage gain of 10X. The voltage
gain in the low-pass filter avoids premature over-
loading in the input amplifier which ten be seen es fallows. The maximum output voltage V,,t is $10
volts.
The maximum signal level et the input of the
low-pass filter is, therefore, +l volt. At this point in the circuit, wide-band noise could still be present end exceed the l-Volt signal level. The voltege gain of 10 in the filter allows the total pre-filter wide-hand noise to exceed the full scale
signal by e factor of 10 (20 dB). The frequency re-
sponse of this filter is edjustahle for variable
“damping” control.
7
OPERATION
2-3.
CONNECTIONS,
MODEL 427
2-5. OPERATING CONSIDERATIONS.
8.
Input. type which metes with coaxial cables such es Keithley Models 8201 end 8202. high.
(5102 on the front, 5103 on the reer panel). These era BNC type* where the inner contact is output high end the outer shell is chassis ground.
rear panel is a 3-prong connector which metes with Keithley pare number CO-6 line cord.
2-4. CONTROLS.
The outer shell is low or chassis ground.
b. Output.
C.
Power Input. The power receptacle (P305) on the
a. Front Panel.
1. Power Switch “PUSH ON” (5302). This switch
controls the line power to the instrument. ‘The
switch is a special pushbutton type with “Power On” indicated by a self-contsined pilot lamp.
2. GAIN (VOLTS PER AMPERE) (S201). This switch sets the overall gain in eight positions from 104 to loll.
ment of zero offsets.
3. RISE TIME Switch (5101). This switch sets
the lo-90% rise time in 10 positions from .Ol to 300 milliseconds(for the filter section only).
4. SUPPRESSION (MAX) Switch (S303). This switch
sets the maximum current suppression in eight pasi­tions from lo-10 to 10-3 A. When the switch to “OFF” the current suppression circuit is disabled.
5. SUPPRESSION (FINE) control (~333). This con-
trol permits adjustment of suppression with 0.1% resolution.
6. SUPPRESSION (POLARITY) Switch (S304). This
switch set* the polarity of the current suppression
(referred to the input).
7. ZERO ADJUST Control (R235). This control per-
mits adjustment of zero offset through the u*e of the OVERLOAD indicator.
b. Rear Panel.
1. Line Voltage Switch (S301). Sets instrument
for either 117 or 234 V operation.
The input receptacle (5202) is e SNC
The inner contact is circuit
Two outp,ut receptacles *re provided
A “ZERO CHECK” position permits adjust-
Fuse RequirP.ment* 3AG, Sla-Slo
117V: 1/4A 234V: l/SA
Keithley No. F”17 Keithley No. F”-20
is
set
8. Gain. The gein of the Model 427 is defined in terms of volts per *“pare. Since the output level is 10 volts for e full scale input, the gain could also
be expressed e* sensitivity in emperes referred to the
input BS in Table 2-1. Vout = - (Iin x GAIN)
Gain or Sensitivity Referred to the Input
GAIN
Setting Resistor
b. Rise Time. The rise time for each gain setting
is listed in the specifications a* “FAST RISE TIME”.
These rise times are obtained when the RISE TIME
switch is set to the positions indicated in Table 2-2.
GAIN
Setti”g
104 105 106 107
1 10;
1oy 1010 loll
c. Suppressian. Current suppression is provided in
the Model 427 for suppression of input currents up to
10e3 amperes.
variations in e larger signal can be observed. Currents
of either polarity can be suppressed. To suppress an input current the SUPPRESSION should be *et to supply
e current of apposite polarity. The FINE control permits
adjustment up to 1.5 times the MAX setting.
d. Overloads, en overload et two places in the circuit: before end after the “RISE TIME” filter circuit. The OVERmAD
lamp (DS302) will indicate whenever the voltsge sensed ia greater then full scale regardless of the RISE TIME
setting or the frequency.
a. Zero Adjust. The ZERO CHECK po*ition grounds the the input of the instrument and co”“ert* the cuerent amplifier to a high-gain voltage amplifier. The ampli-
fied offset voltage will turn on the OVERLOAD indicator whenever the input voltage offset exceeds 5100 t0l. Therefore the ZERO control should be adjusted so that
the OVERLOAD indicator is off when in ZERO CHECK mode,
yielding the specified input voltage drop.
Feedback
Switch Settings for “FAST RISE TIME”
Rise Time
15 ps 15 us
15 I*8 40 us
60 ps .03 ms 800 220 400
1.5 1 ms 100
TABLE 2-l.
Full Scale sensitivity Output
(Amperes)
103 104 105 106 107 108 109 1010
&Is
“S ps
By suppressing background currents, smell
The overload sensing circuit detects
1
x 10-3 1 x 10-4 1 x 10-5 I x 10-6 1 x 10‘7 1 x 10-g 1
x 10-9 1 x 10-10
TABLE 2-2.
RISE TIME Setti”g*
.Ol “S .Ol ms .Ol “S .03 “9
.l “S 400 .3 ms 200
Eq. 9
Full Scale
(Volts)
10 10 10 10 10 10 10 10
DYlWl”iC Range
2000 2000
2000 2000
J
8
MODEL 427
APPLIChTIONS
SECTION 3. APPLICATIONS
3-1. CURRENT~MEASURING SYSTEM. The typical current meaeuring system consists of a current source, a cur­rent amplifier, and a monitoring device, The current source could include an ion chamber, photomultiplier, or other high-impedance device, such as the Model 427 provides sufficient gain to drive a monitoring device such as a chart recorder or other readout. The Model 427 in this case provides an out­put voltage which is calibrated in volts per ampere a.3 in equation 10.
- (V,,t I GAIN)
Example :
3-2. trates the trade-off between fast rise time and dynamic range. a.s the ratio of maximum peak-to-peak current to peak­to-peak current noise. taken as 5-times the rms current noise. The maximum peak-to-peak current is 2-times the maximum full scale current.
When using current suppression the current-suppres-
sion resistor should be considered as an additional current-noise generator. The values given in Table 3-l do not include the contribution of the suppres­sion resistor. Therefore the selected suppression resistor Rs, should be as large as possible to min-
imize the contribution to current noise.
Iin =
GAIN = 106 voltslampe~e ” O”t = +500 In” The input current Iin would be: lin = - (5x10-~vo1ts/106vo1ts per ampere) Iin = - 5 x 10-7
NOISE BANDWIDTH CONSIDERATIONS.
For this application dynamic range is defined
Peak-to-peak current noise is
NOTE
The current amplifier
Eq. 10
amperes
Table 3-l illus-
3-3. NOISE-IMPROVEMENT CONTOURS. The sensitivity and speed of the Model 427 (for either d-c or a-c
measurements) can be compared to the best perfarm-
ante obtainable with the shunt method of measuring current. The best “noise-risetime” product that can be achieved for d-c measurements (with 100 pF shunt capacitance) in a shunt system is 7 x lo-15 ampere-seconds. 2 x lo-l5 ampere-seconds (also with 100 pF shunt capacitance).
(lock-in, etc.) the-degree of improvement is a func-
tion of shunt capacitance and operating frequency.
The achieveable imprownene over the shunt method
can be plotted in a graph similar to a set of noise
contours. Figure 11 shows the measured impravemene
(negative dB) that can be obtained with the Model
427 at a given frequency and shunt capacitance when
compared to an ideal (noiseless) amplifier Fn a shunt
system.
,
I
FIGURE 11. Plot of noise-improvement contours.
However the feedback system achieves
When used in a-c narrowband systems
FREOUENCY IHI1
RMS’Noise Current (Typical)1 as a Function of Gain and Rise-Time Setting
TABLE 3-l.
,vL.. I,.,“,.,
PULL SCALE
GAIN VIA
104 105 106 107
108
109 1010 1011
1
With up to 100 pP input shunt capacitance.
KEY :
x = Filter Bandwidth is greater than current-amplifier bandwidth. * = larger Rise Times are useful for increased filtering of the signal arid noise inherent in the source.
0471
CURRENT
AMPERES 300 100 30
10-3 10-4 10-5 m-6
10-7
104’
10-9
lo-1o *
They do not further improve the instrument noise contribution except when the input shunt capacitance exceeds 100 DF.
* * * * *
* * * :
*
2x10-15 4x10-15 1x10-14 4x10-14 1x10-13 4x10-13 x
* * *
*
1x1:-14
*
*
*x1:-14
Noise increases aa input shunt capacitance increases.
RISE TIME SETTING
10 3 1 .3
* * * * * * * * *
2do-13 2d0-13 5do-13 2~0-12 5x10-12 x x 5~0-14 2do-13 ~0-13 2do-12 x
MO-12 2x10-l2 5x10-12 1x10-11
lx&
*
1x10-8 1x10-9 1.2x10-9 4x10-9 1x10-10
1.5x10-11
.l .03 .Ol
1.2x10-8 4x10-8 1x10-7
1.2x10-10 4x10-10 1x10-9
2x10-11 1x10-10 x
4x10-11
x
x x x x
1x10-B
x
9
ACCESSORIES
MODEL 427
SECTION 4.
4-l. GENERAL. be used with the Model 427 eo provide additional con­venience and versatility.
Description: The Model 1007 is a dual rack mounting kit with over-
all dimensions 3-l/2 in. (64 mm) high and 19 in. (483 mm) wide. of two Angle Brackets, one Mounting Clamp, and extra mounting BCreWS.
The following Keithley accesaaries can
Model 1007 Rack Mounring hit
The hardware included in this kit consists
ACCESSORIES
OPERATING INSTRUCTIONS. A separate Instruction
4-2.
Manual is supplied with each accessory giving complete
operating information.
Application: The Model 1007 co""erts any half-rack, style "M"
instrument from bench mounting to rack mounting in a standard 19-inch rack. for rack mounting 19-inch full rack width insfru-
ltE"tS. The Model 1007 Rack Mounting Kit can be used to m"u"t
instruments of 11 inch or 14 inch depth. should decide the position af the i"~tr"me"ts to be
rack mounted.
instruments positioned as shown and identified as instrument “A” and "B".
The Assembly Inaeructions refer co
The kit may also be used
The user
10
Parts List: Item
NO.
DWCl+ltiO” 22 Angle Bracket 23 Screw, 16-32 x
Phillips Pa" Hd 24 Mounting Clamp 25 Screw, %6-32 x
Phillips Pa" Hd 26 Kep Nut 116-32
27 Screw, 116-32 X
Phillips Pa" Hd
28 Screw, 116-32 x
Phillips Pa" Hd
5/8,
1,
l/2,
718,
VY
Keq'd
2 6
1 247988 1
3
2
1
Keithley Part No.
27410B
-_
__
_-
__
__
0877
MODEL 427
Assembly Instructions:
ACCESSORIES
Model 1007 Dual Rack MountinS Kit
1. Before assembling the rack kit, determine the
pasition of each instrwnent. Since the inserumenfs can be mounted in either location, their position should be determined by the user’s meas”rement. The
following instructions refer to instruments “n” and
UB”
positio”ed as shorvn. For mounfinS 19-inch full
rack Width instruments, disregard steps 2 through 5.
2. Once the position of each instrument has been determined, ebe “side dress” panels on both sides of each instrument should be removed. Renxwal is accomplished by looseninS the screwy (Item 8, oriS­inal hardware) in two places. Slide the “side dress” panels co the rear of the instrument to remove.
3. The mountinS clamp is installed on instrument “A” using the oriSina1 hardware (Item 8). With the screws removed, insert the “mounting clamp” behind the “corner bracket” (Item 7) and replace the screws to hold the mounting clamp in place.
4. Tighten the screwy (Item 8) on instrument “B”.
Insert the “mounting clamp” behind the “corner
bracket” (Item 7) an instrument “8” a8 shown.
5. When mounting instruments having the same depth, a screw (Item 25) and kep nut (Item 26) are required to secure the two instruments together. When ,,,oune­ing instruments of different depth, da not use kep
nut (Item 26) but substitute shorter screw (Item 28).
6. Attach an “anSle bracket” (Item 22) on each instrument using hardware (Item 23) in place of the original hardware (Item 8). For 14 in. long instru-
ments use 116-32 x 518 Phillips screw (Item 23) with
116-32 kep “uf (Item 26).
7. The bottom cover feet and tilt bail assemblies
may be removed if necessary.
8. The original hardware, side dress panels, feet and tilt bail assemblies should be retained for fut-
ure conversion back to bench mountine.
0777
11
CIRCUIT DESCRIPTION
MODEL 427
SECTION 6. CIRCUIT DESCRIPTION
5-1.
GENERAL.
beck amplifier, e X10 gain filter section, suppression .“d power supply circuits ee show” in Figure 12. The
feedback emplifier is located an the “Amplifier Beerd”, PC-289.
Board”, PC-291, PC-292.
located on the “Mother Board”, PC-290. justment. Resistor R307 serves as a current limit de-
5-2. fier is composed of e high-gain amplifier connected ee e feedback emmeter. R227 are set by the GAIN Switch (SZOl). The high-gain emplffier is composed of a dual FET input stage (Q20IA end B), e differential amplifier (QAZOl), end en output stage (9203 end Q204). resistor R201 to the cutput stage et Q203 end Q204. Potentiometers R232, R233, and R234 ere internal fre­quency compensetion controls for leg, lOlo, end 1011 gains respectively.
AD., cantrol.
emplifier is 1 volt.
5-3. of e high-gain amplifier connected aa e 12 dB/octave
low pass filter es sham in Figure 13. The amplifier
consists of intel(rated circuit QAlOl end ~“tp”t stege
(QlOl end Q102).­The gain is established et X10 by resistors RllO end R112 + R113. adjustment.
adjustment.
The filter circuitry is located on the “Pilter
FEEDBACK AMPLIFIER (PC-289). The feedback empli-
PILTBR (PC-292).
The Made1 427 is composed of a feed-
The power supply circuitry is alit. Potentiometer R304 is a” internal voltage ed-
The feedbeck resietors R22o through
The feedback is connected from
Potentiometer R235 is the ZBRO
The full scale output of the feedback
The filter circuit ie composed
Full scale output ie 10 ;olts. -
Potentilnwtel: RlOS is en internal zero
Potentiometer R113 is en interns1 gain
a. +15 ” Reguletor.
secondary of transformer T301. The ec ia rectified by
P full-weve bridge rectifier (D301). Trensistor Q301
is the series pees reguletor. Integrated circuit
301 is . self-conteined reference end regulating cir-
vice.
b. -15 ” Regulator.
secondary of trenaformer T301. The ec is rectified by
P full-wave bridge rectifier (D302). Trensietee Q302
is the series pees reguletor. 302 is e self-contained reference end regulating cir-
cuit. Potentiometer R309 is en internal voltage ad-
,ustment.
vice.
5-5.
suppression is applied et the input es show” in Figure
15. suppression in decade steps from lo-3 te lo-lo *Slp.3=.3*
(Resistors R325 through R332). Potentiometer R333 is
the FINE Control which provides adjustment frnn 0 to
1.5 times the WAX setting. Switch S304 eete the pol­arity (either + end - 15 volt eource). Current sup­presaionis e function of V,,&S,
where “cS = Voltage et the wiper of R333.
Exemple: If MAX AMPEP.Rs = 10-b
Resistor R307 mrves as a current limit de-
CURRKNT SUPPRESSION CIRCUITRY (PC-290). The
The N&X AMPERES Switch (5303) sets the current
IQS = Series Resistor (R325 through R332).
AC power ia tapped from one
QA
AC power is tapped from one
Integrated circuit QA-
--
POWER S"PPLY (E-290).
5-4.
+15 V dc et up to 70 mA for the amplifier circuits.
The regulator circuits ere composed of identicel cam­ponents end are connected ee shown in Figure 14.
The pewer supply provides
GAIN
III
r-5
I I
2!5
SUPPRESSION
FIGURE 12. Block die‘rr of l hi‘h-‘peed current l mplifier
12
end if “cS = cl5 ”
the* Its = +15v = +1.5 x 10-G amperes
107n
RISE TIME
FILTER
0471
Cl01
I,
RIOI
r--------1
0
RI16
0471
FIGURE 16.
component Layout - PC-291.
13
COMI
14
1
FIGURE 17.
Component Layout - PC-290.
MODEL 427
COMPONENT LAYOUTS
?
FTGURE 18.
component Layout - PC-289.
FIGURE 19.
component Layout - PC-292.
0471
15
COMFUNENT L4YOoTS
MODEL 427
PC-290
16
FIGURE 20.
Chaaais - Top View.
0471
MODEL 427
SECTION 6.
REPLACEABLE PARTS LIST: This section contains
6-l.
a list of components used in this instr"ment for user reference. individual parts giving Circuit Designation, Descrip­tion, Suggested Manufacturer (Code Number), Manufac-
A Cb"ar
cem cefr* Ceramic Tubular Cer Trimmer ceramic Trin!mer camp Composition
DCb twsig.
EAL ETB ETT
The Replaceable Parts List describes the applicable. The complete name and address of each
Abbreviations and Symbols
ampere Carbon Variable
ceramic Disc
Deposited Carbon
Designation
Electrolytic, Aluminum Elecrrolytic, Tubular
Electrolytic, Tantalum
REPLACEABLE PARTS
F Fig
GCb k
I-I
M Mfr. MeF Metal Film
MY NO.
turer's Part Number, and the Keithley Part Number Also included is a Figure Reference Number where
Manufacturer is listed in the CODE-TO-NAME Listing
following the parts list.
TABLE 6-l.
farad n ohm Figure
Glass enclosed Carbon Printed Circuit
kilo (103) micro ~~~ (106)
Manufacturer Mylar w watt Number
(10-6)
&
P0ly Polystyrene Ref. TCU v volt
w/l WW"ar
pica (10-12)
Keference Tinner Copperweld
WiR?WO"nd Wirewound Variable
6-2. ELECTRICAL SCHEMATICS AND DIAGRAMS. Schematics and diagrams are included to describe the electrical circuits as discussed in Section 5. Table 6-2 idenc-
ifies all schematic part numbers included.
HOW TO USE THE REPLACEABLE PARTS LIST. This
6-3. Parts List is arranged such that the individual types of components are listed in alphabetical order. Main
Chassis parts are listed followed by printed circuit boards and other subassemblies.
NOW TO ORDER PARTS.
6-4.
a. Replaceable parts may be ordered through the
Electrical Schematics and Diagrams
Description Schematic
Amplifier iloard Mother Board (Power Supply) Filter Board
TABLE 6-2.
Sales Service Department, Keithley Instruments, Inc. or your nearest Keithley representative.
b. When ordering parts, include the following in-
formation.
1. Instrument Model Number
2. Instrument Serial Number
3. Part Description
4. Schematic Circuit Designation
5. Keirhley Part Number
C, All parts listed are maintained in Keithley Spare Parts Stock. Any part not listed can be made available upon request. Parts identified by the
Keitbley Manufacturing Code Number 80164 should be
ordered directly from Keithley Instruments, Inc.
I
PC-289 247660 PC-290 247680
PC-291, PC-292 247671)
0471
17
REPLACEABLE PARTS
MODEL 627
TABLE 6-3.
PC Board Designation series
I
Itern NO.
10 11
12 13
14
15
16 17 18 19
20
1
100 Filter Circuit
100 Filter Circuit 200 Amplifier 300 Power Supply 300 SuppressFan circuit 300 Overload Circuit
Chassis Assembly
Front Panel Assembly 1 2
3 4 5 6
7 8 9
\
Front Panel
Screw, Slotted, 6-32 x 318
Front Panel Overlay Rear Panel Side Exerusion Left Side Extrusion Right corner Bracket Screw, Socket, 6-32 x 114 Screw, Phillips, 6-32 x l/4 Clip for Side Dress Side Dress Panel
Tap Cover Assembly
Top CO"er Screw, Socket, 6-32 x 5116
Bottom Cover Assembly 24763B
Bottom cover Screw, Socket, 6-32 x 5/16 Feet Assembly
Feet
Ball
Tilt Bail
Screw, Phillips, 6-32
Kep Nut, 6-32
f,k -\U'&
TABLE 6-4.
Mechanical Parts Lise
Qty. Per Assembly Keithley Part No. Figure NC
PC-291 PC-292 PC-289 PC-290 PC-290 PC-290
1 4
1 1
1 1 2 4 4 2 2
1 4
1 4
4 4
1 4 4
247566 24758B
247608 24754C 24754C 247458
FA-101 24755B
24732C
2473X
243228 FE-6 171478
20 20 21
23 23 23
21
22
18
WARNING
Using a Line Power Cord other than the one suppLied
with your
shock hazard. damaged, replace only
instrument
If the Line Power cord is lost or
may result in an electrical
with
Keithley Part No. CO-7.
0878
MODEL 427
REPLACEABLE PARTS
0471
FIGURE 21. Chassis Assembly-Exploded View.
FIGURE 22.
Bottom Cover Assemblv.
REPLACEABLE PARTS
HOOEL 427
circuit Ilesig. Value
Cl01
Cl02 680 ;i Cl03 Cl04 6800 pF Cl05 .022 @
Cl06 Cl07 Cl08 c109* c110*
Cl11 Cl12
c115*
Cl16 .033 Cl17 Cl18 .33 c119s 1 c120* 3.3
150 oF
.0022 p
.068 uF
.22
'b
.68 p
2.2 pP
6.8 @ 68 pF
330 DF
.Ol
.l
Rating
-
500 v 500 " 500 v 500 v 200 "
100 " MY 200 v MY 200 v MY 200 v MY 200 v MY
500 v P0ly 500 v Poly 500 " Poly 500 " Poly 200 " Poly
100 v MY 200 v MY 200 v MY 200 " MY
200 v
\
("100" SERIES, PC-291*, PC-292)
P0ly Poly Poly POlY Poly
MY
FILTER BOARD
CAPACITORS
Mfr. Mfr. Code msig.
71590 71590 71590 71590 84171
88480 13050 13050 13050 97419
71590
71590 CPR-330.1 71590
71590 84171
88480
13050
13050
13050
13050
CPR-15OJ CPR-68OJ CPR-22OOJ, CPR-68OOJ 2PJ-223G
~FR-683-1E WA-.22j,F SMlA-.68,,F SMlA-2.2,,F M2WF-6.LQF
CPR-68J CPR-1OOOJ
CPR-3300J 2PJ-10x
3FR-333-1E SMlA-.lPF SMlA-.33pF SMlA-1pF SMlA-3.3,~F
Keithley Fig.
Pat-e No. Ref.
C138-15OP C138-68OP 19 C138-.0022M 19 C138-68OOP 19 C108-.022M 19
C146-.068M 19 C47-.22M C47-.68M C47-2.m C203-6.&I
C138-68P 19 C138-33OP 19 C138-.OOlM 19 C138-.0033M 19 C108-.OlM 16
C146-.033M 19 C47-.lM C47-.33M 19 C47-1M C47-3.3M
19
19 19
16 16
19 16
16
Cl21 5 Cl22 5 Cl23 33 Cl24 100
CiX”it ”
“C3l.g.
no1 connector, lo-Pin, Mini-w
QAlOl Integrated Circuit
0101 Diode, Rectifier
0102 Diode, Rectifier QlOl Transistor Q102 Transistor
SlOl Switch, Rotary, RISE TIME
5102 Connector, BNC, UG1094A/U _- Cap, BNC, mates with 5102
Value Rating
RlOl 7.78 kn I%, l/8 w
R102 8.41 kn l%, l/8 W
R103 51.7 kn l%, l/8 w RlO4 51.7 kR 1%, l/8 w R105 10 kn l%, l/8 w
1000 " CerIl 1000 " CerD 1000 " CerD 100 " &lZIl
Type
Type MfF
MtF MtF MCF MtF
72982 72982 72982
72982
MISCELLANEOUS
Mfr.
code 22526
12040 01295
01295 04713 04713
80164 02660
RESISTORS
Mfr. Mfr. Code Desig.
07716 07716 07716 07716 07716
m-050 C64-SF 19 m-050 DD-330 m-101
Mfr.
Lhsig. 20052
LM301AN
lN914
lN914 2N3903 2N3905
SW33S 31-2221
CEA-7.78KG R88-7.78k CEA-8.41~Jl R88-8.41k
cm-51.7m R88-51.7k CEA-51.7UJ R88-51.7k CEA-lO* R88-10k
C64-5P C64-33P C64-1OOP 19
Keithley
Part No.
CS-237 IC-24 RF-28 RF-28 TG-49 TG-53
;;r;g CAP-18
Keiehley Part No. Ref.
19 19
Fig.
Ref. 19
19 19 19 19 19
19
Fig.
19 19 19 19 19
3
20 1072
FlLTER BOARD (cont'd)
RESISTOR8 (cont'd)
Value 1
R106 RIO, R108 R109 RllO
Rlll 10%. l/4 w
C203 C204 C205
kfl l%, l/8 w
1
kil
200 n
61.9 kS 2 kn 10 kn 470 !?
1.8 kfl
10 k0 470 R 200 iz
10 kR
RCltF"g Type
1%, 1/B w
75 w :l%, l/2 w .l%, 112 w
.l%, l/E w .75 w
l%, l/8 W 10%, l/4 w
1%, l/8 w 1%. l/8 w lo%, l/8 W l%, l/8 W l%, l/8 W RI20
1000 v 1000 " 600 V
1000 " 200 v
Mfr., Code
MtF MCF Camp MCF
MtF
camp
MCF
camp
MtF
camp
MU MU
camp MtF Ml3
‘WPLIFIER BOARD
("200" SERIES, E-289)
CerD 72982 &l-D 72982 &t-T 71590 cem 72982
MY
07716 07716 80294 91637 91637
44655 91637 80294 07716 44655
07716 07716 44655 07716
07716
CAPACITORS ( * Located on Switch S201. )
Mfr.
13050
Mfr. Keithley Desig. i'art NO.
CF.&-lkn CEA-lkS2
3009P-200 Km-Ml MFF-536R
RCO7-102 MFF-61.9kR
3009P-2k CPA-l.Okn KC07-471
CEA-1.RkR CEA-IOkR RC07-471 CEA-200n CEA-1Okn
Mfr. Keithley
loss-D22 801000X5F0102~ C64-.OOlM
TCZ-1R5
801000~5~0102~ C64-.ool~ SM2‘+.047IJF
R88-lk 19 R88-lk 19 RP-89-200 19 R169-1M 19 R168-536k 19
R76-lk 19 R168-61.9k 19 K-89-211 19 R88-10k 19 ,176.470 19
R88-L.8k 19 R88-1Ok 19
R76-470 19 R88-200 19 R88-IOk 19
C22-.0022M
c77-1.5P C143-.047M
Fig. Ref.
Pig.
18 18 18 18 18
C206 C207 C208 C209 c210
.047 p
470 pF
.0022 UF ,001 b
10 ilF
,001 LP 1000 72982
10
iJ.F
.OOl UF
.oo47 ilF*" .0047 IiF
470 pF *C217 *C218
C219 c220 cG-5 c221
c222 C223 C224
**Nominal Value, Selected in Factory Test
47 pF
5
PF
1.5 DF
1.5 6F 600 " ,033 pF 100 " .OOl UF .0033 !,F .0033 5
200 " 1000 v
1000 v 1000
20 "
20 v 1000 v
200 v
1.000 v
500 " * C216 500 v 200 v 600 v
1000 " 1000
1000 v
MY
CerD
13050 72982
72982 17554
17554
72982 97419 56289
71590 71590 00686 71590 71590 88480 72982
56289 56289
SMZA-.047PF
00471
loss-"22 801000X5F0102K
TSDl-20-low 801000X5F0102K
TSDI-20-10°F 8omoox5Foio2K C64-.OOlM
loss-D47
TCZ-IRS
3FR333-1E 801000X5F0102~ 1oss-033 loss-D33
C143-.047M 18 C64-47OP 18 C22-.0022M 18 C64-.OOlM 18 C179-10M 18
C64-.OOlM 18 C179-LOM 18
C66-.0047M** C22-.0047M 20
wp c a-~w-r~s,fy C146-.003M 18 C64-.OOlM 18
C22-.0033M 18
C22-.0033M 18
18 20
1075
21
FiXPLACEABLE PARTS
MODEL 427
AMPLIFIER BOARD (cont'd)
CirCUit Desig.
D201
0202 D203
D204 D205
D206 D207 D208
D209 D2lO
QA201 wegrated Circuit, Operational Amplifier
s201 5201 5202
Type
Special Special Silicon, NPN, case TO-106 Silicon, NPN, case TO-106
SilkOn Silicon SiliCOtl Silicon
Type
Switch, Rotary, GAIN Not Used Receptacle, BNC (UG1094AfU)
DIODES
Mfr.
Code 80164
80164 07263 07263
01295
01295 01295 01295 01295 01295
MISCELLANEOUS
Mfr. Mfr. Keithley Fig.
Code tlesig. Pare NO. Ref.
07263 80164
02660
RESISTORS ( * Located on Switch 5201. )
Mfr. msiu.
.?&5sk
2133565 2N3565 lN645
lN645 lN914 lN914 lN914 lN914
@715C SW-337
31-2221
Keithley
Part NO. Ref.
-2245&A .2&l\;' (*‘4 18 TG-39
TG-39
RF-14 18 RF-14 18
RF-28 18 RF-28 18 RF-28 18 RF-28 18
IC-26 Jk: ;::c;,d 18 SW-337 ? ,~> 18
cs-249
Fig.
1 S Z2&55A ;> fj 3 :I ,~ c:Jj 18 18
18 18
R201 R202 R203 R204 R205
R206 R207
R208 R209 R210 499 n
R211 499 n R212 10 R 8213 470 n R214 10 kn R215 470 n
R216
R217 * R218 270 kn * R219 *R220
* R221 "R222 9~ R223
R224 R225 108 n
10 n 1 MCI
100 kR
23.2 k0
22.1 k0 10 ki? l%, 118 W
18.2 kn l%, l/2 w MtF 10 kfi l%, l/S w MtF 07716
12.1 kO l%, l/8 W MtF
10 n 10 D
100 n
900 a
10 kn 100 kR 1 wl 10 MS?
Mfr. Code Desig. Part No. Ref.
lo%, l/4 w lo%, l/2 w I%, l/8 W l%, l/8 W ix, 118 w
l%, l/S w MtF 07716 l%, l/8 W
l%, l/S w lO%, l/4 w l%, l/S w IO%, l/4 w
10%. l/4 w lO%, l/4 w lO%, l/2 w
l%, l/2 w l%, l/2 w
l%, l/2 w l%, l/2 w l%, l/2 w 1%,1 w 1%,2 w
corn; MtF MW
MtF MM 07716
MtF MtF
COmp '44655 Camp 44655 camp
Mm 07716
DCb 91637
MtF 07716 CEC-1OM
MtF 07716 Mm 07716 DCb 91637 DCb 91637
44655 01121 07716 07716 07716
07716 07716
07716 07716
44655 07716 44655
01121
Mfr.
RC07 R76-10 18 EB-lM CBA-lOOki? R88-100k CF,A-23.2kn
CEA-22.lkn CEA-1OM R88-10k 18
CEC-18.2kQ R94-18.2k 18 CEA-lOkS1 R88-10k CBA-12.lka R88-12.lk CEA-4990
CEA-499n CEA-lOS2 RC07-471 CEA-low2
RC07-471
RC07-100 R76-10 18 RC07-100 EB-270kR CEC-loon DCF-l/2-90Ofi
CEC-100kn CEC-lMn DC-l-lOM0 DC-2-1oSn
Keitbley Fig.
RI-1M R88-23.2k 18
R88-22.lk 18
RS8-+,9- 3-01Lc
R88-449 RSS-10
R76-470 18 RSS-10k 18 R76-470 18
R76-10 18 Rl-270k 20 R94-100 20 812-900
R94-10k R94-100k
301&
18
18
18 :i
18 18
20
20 26
22
1072'
MODEL 427
REPLACEABLE PARTS
AMPLIFIER BOARD (cont'd)
RESISTORS (cont'd)
Value Rating Type
R226 R227 R228 R229 R230 220 kn
R231 330 kfi R232 100 kR R233 R234 R235 500 n
h~ominal value, selected in test.
circuit iksig. Type
Q201 Q202 Q203 Q204
*Selected X-70
109 n GCb 1010 n : GCb
*15 R
10 kn
10%. l/4" camp 10%. 114 w lo%, l/4 w corn;
lo%, l/4 w
l/2
1 Mn
1
MCI
Dual, PET, case TO-71 Silicon. NPN, Case TO-92
Silicon, NPN, Case TO-92
PNP. Case TO-92
112
,,,,,,,,m;,,. E
112
Mfr. mr* Keiehley Code Llesig. Part NO.
63060 63060
ComJ
camp
MOTHER BOARD PARTS LIST
("300" SERIES, PC-290)
44655 44655 44655
44655 RC07-334
80294
80294 3068P-Df 80294 3068%1M
llelipot
TRANSISTORS
Mfr. Mfr. Code
80164 2N5452 04713 2N5089­04713 2N3903 04713
CAPACITORS
Fig. Ref.
9 g::::;10 x07-150
RC07-103 R76-10k 18 RC07-224
3068P-100k
77PF.500
Lksig. Part No.
2N3905
RZO-109 R*l-rb20 R20-10lC$3~5-,&0 R76-15
X76-220k 18 R76-330k
RP89-10Ok RP89-lM RP89-1M
RP-64-500
Keithley
25099.4" 'X-62 18 w-49 18 z-53 18
18
18 18 18 18
Fig.
Ref. 18
Value Rating Type
c301 C302 200 fl c303 c304 c305
C306 c307 C308 c309 c310
C311 C312 c313 c314 c315
D301 Four Wade Bridge 83701 m-10 RF-36 17 D302 Four Diode Bridge 83701 PD-10 RF-36 D303 Silicon 01295 lN645 RF-14 17
0304 Not Used __ __ __ -­0305 Silicon 01295 lN914 RF-28 17
200 p
10 llF 10 @
2200pF 200 p
200 UF
10 GF
2200PF
10 fl
200 p 10 UF
.47 pE
10 P O.Ol!JF
35 " 35 v 20 " 20 v
1000 ”
35 " 35 " 20 " 1000 " 20 "
35 "
20 " ETT 20 " 20 "
500 "
EAL EAL ETT ETT CC?!2D
EAL EAL ETT CerD ETT
EAL 90201
Mfr. Code i%sig. Part NO.
90201 90201 17554 17554 72982
90201 MTV-200UF C177-200M 90201 MT"-200!JF C177-200M 17554 TSDl-zo-10UF C179-10M 72982 17554
17554
Mfr.
Mfr. Keiehley
MT”-200m MT”-ZOO!JF
TSD1-20-10pF TSDI-zo-IO&IF m-222
DD-222 TSD~-20-10uF C179-10M
MTV-200m
TSDl-ZO-10pF
Tml-20-.47UF TSDl-20-lO!JF
871-25u0-103M
C177-ZOOM C177-200M C179-10M C179-10M C64-2200P
C64-2200~
C177-200M
C179-10M
C179-.47M C179-10M
C22-.OlM
Keithley
Fig. Ref.
17 17 17
17 17 17
::
Fig.
17
REPLACEABLE PARTS
MOTHER BOARD (cont'd)
DIODES (cont'd)
MODEL 427
Cit-CUit rlesig.
D308 0309 D310 0311 0312 Silicon
5301
5307.
QA301
QA302 QA303
5301 S302
5303 Q301
4302 Q303
5304 F301 F301 T301 P305
__ DS-301
DS-302
CirCUFt Llesig. Rating Type
Type
Silicon SiliCOll Silicon
Silicon 01295
Type
Connector, Mini-P" connector, Mini-P" Integrated Circuit, Voltage Regulator 07263 Integrated Circuit, Voltage Regulator 07263 LEA7723393 IC-25
Integrated Circuit Switch, Line Voltage Switch, "PUSH ON" Power with lamp Switch, CURRENT SUPPRESS 80164 SW-339 SW-339
Transistor Transiseor Transistor, Switch, POLARITY Fuse, 117", .25A, Slo-Blo, 3 AG Fuse, 234", 1/8A, Slo-Ho, 3 AG Transformer Receptacle, AC
Line cord, mates with P305 Pilot lamp, neon (replacement far 5302)
Pilot Lamp, O"~RLOAD
Value
Silicon, NPN, TO-92 case
iESISTORS (*Located on Switch S303.)
Mfr. Code
01295 01295 01295
01295 lN914
MISCELLANEOUS
Mfr. Mfr. Code
22526 47439 22526 47439
07263 A749C 80164 SW-318 80164
02735 40312 02735 40312
04713 80164 SW-236
75915 313.250 71400 MDL
80164 TR-138 82389 AC3G 70903 17258-S co-7 08806 07294 CF03ACS1869
Mfr. Code
Mfr. rJesig.
lN914 lN914 lN914
lN645 RF-14
Desig.
UGA7723393
PBL-5-BSA3C7A SW-340 3
2N3903 TG-49 17
C/A(N&2P) PL-58
Mfr. Keithley
LkSiE. Pat-t NO.
Ketthley Part No.
RF-28 RF-28 RF-28
RF-28
Keiehley
Part NO. CS-236
CS-236 IC-25
x-27 17 SW-318 3
TG-54 17 w-54 17
SW-236 3 F"-17 3 F"-20 3 TR-138 20 CS-235 3
PL-51
Fig. Ref.
17 17 17
17
__
Fig. Ref.
17 17 17 17
‘20
-_
FFg.
Ref.
2
R301 R302 R303 R304 R305
R306 R307
R308
R309
R310 R311
R312 R313 R314 R315
R316 R317 R318 R319 R320
R321 R322 R323 R324
hR325 10 kn
634 0
8.2 a
1.37 kfi 200 0.
1.24 kfi 634 R
8.2 n
1.37 kn 200 a
1.24 k.Q
9.09 kfl 14 kn 1 kR 10 n 1 kfl
9.09 kR 1 kfl 1 kR 14 kn 10 R
10 kn 10 kfi 330 R 47 kfl
l%, l/8 w 5%, l/2 w 1%, l/8 w
0.5 w
ix, ua w
1%. l/8 W: 5%, l/2 w l%, l/8 w
0.5 l%, l/8 w
l%, l/8 w l%, l/S W
W
I%, ifa w
lO%, l/4 w l%, l/8 w
l%, l/8 " l%, l/8 w l%, l/8 w l%, l/8 W lO%, l/4 "
COmp MtF
MtF MtF
COtlIp MtF
MtF MtF
MtF 07716
MtF
CO*p 44655
MtF 07716
MCF MtF MtF MtF
07716 CEA-634n R88-634 17 01121 07716 80294 07716
07716 01121 07716 80294
07716 07716 07716
07716 07716 07716 07716 44655
44655 44655 44655 44655 x07-473 R76-47k 07716
EB-8.2sl
CEA-1.37kn
3329P-200
CEA-l.lkO CEA-634n
m-8.2$? CEA-1.37kR 3329P-200 CEA-l.lkR
CEA-9.09kn CEA-14kfi CERlkR RC07-100 CEA-lkn
CEA-9.09kn CFA-1kR CBA-1kR CEA-14kn a07-100
RC07-103 R76-10k RC07-103 x07-331
CEC -1Okfl
R19-8.2 R88-1.37k RP-88-200
Rae-l.24 17 R88-634
R19-8.2 R88-1.371 RP-98-200 ~88-1.24
R88-9.09k R88-14k R88-lk R76-10 R88-lk
,R88-9.09k
RBB-lk R88-lk R88-14k R76-10
R76-10k R76-330
R94-1Ok
17 17 17
17 17 17 17 17
17 17
17
I 17
17 17
17 17 17 17
17 17 17 1Y
20
24
0574
MODEL 427
REPUCEABLE PARTS
MOTHER BOARD (cont'd)
RESISTORS (cont'd)
circuit lksig.
Value Rating
100 kn
1 10 Mn l%, 1 w DCb 100 MO DCb 109
hR331 *R332
F.333 10 k0 R334
R335
1010 R CCb 63060 Rx-l-101On 1011
33 kn
68 kSI
Mfr.
Type
l%, l/2 " MtF
Mn
n GCb
il GCb 63060 Rx-l-1olln
l%, l/2 w 1%,2 w
2 W ww 12697 62JA-10kiI RP-YZ-10k
lO%, l/2 w
lO%, l/4 w C0mp
MtF
Camp
Code
01121 44655
Mfr. Desig.
CEOlOOI& R94-look 20 CEOM-i DC-l-1OMn DC-2-100Mo Rx-l-1090
EB-33kn
RC07-683 R76-6Sk
Keithley
Part No.
R94-1M
-to
.rw-dl pw3~-@620
Rl- 33k
f$e~-/“G
Fig.
Ref.
2.
17
17
__
1176
25
SECTION 7. CALIBRATION
MODEL 427
GENERAI..
7-1. checking the instrument to verify operation within specifications. The procedures and adjustments should be performed in the exact sequence given to obtain satisfactory results.
7-2. TEST EQUIPMENT. in Table 7-1.
tuced provided the accuracy tolerances are equal to or
better than the equipment specified.
The Suppression Max. Amperes switch will be left in the E posirion unless stated otherwise.
PKOCED”RES .
7-3.
a. Preliminary Calibration.
1. Power Supplies.
a).
point and chassis and adjust the f15 volt poten-
tiometer R309 for +15 Volts t10 "". "Sing the oscilloscope check for less than 1 m" peak-to­peak ripple.
b). Connect Model 163 between the -15 volt test
point and chassis and adjust the -15 volt poten-
tiometer R304 for -15 volts ?lO mV. Check for less
than 1 mV peak-to-peak ripple.
This section contains procedurea for
Use the test equipment specified
Equivalent instruments may be substi-
NOTE
Connect Model 163 between the +15 volt test
2. Line Regulation. Plug the Model 427 line cord in to a "ariac
a).
with Line Monitor.
Check the il5 volt supplies with the "ariac
b).
adjusted for 90 and 125 volts. The voltages should
be i-15V +20 m" with less than 1 mV peak-to-peak
ripple.
3. 234 Volt Operation. Set the 117-234 volt switch to the 234
a).
volt position and plug the 42, line cord into the
234 volt line.
b). Check the 215 volt supplies. They should
read i15 volts ?1O mV with less than 1 mV peak-
to-peak ripple.
4. Overload Circuit Check. Connect Model 163 to the Model 427 output.
a) f
Set the Model 163 to the 10 volt range.
Set the Model 427 controls as fallows:
b).
GAlN : 106 "olts/amperes
SUPPRESSION: (-1 10-5 amperes
RlSE TIME: 300 Ins
c). Turn the Suppression Fine control to obtain
a reading of approximately t9.5 V on the Model
163.
The Model 427 overload light should be off.
1nStr”ment Type
I-
Picoampere source Digital Voltmeter
Oscilloscope Function Generator Microvolt-*meter Variable Transformer Line Voltage Monitor True RMS "TVM
26
TABLE 7-l.
Test Equipment
Specification 10-14
to 1.1 x lo-4A
il uv to lOOOV, 0.1% of reading
__
-_
-11
_-
10
to 10-l*
10 "V fO lOOOV, 90-140V rms, 50-60 Hz 90-140V rms, X-60 Hz
Mfr. and Model No.
Keithley, Model 261 Keithley,,,~Model 163 Tektronix, Mod'+,~~ or 5618 ,,~ Wavetek, Model 111 or 130 Keithleiy, Model l?i variac ',l_
--
Ballantine, Model 320
~/,'
-I
1072
MODEL 427
CALIBRATION
d). Slovly t”rn the Suppression Fine control CW until the overload light comes on. ~,,is should occur between +10 and +11 volts.
e). Set the Model 427 Suppression Polarity switch ta (+) and repeat steps & and c, Readings on the DVM will now be negative.
5. current Amplifier Zero.
a). Set the Model 427 gain switch to zero check,
suppression to E and Rise Time to 30” ms.
b). Turn the 427 front panel zero control ccw until overload light comes an. Then very slowly turn the zero control cw until light goes off. C”“ti”“e turning c0*tr01 cw until light comes on again. Then slowly turn control ccw and set in region where overload light stays off.
6. Filter Amplifier Zero and Gain.
a). Set the Model 427 gain to lo4 V/A and Rise Time to 300 me. Connect the Model 163 DW to the Model 427 output. Set the Filter Amplifier zero pot (F.108) for 0 ilm” at the Model 427 output.
Set the 427 Gain to lo5 V/A and cmmect a
b). DVM (1V range) to the OUtPUt Of the first stage amp­lifier (QA201, Q203, 4204) at location on PC-290
(mother baard) at jumper found directly below pot-
entiometers R232 and R233.
set the Suppression to
10” amperes and adjust the front mnel pot R333 for
a reading of l.OOOV.
connect DVM (1OV range) CO output of 427 and adjust Filter Amplifier gain pot (R113) for a reading of 10.00 volts.
Set the Model 261 to N6 ampere and the
a).
Model 427 gain to 10’ V/A and connect the test
set up as shown in Figure 23 using a BNC TEE
connector on the Model 427 input.
b). With no input connected set up, the Model 153 for CENTER ZERO and VOLT K-21%. Zero on the 100 pV range then set the range to 1. mV.
c). >ir&t$ Model 261 output OFF increase
the -1 153 $ensftivity to 300 v” range while
mai”camCig~ a “0” Indication on the Model 153
using the Model 427 front panel zero control. Correct drift with the Model 427 zero co”trol as
needed during checks.
d). Switch the Model 261 between OFF and (+)
,..~as\p,eeded to obtain a steady reading on the Model
! 153.’ me reading should be leSS tha
P-
300 pv.,
e). Repeat step $ but witch befw:&,FF~%“d (-) on tiy Model 261. The reading should be less thqh +300 u”. Re-zero the Model 427.
0877
FIGURE 23.
Measurement of Input Voltage Drop.
27
CALIBRATION
MODEL 427
TABLE 7-2.
427
GAIN V/A RISE TINE FREQUENCY
11
;;10 109
108 107 106 105 104
8. Amplifier Rise Time. Connect Function Generator to the Model
a). 427 input and connect the Model 427 rear panel output t" the Oscilloscope Using the test set up shar" in Figure 24.
Adjust the 10' through 1011
b). the specified 10% to 90% rise time using the tri­angular wave frequency and adjustment listed in the table. Adlust the Function Generator as
needed to obtain a 10 volt peak-to-peak output
from the Model 427.
rangea for the specified rise times. There should be no overshoot on any of the ranges.
Check the 10 through lOti
427 WAVETEK
1.0 ms 100 Hz .3 me 500 Hz .l ma
.03 ma 2 kHz .03 me 10 kHz .Ol m 10 kliz .Ol me 10 kH* .Ol r@E 10 kliz
ranges within
1 kHz
MAX 10-90x
RISE TIME
1.50 "Is Slider 6 Pot
0.40 m
0.22 la8 Pot
0.60 me None
0.40 me
0.015 Ins NO"=
0.015 ms Ncme
0.015 ms NO"=
9. Amplifier Noise.
a) .
427 input high end ground.
rear panel output and check the Model 427 BMS output noise for all settings in Table 7~3.
10. Filter Rise Time.
Connect B 1OOpF capacitor between Model
Connect the TRMS VTVM to the Model 427
b).
Set the oscilloscope controls as follows:
4. VERTICAL INPUT: ZV/Di".
COUPLING: DC' TRIGGER: COGPLING: AC
Ext.
RISE TIME
ADJUSTMENT
Slider 6 pot
NO"=
Shielded
/
- r ,I,,,1 PUNCTION GENERATOR
- L-- J
GAIN V/A
(427)
11
;;10 109
1oS 107 106 105 104
i
, CAPA
_ I
I ,
FIGURE 24. Measurement of Rise Time,
TABLE 7-3.
RISE TIME
(427) T
1.0 ms .3 In*
.l ms .03 me .03 me
.Ol ma .Ol ma .Ol m
TRUE MS
100
"I" 30 mv 10 mv 10 mv
3 mv 3 mv 3 mv 3 rev 2 mv
I I
MAX. RMS
NOISE
40 mv 20 mv 10 mv
5 mv
2 nlv 2 mv 2 mv
28
0574
>
MODEL 427
CALIBRATION
TABLE 7-4.
10 !a 10 pa
.l Ins .l nla
1 ms 1 me
10 me
1.0 tn.5
FUNCTION GENERATOR
Wavetek
Frequency
10 kHz .Ol Ins .015 In*
1 kHz .03 me .040 me
1 kHz .l In* .15 ms 100 HZ .3 me .37 ma 100 Hz 1 me 1.1 Ins
10 H7. 3 Ins 3.7 Ins
10 "7. 10 Ills 11 m
10 HZ 30 Ilie 37 me
SERIES
RESISTOR MODEL 427
1om
FIGURE 25. Measurement of Filter Rise Time.
427 Rise Time
setting
CURRENT
AMPLIFIER
Max lo-90%
OSCILLOSCOPE
RfSe Time
Set the Model 427 gain to lo4 V/A.
b).
the series resistor (104) and the square wave fre­quency listed, check the filter amplifier lo-90% rise time. as needed to obtain a 10 volt peak-to-peak ""tput from the Model 427. a combination of both should not exceed t 10%. Trigger the Oscilloscope from the Function Gen­erator sync output.
Set the Function Generator amplitude
The overshoot and dipping or
“*“etek
OSCillO*COpe
.l eec 1 HZ 100 me 110 Ins .l set 1 HZ
Frequency Setting Rise Time
L
"sing
TABLE 7-5.
the Function Generator for 1 volt out of the Model 427. below check the lo%-90% rise time of the filter
amplifier.
427 Rise Time Max lo-90%
300 tns 370 Ills
"sing the square wave frequency listed
Set the Oscilloscope for .2V/Div and set
c) .
0574
29
CALIBRATION
MODEL 427
b. Final Calibration.
1. Gain Accuracy. Connect the Model 261 Picoampere Source to
4. the input of the Model 427 and connect the Model 163 to the Model 427 output.
Tima Co"sta"t to 300 Ins.
Set the Model 163 on the 1 volt range and
b).
step the Model 261 and Model 427 through the ranges in Table 7-6. range given. age OUtpUt is negative.
261
-
2. Offset current 4. Drift.
The DVM readings must be within the
For positive current inputs the volt-
TABLE 7-6.
427 Gain
Set the Model 427
Model 163
.98V to 1.02V .98V to 1.02v .98V to 1.02v .98V to 1.02V .98V to 1.02V .98V to 1.02V .96V to 1.04V .96V to 1.04V
4.
through the positions in Table 7-7. The readings
on the Model 163 should be within the tolerance
polarity switch in the (-) position. The Model
163 readings will now be positive.
Step the Suppression and Cain switches
TABLE 7-7.
SUPPRESSION
LO-lo 10-9 10-8 lo-7 lo-6 10-z
IO-3 10
Repeat stepa a and c with the suppression
d)
-lov t10 mv
-lOV -i600 mV
-lOV i-600 mV
-10" i600 mV
-lOV t600 mV
-lOV f600 mV
-lOV C600 mV
-lov i-3 "
MODEL 163
Re-check the current amplifier and filter
a).
amplifier zero. Place a CAP-18 on the Model 427
input and sat the Model 427 Cain to 1011 V/A and
Rise Tim2 to 300 ma.
b). Connect the Model 163 to the Model 427 out-
put and set it to the 1 volt range. The reading
on the Model 163 should be less than 100 mV.
3. current suppression. a). Place a CAP-18 an the Model 427 input and
set the gain to lo11 V/A. Connect Model 163 to
the Model 427 output and set it to the 10 volt range.
Set the Model 427 Suppression switch to
b/6
lo- , set the Polarity to (+) and the Fine co"­tral to obtain a -10 volt i10 m" reading on the
Model 163.
Set the Model 427 controls as follows:
4. GAIN: LO5 V/A
SUPPRESSION: 1O-7 ampere
RISE TINE: 1 ms
POLARITY: *POLARITY is (+) for setting recorder
printer left of zero and (-) for setting printer right of zero.
Set the recorder sensitivity to 10 mV full
b).
scale and "sing the suppression FINE control set the recorder printer to a convenient spot for
recording drift of the Model 427.
After a 1 hour warm-up the Model 427
c) .
should drift no more than t500 u" (five minor divisions) in any subsequent 24 h&r period *500 lJV/"C.
(+) or c-j*
30
0574
-
I ’
/ ’ :
0
ip IT-----3-----J
A
I
I
Y
SERVICE FORM
Model No. Name
Serial No.
P-0. No. Date
Phone
Company
Address
City
State
Zip
List all control settings and describe problem.
(Attach additional sheets as necessary.)
Show a block diagram of your measurement system including all instruments connected (whether power
is turned on or not). Also describe signal source.
Where is the measurement being performed? (factory, controlled laboratory, out-of-doors, etc.) What power line voltage is used?
Frequency?
Variation?
Ambient Temperature?
OF. Rel. Humidity?
Variation?
OF.
Other?
Any additional information. (If special modifications have been made by the user, please describe below.)
*Be sure to include your name and phone number on this service form.
Addendum 29103-C-l
u/a/a3
Instruction Manual Addendum
Model 427 Current Amplifier
The following change information is provided as a supplement to thk manual in order to provide the
user with the latest improvements and changes to the manual in the least amount of time. It is recom­mended that this information be incorporated into the appropriate places in the manual immediately.
Replace the information contained in step 8, page 28, under Amplifier Rise Time, with the following procedure:
8. Amplifier Rise Time a. Connect the Function Generator to the Model 427 input and connect the Modal 427 rear panel
output to the oscilloscope using the test setup shown in Figure 24.
b. Adjust the 109 through 101’ rangas within the specified lo%-90% rise time using the triangular
wave frequency and adjustment listed in Table 7-2. Adjust the Function Generator, as needed, to
obtain a 10 Volt p-p output from the Model 427.
c. Without altering the test sat-up, verify that the 10 through to8 ranges meet the rise time
specifications in Table 7-2. Adjust the Function Generator, as required to obtain a 10 Volt p-p out-
put from the Modal 427. There should be no overshoot on any range.
d. Remove the 1OOpF capacitor from the test set-up and connect the Function Generator directly to
the Modal 427 input. Verify the 101 through 106 10% -90% rise time, using the square wave fra­quency. per Table 7-2. There should be no overshoot on any range except for the 104 V/A which should be lass than 10% overshoot.
. .
m INSTRUMENTS
Model 427 Current Amplifier Addendum
INTRODUCTION
This addendum to the Model 427 Current Amplifier Instruction Manual is being provided in order to supply you with the latest information in the least possible time. Please incorporate this information into the manual immediately.
Page 3; Note that in Figure 2 the dials on the knobs are now black.
29103-c-2 /7-90
Page 20; Replace Table with the following:
(“100” SERIES, PC-291’, PC-292)
FILTER BOARD
CAPACITORS
clrcult Deslg.
Cl01 Cl 02 68OPF 5oov Cl 03 Cl04 Cl05 Cl06 Cl07 Cl06 .66PF 2oov C109’
c110* 6.6pF 2oov Cl11 66PF Cl12 33OpF 5oov Cl13 Cl14 .0033pF 5oov Cl 15’ Cl16 Cl17 .lj~F 2oov Cl16 .33yF 2oov
Cl19’ Cl20 3.3pF Cl21 Cl 22 Cl23 33pF 1 oov Cl24 1 OOpF
Value
15OpF
.0022pF 68OOpF .022pF .066pF .22kF 2oov
2.2kF
.OOlpF .OQF
.033pF
1P
5pF 5pF
Rating 5oov
5oov 5oov 2oov 1 oov
2oov
5oov 5oov 2oov
1 oov
2oov 2oov 1 ooov 1 ooov
1 oov
Type
P0ly
Poly Poly Poly Poly
MY i;
MY MY
Poly Poly Poly Poly Poly
MY 1;
i; CerD
CerD CerD CerD
Mfr. Code
71590 CPR-IBOJ 71590 CPR-660J 71590 CPR-2200J 71590 CPR-6800J 64171 2PJ-223G
68460 3FR-663-l E
13050 SMIA-.22kF 13050 SMlA-.66pF
13050 SMIA-2.2kF 97419 M2WF-6.6pF 71590 CPR-66J 71590 CPR-330J 71590 CPR-IOOOJ 71590 CPR-3300J 64171 2PJ-103G 66480 3FR-333-l E 13050 SMIA-.lkF 13050 SMIA-.33kF 13050 SMlA-IpF 13050 SMl A-~.~FF
72962 DD-050
72962 DD-050 72962 DD-330 72962 DD-101
Mfr. Deslg.
MISCELLANEOUS
Kelthley Pall No.
Cl36-15OP Cl36-660P Cl36-.0022M ‘X38-6800P C108-.022M Cl46-.066M C47-.22mF C47-.66mF C47-2.2M C203-6.6M Cl 36.66P Cl 38-33OP Cl 36-,001 M Cl36-.0033M Cl06-.OlM ‘2146..033M
C47-.I M C47-.33M C47-1 M C47-3.3M C64-5P C64-5P C64-33P C64-IOOP
Fig. Ref.
19 19
:i 1:
19 19 16
16 19 19 19
1: 19
1:
;: ;z
19 19
Circuit Deslg.
JlOl QAIOI
DlOl
D102 a101 a102 SIOI
J102
-
Type Connector, IO-Pin, Mini-PV
Integrated Circuit
Diode, Rectifier Diode, Rectifier Transistor
Transistor
Switch, Rotary, RISE TIME Knob, Rise Time Connector, ENC. UGl094A/U
Cap, BNC, mates with J102
Clrcult Desig. Value
RI01 7.76kR R102 6.41 kn R103 RI04 51.7kn 1%. 1/6W M1F RI05 IOkn
51.7kQ
Rating
I%, 1/6W MtF I%, 1/6W MtF l%, 1/6W MtF
1-i; l/SW
Type
MtF
Mfr. code
22526 12040 01295 01295 04713 04713 60164
02660
Mfr. Code
07716 07716 07716 07716 07716
Mfr. IJesig.
20052 LM30lAN 1
N914 1 N914 2N3903
2N3905 SW-336
31-2221
Mfr. Desig.
CEA-7.76KR CEA-6.41 KR
CEA-51.7KR R66-51.7k CEA-52.7KR R66-51.7k CEA-1 Om
Kelthley Part No.
CS-237 IC-24 RF-26 RF-28 TG-49 TG-53 SW-336 KN-46 cs-249 CAP-l 6
Keithley Part No.
R66-7.76k R66-6.41 k
R66-1 Ok
Flg. Ref.
;‘z ii
19 19
19 2 3
-
Flg. Ref.
29103-c-2 /7-90
Page 22; Replace Table with the following:
AMPLIFIER BOARD (cont’d)
DIODES
Circuit Deslg.
D201 D202 D203 D204 D205 D206 D207 D208 D209 D210
Type
Special Special Silicon, NPN, Case TO-106 Silicon, NPN, Case
Silicon Silicon Silicon Silicon
k
80164 80164 07263 07263 01295 01295 01295 01295
01295
01295 1 N914
Mfr. Desig.
24555A 24555A 2N3565 2N3565
1 N645 1 N645 1 N914 IN914 1 N914
MISCELLANEOUS
Chult Mfr. Mfr. Deslg.
i%,:“’
J201 Not Used J202 Receptacle, BNC (UG-1094AIU) 02660 31-2221
Type
Integrated Circuit, Operational Amplifier. 07263
Switch, Rotary, GAIN 80164
Knob, Gain
Code Desig.
%E
RESISTORS (*Located on Switch 5201)
Circuit Lhig. VSIIJS Rating
Type
Mfr. Code
Mfr. Desig.
Keithley Part No.
24555A 24555A TG-39 TG-39
RF-14 16 RF-14 16 RF-26 RF-26 RF-26 16 RF-28 18
Fig. Ref.
18
1:
18
Keithley Fig. Part No. Ref.
IC-26 18
SW-337 18
KN-46 2
cs-249 18
Keithley Part No.
Flg. Ref.
R201 1on IO%, 1/4W Comp 44855 R202 lfvm R203 R204 23.2kn R205 22.lkn l%, 1/8W MtF 07716 R206 IOkn I%, 1/8W R207 R206 R209 12.lkn R210 499n I%, 1/8W R211 4990 I%, 1/8W R212 R213 47on IO%, 1/4W, Comp R214 R215 470R 1 O%, 1/4W Comp R216 IOR lo%, 1/4W, Comp R217 R218’ 270k.Q lo%, 1/2W Comp R219’ R220’ 9000 1 %, 1/2w DCb 91637 R221’ 1ok.Q I%, 1/2w, R222’ 1ook.Q 1%. 1/2w R223’ IMn l%, 1/2w R224 IOMR 1%. 1 w R225 10BR
1ookQ I%, 1/8W. MtF 07716
18.2kR l%, 1/2w MtF 07718 1ok.Q I%, 1/8W, MtF 07716
1on 1 %, 1/8W MtF 07718 1okQ I%, 1/6W MtF 07716
ion lo%, 1/4W Comp 44655 1 OOR l%, 1/2w MtF 07716
IO%, 1/2W Comp 01121 I%, 1/8W MtF 07716
MtF
I%, 1/8W MtF 07716
MtF 07716 MtF
MtF 07716 MtF 07716 MtF 07718 DCb 91637
l%, 2w DCb 91637
07716
07716 44655 44655
44855 01121
RC07 ELI-1 M CEA-100kR CEA-23.2kR CEA-22.lkQ CEA-1 Okn CEC-18.2kQ CEA-1 Okn CEA-12.lkn CEA-499n CEA-499R CEA-1 OR RC07-471 CEA-IOkR RC07-471 RC07-100 RC07-100 ES-270kn
CEC-IOOR
DCF-l/2-900n
CEC-IOkR CEC-IOOkR CEC-1 Ma
DC-I-IOMR
DC-2-l OQ
R76-10 Rl-IM R88-1 OOk R88-23.2k R88-22.1 k R88-IOk R94-18.2k R88-IOk R88-12.1 k R88-499 R88-499 R88-10 R76-470 R88-10k R78-470 R76-10 R76-10 Rl -270k R94-100 RI 2-900 R94-10k R94-100k R94-1 M Rl3-IOM Rl4-IO8
18 18 18 18 18 18 18 18 18 18
1: 18
18
::
29103-c-2 I 7.90
Page 24; Replace Table with the following:
ClrCUlt De&g.
D306 D309 D310 0311 D312
CkUlf
De&g.
J301 J302
QA301 DA302 QA303 5301 5302 5303
Q301 Q302 Q303 5304 F301 F301 T301 P30.5
­DS-301
DS-302
MOTHER BOARD
TYPe
Silicon Silicon Silicon Silicon Silicon
TYPO
Connector, Mini-PV Connector, Mini-PV
Integrated Circuit, Voltage Regulator Integrated Circuit, Voltage Regulator Integrated Circuit Switch, Line Voltage Switch, “PUSH ON’ Power with lamp Switch. CURRENT SUPPRESS Knob Amperes
Transistor
Transistor Transistor. Silicon, NPN. TO-92 Case Switch POLARITY Fuse. tt7V. .25a, Slo-Blo.3AG Fuse, 234V, IIBA. Slo-Blo, 3AG Transformer Receptacle, AC Line cord. mates with P305 Pilot lamp, neon (replacement for 5302)
Pilot Lamp, OVERLOAD
Knob, Fine Adjust
(cont’d)
DIODES (co&d)
Mfr. Mfr. Code
01295 01295 01295 01295 1 N645 01295
MISCELLANEOUS
Mfr. Mfr. Code
22526 22526 07263 07263 07263 80164 SW-316 60164 60164
02735 02735 04713 60164 75915 71400 90164 92369 70903 09806 07294
RESISTORS (*Located
Deslg.
IN914 IN914 IN914
IN914
Deslg. Part No. Ref.
47439 47439
UGA7723393 UGA7723393
A749C
PBL-5-BSA3C7A
SW-339 40312
40312 2N3903
SW-236
Ei250
TR-136
AC3G 17256-S C7A (NE-2P) CFO3ACSl669
on
Switch S303)
Kelthley Part No.
RF-28 RF-26 RF-26 RF-14 RF-26
Ketthley Ftg.
CS-236 CS-236 IO-26 IC-25 IC-27 SW-316 SW-340 SW-339 KN-46
._
TG-54 TG-5*
.-_.
TG-49 SW-236 FU-17 FU-20 TR-136 CS-235 co-7 PL-58 PL-51 KN-58
Flg.
Ref.
17 17
;:
-
17 ;:
17
17 3 3 20 2
17
17
17 3
3 ;0
3
-
-
2
2
Destg.
R301 R302 R303 R304 R305 R306 R307 R306 R309 R310 R311 R312 R313 R314 R315 R316 R317 R316 R319 R320 R321 R322 R323 R324 R325
VdUe 634fl
6.2D
1.37k.D
*oo*
1.24kn
634*
6.2n
1.37la
2oon
1.24kQ
9.09ko 14kR 1kfJ 1 OkR
&%n
lk0 IkQ 14kfl IOCl 1 Okn 1 OkR 33on 47kn 10kQ
Aatlng
1%. 1/6W
5%, 1/2w Comp
1%. IIBW MtF
0.5w 1%. l/SW 1%. 119w MtF
5%. t /2w Comp
1%. l,QW M1F
0.5w 1%. l/SW MtF l%, IBW 1%. 1/8W I%, 1/8W MtF 10%. 1/4w Comp I%, l/QW I%, l/BW I%, 1/6W MtF I%, 1/6W 1%. 1/6W MIF 10% 1/4w 10%. 114w Comp IO%, 1/4w 10%. 114w Comp 10%. 114w Comp 1%. 1/2w
TYPO
MtF
­MtF
­MtF
MtF
MtF MtF
MtF Comp Comp
MtF
Mfr. Code
07716 CEA-6340 01121
07716 60294 3329P-200 RP-98-200 07716 CEA-1.1 k.Q R68-1.24 07716 01121 07716 60294 3329P-200 RP-98-200 07716 CEA-1 .I Icn R68-1.24 07716 CEA-9.09kR 07716 CEA-14kR 07716 44655 RC07-100 R76-10 07716 CEA-1 kn 07716 CEA-9.09kR 07716 07716 CEA-1 kR 07716 44955 RC07-100 44655 RC07-103 R76-t0k 44655 RC07.103 44655 44655 RC07-473 07716 CEC-lOk0
Mfr. Desig.
EB-6.2n CEA-1.37kR
CEA-634n EB-9.2n CEA-t.37M
CEA-1 kn
CEA-1 kn CEA-14kn
RC07-331
Kelthley
Part No.
R66-634 RIQ-6.2 R&?-l .37k
R98-634 RIQ-6.2 R88-1.371
R66-9.09k R99-t4k R66-1 k
RBB-1 k RBB-9.09k RBB-1 k RBB-I k R96-14k R76-10
R76-IOk R76-330 R76-47k R94-10k
Flg.
Ref.
17 17 17 17 17
;: ;:
17 17
1: 17 17
;: 17 17 17
;: 17 17 20
29103-C-2 / 7-90
HOW TO INSTALL IC-333
CUT PIN 5 OF THE IC-333.
ii. PIN 1 IXF THE Op AMP GOES INTO THE HOLE IOF PIN 2.
PIN 2 OF THE CIp AMP GOES INTO THE HOLE CiF pIN S.*j:
8.
C. PIN 3 OF THE Op AMP GOES INTO THE HOLE OF PIN 4.
D . PIN 4 OF THE OP iiw GOES INTO THE HOLE OF PIIN 5.
cc
PIN & OF THE OP AMP GOES INTO THE HOLE OF PIN .5.X+
E.
F. PIN 7 OF THE Op AMP GOES INTO THE HOLE OF PIN 3.
G. FIN 3 OF THE OF GMF GOES INTO THE HOLE OF PIN 10.
PIN HOLES 1,7,9 WILL REMAIN EMPTY.
ON THE REVERSE SIDE OF THE PC-&u
=“9 INSTkLL A CAPACITOR
c-64-22pF BETWEEN FINS 3 AND b OF PC BOARD. %*
CHANGE R210 AND R211 FORM R-83-1K TO R-38-3.01K.
REMOVE CAPACITORS C-207,C-203
AND C-20’? FROM THE
CIRCUIT BOARD. THEY ARE NO LONGER NEEDED.
SEE ATTACHED DRAWING.
4
MODEL 427
COMPONENT UYOUTS
rR201-+201 --y-C2031
-
-c107-
FIGURE 18.
component Layout - PC-289.
FIGURE 19.
Component Layout - PC-292.
15
Loading...