Datasheet TDA2030A Datasheet (Contek)

TDA2030A LINEAR INTEGRATED CIRCUIT

14W HI-FI AUDIO AMPLIFIER

DESCRIPTION

The Contek TDA2030A is a monolithic audio power amplifier

integrated circuit.

FEATURES

*Very low external component required.
*High current output and high operating voltage.
*Low harmonic and crossover distortion.
*Built-in Over temperature protection.
*Short circuit protection between all pins.
*Safety Operating Area for output transistors.

1

TO-220B

PIN CONFIGURATIONS

1 Non inverting input
2 Inverting input
3 -VS
4 Output
5 +VS

ABSOLUTE MAXIMUM RATINGS(Ta=25 C)

PARAMETER SYMBOL VALUE UNIT

Supply Voltage Vs +-12 V
Input Voltage Vi Vs V
Differential Input Voltage Vdi +-15 V
Peak Output Current(internally limited) Io 3.5 A
Total Power Dissipation at Tcase=90 C Ptot 20 W
Storage Temperature Tstg -40~+150 C
Junction Temperature Tj -40~+150 C

ELECTRICAL CHARACTERISTICS(Refer to the test circuit, Vs =+-16V,Ta=25 C)

PARAMETER SYMBOL TEST CONDITIONS MIN TYP MAX UNIT

Supply Voltage Vs +-6 +-22 V
Quiescent Drain
Current
Input Bias Current Ib 0.2 2 mA
Input Offset Voltage Vos Vs=+-18v +-2 +-20 mV
Input Offset Current Ios +-20 +-200 nA

Id 50 80 mA

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1

TDA2030A LINEAR INTEGRATED CIRCUIT

(Continued)
Output Power Po d=0.5%,Gv=26dB,f=40 to 5kHz

RL=8W 15 18 W
RL=4W 10 12 W

Vs=+-19V, RL=4W 13 16 W
Power Bandwidth BW Po=15W,RL=4W 100 KHz
Open loop voltage
Gain
Closed Loop
Voltage Gain
Total harmonic
distortion

Total harmonic
Distortion
Second Order CCIF
Intermodulation
distortion
Third Order CCIF
Intermodulation
Distortion
Input Noise Voltage B=curve A 2 mA
Input Noise Voltage eN B= 22Hz to 22kHz 3 10 mV
Input Noise Current iN B= 22Hz to 22kHz 80 200 pA
Input
Resistance(pin 1)
Supply Voltage
Rejection
Thermal Shut­Down Junction
Temperature

Gvo f=1kHz 80 dB

Gvc 25.5 26 26.5 dB

THD Po=0.1 to 14W,RL=4W

f=1kHz

Po=0.1 to 14W,RL=4W

f=1kHz

THD Po=0.1 to 9W,RL=8W

f=40 to 15 kHz

d2 Po=4W ,RL=8W

f2-f1=1 kHz

d3 f2=14 kHz,f1=15kHz 0.08 %

Ri Open loop,f=1kHz 0.5 5 MW

RL=4W,Gv=26dB

Rg=22kW,f=1kHz

Tj 145 C

0.08 %

0.03 %

0.05 %

0.03 %

54 dB

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2

TDA2030A LINEAR INTEGRATED CIRCUIT

TEST CIRCUIT

+Vs

C1

1 m F

Vi

R3

680 W

C2

22 m F

APPLICATION CIRCUIT

C1

1 m F

Vi

R3

22k

R3

680 W

C2

22 m F

22k

R3

W

1

W

2

220 m F

1

Contek
TDA2030A

2

C5

220 m F

Contek
TDA2030A

100 m F

C5

C6

100 m F

C3

100nF

D1

1N4001

5

4

3

R1

13k W

1N4001

C6

C4

100nFC7220nF

R4
1 W

D1

RL

-Vs

+Vs

C3

100nF

D1

1N4001

5

4

3

R1

13k W

D1

1N4001

C4

100nFC7220nF

R4
1 W

RL

CONTEK

-Vs

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3

TDA2030A LINEAR INTEGRATED CIRCUIT

+Vs

Vi

22 mF

0.1 mF

100k W

2.2mF

1

100k W

Contek
TDA2030A

2

W

100k

4.7k W

2.2mF

Fig.1 Single supply amplifier

5

3

220mF

100k W

1N4001

1N4001

4

R4

1W

C7

220nF

F

m

2200

W

RL=4

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4

TDA2030A LINEAR INTEGRATED CIRCUIT

TYPICAL PERFORMANCE CHARACTERISTICS

Gv

(dB)

140

100

60

Fig.2 Open loop frequency

response

180

Phase

90

0

Gain

20

Phase

Po

(W)

Fig.3 Output power vs. Supply

voltage

24

Gv=26dB

20

16

12

d=0.5%
f=40 to 15kHz

RL=4W

RL=8W

d

(%)

Vo

(Vp-p)

-20

-60
1

10210310410510610

10

Fig.4 Total harmonic distortion

vs. output power

2

10

1

10

0

10

-1

10

-2

10

-2

10

10

f=15kHz

f=1kHz

-1

Gv=26dB

10

Fig.6 Large signal frequency

response

30

25

20

15

10

Vs=+-15V
RL=4 W

8

7

4

24 28 32 36 40 44

Vs (V)Frequency (Hz)

Fig.5 Two tone CCIF

2

intermodulation distortion

10

d

(%)

1

10

Vs=32V

Order (2f1-f2)

Order (2f2-f1)

2

10

Po=4W
RL=4W
Gv=26dB

10

3

0

Vs=38V

W

RL=8

Vs=32V

RL=4W

0

1

10

Po (W) Frequency (Hz)

2

10

10

-1

10

-2

10

1

10

Po (W)

4

10

5

10

Fig.7 Maximum allowable power

dissipation vs. ambient

temperture

30

Vs=+-15V
RL=8 W

Ptot
(W)

25

20

15

10

heatsink having

Rth=4

heatsink having
Rth=8

X

C/W

heatsink having

Rty=25

infinite heatsink

C/W

X

C/W

X

5

10

CONTEK

1

2

10

3

10

Frequency (kHz)

4

10

Contek Microelectronics Co.,Ltd.

5

-50 0 50 100 150 200

Tamb (XC)

5

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TDA2030A LINEAR INTEGRATED CIRCUIT

+Vs

C5

220 mF

/40V

5

C6

3

BD908

1N4001

4

0.22 mF

C8

2200mF

R8

1W

BD907

1N4001

C7

0.22 mF

Vi

C1

2.2 mF

F

m

C2

22

F

R1

56kW

C3

m

0.22

R6

1.5W

1

R3

Contek

W

56k

TDA2030A

R2

56kW

Fig. 8 Single supply high power amplifier(Contek TDA2030+BD908/BD907)

2

R4

3.3kW

C4

10mF

R5

30k

W

R7

1.5W

TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 8

PARAMETER SYMBOL TEST CONDITIONS MIN TYP MAX UNIT

Supply Voltage Vs 36 44 V
Quiescent Drain
Current

Output Power Po

Voltage Gain Gv f=1kHz 19.5 20 20.5 dB
Slew Rate SR 8 V/msec
Total Harmonic d Po=20W,f=1kHz 0.02 %
Distortion Po=20W,f=40Hz to 15kHz 0.05 %
Input Sensitivity Vi Gv=20dB,Po=20W,

Signal to Noise S/N
Ratio RL=4W,Rg=10kW

Id Vs=36V 50 mA

d=0.5%,RL=4W

f=40Hz to 15kHz,Vs=39V

d=0.5%,RL=4W

f=40Hz to 15kHz,Vs=36V

d=0.5%,f=1kHz,

Vs=39V

RL=4W

d=0.5%,RL=4W
f=1kHz,Vs=36V

f=1kHz,RL=4W

RL=4W,Rg=10kW

B=curve A,Po=25W 108 dB

B=curve A,Po=25W

35

28

W

44

35

890 mV

100

RL=4W

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6

TDA2030A LINEAR INTEGRATED CIRCUIT

TYPICAL PERFORMANCE CHARACTERISTICS

(W)

Fig. 10 Output power vs. supply

voltage

Po

45

35

d

(%)

10

Fig. 11 Total harmonic distortion

vs. output power

Vs=36V
RL=4W

0

Gv=20dB

25

15

5

24 28 32 34 36

Fig. 12 Output power vs.

Input level

Po

(W)

20

Gv=26dB

15

10

5

0

100 250 400 550 700

Gv=20dB

-1

10

-2

40

Vs
(V)

10

-1

10

f=15kHz

f=1kHz

0

10

1

10

(W)

Po

Fig. 13 Power dissipation vs.

output power

Ptot

(W)

(mV)

20

15

10

5

Vi

0

0 8 16 24 32

Complete
Amplifier

BD908/

BD907

Contek

TDA2030

(W)

Po

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7

TDA2030A LINEAR INTEGRATED CIRCUIT

+Vs

5

3

R1

22kW

C3

100nF

D1

1N4001

4

C8

R5

D2

1N4001

C4

100nFC7220nF

R4
1

W

RL

C5

R3

22kW

100 mF

1

Contek
TDA2030A

C1

1 mF

Vi

2

R3

680W

C2

22 mF

C6

100 mF

-Vs

Fig. 14 Typical amplifier with split power supply

Vs+

C6

C1

220 m F

IN

R1

22k W

1

2

Contek
TDA2030A

100 m F

5

3

22 m F

R3

22k W

C4

R4

680

4

W

100nF

C7

F

m

C8

0.22

R8
1 W

RL
8 W

R7

W

22k

CONTEK

Vs-

C2

100 m F

R2

22k W

100nF

1

Contek
TDA2030A

2

C3

5

4

3

R5

22k W

C5

22 m F

R6

680 W

Fig. 16 Bridge amplifier with split power supply(Po=34W,Vs+=16V,Vs-=16V)

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C9

1 W

F

m

0.22

R9

8

TDA2030A LINEAR INTEGRATED CIRCUIT

MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES

Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is
specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems
divide the audio spectrum two or three bands.

To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must
overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to
ensure that each unit generates the correct amount of acoustic energy for its segments of the audio spectrum. In this
respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies
of the crossover filters(see Fig. 18).As an example,1 100W three-way system with crossover frequencies of 400Hz
and 3khz would require 50W for the woofer,35W for the midrange unit and 15W for the tweeter.

Both active and passive filters can be used for crossovers but active filters cost significantly less than a good
passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from the
typical defects of passive filters:

--Power less;

--Increased impedance seen by the loudspeaker(lower damping)

--Difficulty of precise design due to variable loudspeaker impedance.

Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it
particularly interesting and economically sound to use monolithic power amplifiers.

In some applications complex filters are not relay necessary and simple RC low-pass and high-pass
networks(6dB/octave) can be recommended.

The result obtained are excellent because this is the best type of audio filter and the only one free from phase and
transient distortion.

The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly well
beyond the crossover frequency to avoid distortion.

A more effective solution, named "Active power Filter" by SGS is shown in Fig. 19.

The proposed circuit can realize combined power amplifiers and 12dB/octave or 18dB octave high-pass or low-

pass filters.

In proactive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active

filter operations.

The impedance at the Pin(-) is of the order of 100 W,while that of the Pin (+) is very high, which is also what was
wanted.

100

IEC/DIN NOISE

80

SPECTRUM

FOR SPEAKER

60

40

20

0

1

10

CONTEK

Fig. 18 Power distribution vs.

frequency

Morden

TESTING

10

2

Music

Spectrum

3

10

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Fig. 19 Active power filter

C1 C2 C3

R2R1

R3

4

10

5

10

Vs+

RL

3.3kW

Vs-

100W

9

TDA2030A LINEAR INTEGRATED CIRCUIT

The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are:

Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20.
It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz.
The midrange section consistors of two filters a high pass circuit followed by a low pass network. With Vs=36V the
output power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange and
the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance(RL=4 W
to 8W).
It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers.

IN

680W

Vs+

22kW

100 mF

C1=C2=C3=22nF,R1=8.2K W,R2=5.6KW,R3=33KW.

1 mF

W

22k

Low-pass

300Hz

22k W

22kW

Band-pass

300Hz to 3kHz

0.1 mF0.1 mF

3.3kW

High-pass

3kHz

0.1 mF0.1 mF

12kW

100W

22kW

33nF

100W

6.8kW

100 mF

3.3nF

100W

2200 mF

0.22 mF

1

18nF

2

3.3kW

0.22 mF

22kW22kW

100 mF

18nF

1

2

0.22 m F

1

22kW

47 mF

2

Contek
TDA2030A

Vs+

Contek
TDA2030A

2.2k W

Contek
TDA2030A

2.2k W

1.5W

5

4

3

0.22 mF

1.5W

1N4001

5

4

3

1N4001

Vs+

1N4001

5

4

3

1N4001

High-pass

3kHz

1N4001

1N4001

BD908

BD907

Vs+

2200 mF

1W

4W

0.22 mF

Woofer

220 mF

W

1

0.22 mF

8W

Midrange

100 mF

W

1

F

m

0.22

8W

Tweeter

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10

TDA2030A LINEAR INTEGRATED CIRCUIT

MUSICAL INSTRUMENTS AMPLIFIERS

Another important field of application for active system is music.
In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and it
is also more reliable. A typical example(see Fig. 21) consist of four amplifiers each driving a low-cost, 12 inch
loudspeaker. This application can supply 80 to 160W rms.

TRANSIENT INTER-MODULATION DISTORTION(TIM)

Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers.
When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency components,
the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation
distortion will be produced as in Fig.22.Since transients occur frequently in music this obviously a problem for the
designed of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic
distortion of an amplifier, which tends to aggravate the transient inter- modulation(TIM situation.)The best known

Fig.21 High power active box for musical

instrument

20 to 40W

Amplifier

20 to 40W

Amplifier

20 to 40W

Amplifier

20 to 40W

Amplifier

INPUT

AMPLIFIER

V1 V2 V3 V4

V1

V2

V3

V4

Fig.22 Overshoot phenomenonin

feedback amplifiers

PRE

FEEDBACK

V4

POWER

AMPLIFIER

PATH

OUTPUT

method for the measurement of TIM consists of feeding sine waves superimposed onto square wavers, into the
amplifier under test. The output spectrum is then examined using a spectrum analyzer and compared to the input.
This method suffers from serious disadvantages: the accuracy is limited, the measurement is a tatter delicate
operation and an expensive spectrum analyzer is essential. A new approach (see Technical Note 143(Applied by
SGS to monolithic amplifiers measurement is fast cheap, it requires nothing more sophisticated than an
oscilloscope-and sensitive-and it can be used down to the values as low as 0.002% in high power amplifiers.

The "inverting- sawtooth" method of measurement is based on the response of an amplifier to a 20KHz saw-tooth
wave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will
follow the upper line in Fig.23 cutting of the shade area and thus increasing the mean level. If this output signal is
filtered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it is
difficult to measure because it is indistinguishable from the DC offset of the amplifier. This problem is neatly avoided
in the IS-TIM method by periodically inverting the saw-tooth wave-form at a low audio frequency as shown in
Fig.24.Inthe case of the saw-tooth in Fig. 25 the means level was increased by the TIM distortion, for a saw-tooth in
the other direction the opposite is true.

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11

TDA2030A LINEAR INTEGRATED CIRCUIT

SR(V/ms)

m2

m1

Input

Signal

Filtered

Output

Siganal

Fig.23 20kHz sawtooth waveform Fig.24 Inverting sawtooth waveform

The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured
easily with an oscilloscope. If the peak- topeak value of the signal and the peak-to-peak of the inverting sawtooth are
measured, the TIM can be found very simply from:

TIM

VOUT

* 100=

Vsawtooth

10

TIM(%)

10

10

1

0

-1

Fig. 25 TIM distortion Vs.

Output Power

TDA2030A
BD908/907
Gv=26dB
Vs=36V

W

RL=4

RC Filter fc=30kHz

10

SR(V/ s)

1

10

0

10

2

Fig. 26 TIM design

diagram(fc=30kHz)

RC Filter fc=30kHz

TIM=0.01%

TIM=0.1%

TIM=1%

-2

10

-1

10

0

10

1

10

Po(W)

2

10

-1

10

-1

10

0

10

1

10

Vo(Vp-p)

2

10

In Fig.25 The experimental results are shown for the 30W amplifier using the TDA2030A as a driver and a low-cost
complementary pair. A simple RC filter on the input of the amplifier to limit the maximum signal slope(SS) is an
effective way to reduce TIM.

The Diagram of Fig.26 originated by SGS can be used to find the Slew- Rate(SR) required for a given output power
or voltage and a TIM design target.
For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. Peak to peak output voltage is 20V then,
referring to the diagram, a Slew-Rate of 6V/ ms is necessary for 0.1% TIM.
As shown Slew-Rates of above 10V/ ms do not contribute to a further reduction in TIM.
Slew-Rates of 100V/ms are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend to turn
the amplifier into a radio receiver.

POWER SUPPLY

Using monolithic audio amplifier with non regulated supply correctly. In any working case it must provide a supply

voltage less than the maximum value fixed by the IC breakdown voltage.

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12

TDA2030A LINEAR INTEGRATED CIRCUIT

It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage
variations with and without load. The TDA2030(Vsmax=44V) is particularly suitable for substitution of the standard IC
power amplifiers(with Vsmax=36V) for more reliable applications.
An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram of
Fig.27.

A regulated supply is not usually used for the power output stages because of its dimensioning must be done taking
into account the power to supply in signal peaks. They are not only a small percentage of the total music signal, with
consequently large overdimensioning of the circuit.
Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the
additional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer
designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying the
required energy.

In average conditions, the continuous power supplied is lower. The music power/continuous power ratio is greater
in case than for the case of regulated supplied, with space saving and cost reduction.

Fig.27 DC characteristics of

50W non-regulated supply

Io(A)

Ripple
(Vp-p)

4

2

0

220V

3300mF

Vo(V)

36

34

32

30

28

0 0.4 0.8 1.2 1.6 2.0

Ripple

Vout

Mains(220V) Secondary Voltage DC Output Voltage(Vo)

Io=0 Io=0.1A Io=1A
+20% 28.8V 43.2V 42V 37.5V
+15% 27.6V 41.4V 40.3V 35.8V
+10% 26.4V 39.6V 38.5V 34.2V

24V 36.2V 35V 31V

-10% 21.6V 32.4V 31.5V 27.8V

-15% 20.4V 30.6V 29.8V 26V

-20% 19.2V 28.8V 28V 24.3

Vo

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13

TDA2030A LINEAR INTEGRATED CIRCUIT

SHORT CIRCUIT PROTECTION

The Contek TDA2030 has an original circuit which limits the current of the output transistors. This function can be
considered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device
gets damaged during an accidental short circuit from AC output to Ground.

THERMAL SHUT-DOWN

The presence of a thermal limiting circuit offers the following advantages:

1).An overload on the output (even if it is permanent),or an above limit ambient temperature can be easily supported
since the Tj can not be higher than 150 C

2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no possibility of
device damage due to high junction temperature increase up to 150, the thermal shut-down simply reduces the power
dissipation and the current consumption.

APPLICATION SUGGESTION

The recommended values of the components are those shown on application circuit of Fig.14. Different values can be
used. The following table can help the designer.

COMPONENT RECOMMENDED

VALUE

R1 22KW Closed loop gaon

R2 680W Closed loop gaon

R3 22KW Non inverting input

R4 1W Frequency stacility Danger of oscillation

R5 3R2 Upper frequency

C1 1mF Input DC decoupling Increase of low

C2 22mF Inverting DC

C3,C4 0.1mF Supply voltage

C5,C6 100mF Supply voltage

C7 0.22mF Frequency stability Larger bandwidth
C8 1/(2p*B*R1) Upper frequency

D1,D2 1N4001 To protect the device

PURPOSE LARGE THAN

setting.

setting.

biasing

cutoff

decoupling

bypass

bypass

cutoff

against output voltage

spikes.

RECOMMENDED

Increase of Gain Decrease of Gain

Decrease of Gain Increase of Gain

Increase of input

impedance

at high frequencies

with inductive loads.

Poor high frequencies

attenuation

smaller bandwidth Larger bandwidth

LARGE THAN

RECOMMENDED

VALUE

Decrease of input

Dange of oscillation

frequencies cutoff

Increase of low

frequencies cutoff

Dange of oscillation

Dange of oscillation

VALUE

impedance

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14