Datasheet RC4156M, RC4156N, RC4157N Datasheet (Fairchild Semiconductor)

www.fairchildsemi.com

RC4156/RC4157

High Performance Quad Operational Ampliﬁers

Features

• Unity gain bandwidth for RC4156 – 3.5 MHz

• Unity gain bandwidth for RC4157 – 19 MHz

• High slew rate for RC4156 – 1.6 V/µS

• High slew rate for RC4157 – 8.0V/µS

Description

The RC4156 and RC4157 are monolithic integrated circuits, consisting of four independent high performance operational ampliﬁers constructed with an advanced epitaxial process.

These ampliﬁers feature improved AC performance which far exceeds that of the 741 type ampliﬁers. Also featured are

• Low noise voltage – 1.4 µVRMS

• Indeﬁnite short circuit protection

• No crossover distortion

excellent input characteristics and low noise, making this device the optimum choice for audio, active ﬁlter and instrumentation applications. The RC4157 is a decompensated version of the RC4156 and is AC stable in gain conﬁgurations of -5 or greater.

Block Diagram

Output (A)

–Input (A)

+Input (A)

+Input (B)

–Input (B)

Output (B)

A

+

B

D

+

C

65-3463-01

Output (D)

–Input (D)

+Input (D)

+Input (C)

–Input (C)

Output (C)

Pin Assignments

+V

1

2

3

4

S

5

6

7

Output (A)

–Input (A) +Input (A)

+Input (B) –Input (B)

Output (B)

14

13

12

11

10

65-3463-02

9

8

Output (D) –Input (D) +Input (D) –V

S

+Input (C) –Input (C) Output (C)

REV. 1.0.1 6/13/01

PRODUCT SPECIFICATION RC4156/RC4157

Absolute Maximum Ratings

(beyond which the device may be damaged)

Parameter Min Typ Max Units

Supply Voltage ±20 V

Input Voltage

Differential Input Voltage 30 V

Output Short Circuit Duration

< 50°C SOIC 300 mW

P

DTA

Operating Temperature RC4156/RC4157 0 70 °C

Storage Temperature -65 150 °C

Junction Temperature SOIC, PDIP 125 °C

Lead Soldering Temperature (60 seconds)

For T

A

Notes:

1. Functional operation under any of these conditions is NOT implied. Performance and reliability are guaranteed only if Operating Conditions are not exceeded.

2. For supply voltages less than ±15V, the absolute maximum input voltage is equal to the supply voltage.

3. Short circuit to ground on one amplifier only.

2

3

> 50°C Derate at SOIC 5.0 mW/°C

1

±15 V

Indeﬁnite

PDIP 468 mW

DIP 300 °C

SOIC 260 °C

PDIP 6.25 mW/°C

Operating Conditions

Parameter Min Typ Max Units

θ

JC

θ

JA

Thermal resistance 60 °C/W

Thermal resistance SOIC 200 °C/W

PDIP 160 °C/W

Electrical Characteristics

(VS = ±15V, RC = 0°C ≤ TA ≤ +70°C)

RC4156/4157

Parameters Test Conditions Min Typ Max Units

Input Offset Voltage RS ≤ 10 kΩ 6.5 mV

Input Offset Current 100 nA

Input Bias Current 400 nA

Large Signal Voltage Gain RL ≥ 2 kΩ,V

Output Voltage Swing RL ≥ 2 kΩ ±10 V

Supply Current 10 mA

Average Input Offset Voltage Drift 5.0 µV/°C

±10V 15 V/mV

OUT

2 REV. 1.0.1 6/13/01

RC4156/RC4157 PRODUCT SPECIFICATION

Electrical Characteristics

(VS = ±15V and TA = +25°C unless otherwise noted)

RC4156/4157

UnitsParameters Test Conditions Min Typ Max

Input Offset Voltage R

Input Offset Current 30 50 nA

Input Bias Current 60 300 nA Input Resistance 0.5 MΩ

Large Signal Voltage Gain R

Output Voltage Swing R

Input Voltage Range ±12 ±14 V Output Resistance 230 Ω

Short Circuit Current 25 mA

Common Mode Rejection Ratio RS ≤ 10 kΩ 80 dB

Power Supply Rejection Ratio RS ≤ 10 kΩ 80 dB

Supply Current (All Amplifiers) RL = ∞ 5.0 7.0 mA

Transient Response (4156)

Rise Time 60 nS

Overshoot 25 %

Slew Rate 1.3 1.6 V/µS

Unity Gain Bandwidth (4156) 2.8 3.5 MHz

Phase Margin (4156) RL = 2 kΩ, CL = 50 pF 50 %

Transient Response (4157) AV = -5

Rise Time 50 nS

Overshoot 25 %

Slew Rate 6.5 8.0 V/µS

Unity Gain Bandwidth (4157) AV = -5 15 19 MHz

Phase Margin (4157) AV = -5, RL = 2 kΩ,

Power Bandwidth V

Input Noise Voltage

1

Input Noise Current F = 20 Hz to 20 kHz 15 pA

Channel Separation 108 dB

Note:

1. Sample tested only.

≤ 10 kΩ 1.0 5.0 mV

S

≥ 2 kΩ, V

L

≥ 10 kΩ ±12 ±14 V

L

±10V 25 100 V/mV

OUT

RL ≥ 2 kΩ ±10 ±13 V

50 %

CL = 50 pF

OUT

= 20V

p-p

20 25 kHz

F = 20 Hz to 20 kHz 1.4 5.0 µV

RMS

REV. 1.0.1 6/13/01 3

PRODUCT SPECIFICATION RC4156/RC4157

Typical Performance Characteristics

140 110 100

(dB)

VOL

A

-10

90 80 70 60 50 40 30 20 10

4156

A

VOL

R = 2K

L

C = 55 pF

L

0

45

Φ

90

Φ (Deg)

135

0

10

100

1K 10K 100K

1

1M

10M

180

65-0738

F (Hz)

120

100

80

60

PSRR (dB)

40

20

0

-100

-50

-V

S

0

TA (°C)

+V

S

65-0740

+50 +100 +150-25 +25 +75 +125-75

Figure 1. Open Loop Gain, Phase vs. Frequency Figure 2. PSRR vs. Temperature

2

3

6

5

100K

4156/57

100K

4156/57

1

7

V

OUT1

C.S. = 20 log ( )

V

100 V

OUT2

V

OUT2

65-0739

OUT1

-140

-120

1K

-100

-80

-60

CS (dB)

-40

1K

-20

0

10 100 1K 10K 100K

1K

F (Hz)

Figure 3. Channel Separation vs. Frequency

1.3 35

1.2

1.1

1.0

0.9

0.8

Transient Response

(Normalized to +25°C)

0.7

0.6

-100 -50

65-0741

0 +50 +100 +150-75 -25 +25 +75 +125

TA (°C)

30

25

20

15

(nV Hz )

n

e

10

5

e

n

I

N

0

10 100 1K 10K 100K

F (Hz)

Figure 4. Transient Response vs. Temperature Figure 5. Input Noise Voltage, Current

Density vs. Frequency

1.4

1.2

1.0

0.8

0.6

0.4

0.2

0

(pA Hz )

N

I

65-0742

4 REV. 1.0.1 6/13/01

RC4156/RC4157 PRODUCT SPECIFICATION

Typical Performance Characteristics (continued)

1.3

1.1

1.2

1.1

1.0

0.9

SR,BW

0.8

(Normalized to +25°C)

0.7

0.6

-100

-50 0 +50 +100

TA (°C)

65-0743

+150

1.0

0.9

SR, BW

0.8

(Normalized to ±15V)

0.7

SR and

BW

0

±2 ±5 ±10 ±15 ±20

±VS (V)

Figure 6. Slew Rate, Bandwidth vs. Temperature Figure 7. Slew Rate, Bandwidth vs. Supply Voltage

30

V

= 28V VS = ±15V

(V)

30

10

OUT P-P

V

OUT P-P

V

OUT P-P

= 18V VS = ±10V

= 8V VS = ±5V

25

20

(V)

15

OUT P-P

1.0

V

4156

(Voltage Follower) R = Open

L

C = 50 pF

L

0.1 100 1K 10K

F (Hz)

100K

65-0746

1M

OUT P-P

V

100

10

05

0

1K

RL ( )

10K 100K

Ω

BW

65-0744

65-0749

Figure 8. Output Voltage Swing vs. Frequency Figure 9. Output Voltage Swing vs. Load Resistance

70

60

50

40

30

ΦM (Deg)

20

10

0

10 100

ΦM

BW

1K

4156

10K 100K

7

6

5

4

3

2

1

0

BW (MHz)

65-0745

CL (pF)

Figure 10. Small Signal Phase Margin,

Unity Gain Bandwidth vs. Load Capacitance

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PRODUCT SPECIFICATION RC4156/RC4157

Typical Performance Characteristics (continued)

140

120

100

80

(nA)

OS

60

, I

B

I

40

20

0-

-100 -75

Figure 11. Input Bias, Offset Current vs. Temperature Figure 12. CMRR vs. Temperature

-25 0 +25 +50 +75 +100

-50

TA (°C)

I

B

I

OS

Applications

The RC4156 and RC4157 quad operational ampliﬁers can be used in almost any 741 application and will provide superior performance. The higher unity gain bandwidth and slew rate make it ideal for applications requiring good frequency response, such as active ﬁlter circuits, oscillators and audio ampliﬁers.

The following applications have been selected to illustrate the advantages of using the Fairchild Semiconductor RC4156 and RC4157 quad operational ampliﬁers.

Triangle and Square Wave Generator

The circuit of Figure 13 uses a positive feedback loop closed around a combined comparator and integrator. When power is applied the output of the comparator will switch to one of two states, to the maximum positive or maximum negative voltage. This applies a peak input signal to the integrator, and the integrator output will ramp either down or up, opposite of the input signal. When the integrator output (which is connected to the comparator input) reaches a threshold set by R1 and R2, the comparator will switch to the opposite polarity. This cycle will repeat endlessly, the integrator charging

+125+150

140

120

100

80

60

CMRR (dB)

40

20

65-0747

0

-100 -75

-25 0 +25 +50 +75 +100

-50

TA (°C)

positive then negative, and the comparator switching in a square wave fashion.

The amplitude of V

is adjusted by varying R1. For best

2

operation, it is recommended that R1 and VR be set to obtain a triangle wave at V2 with ±12V amplitude. This will then allow A3 and A4 to be used for independent adjustment of output-offset and amplitude over a wide range.

The triangle wave frequency is set by C0, R0, and the maximum output voltages of the comparator. A more symmetrical waveform can be generated by adding a back-to-back Zener diode pair as shown in Figure 14.

An asymmetric triangle wave is needed in some applications. Adding diodes as shown by the dashed lines is a way to vary the positive and negative slopes independently.

The frequency range can be very wide and the circuit will function well up to about 10 kHz. The square wave transition time at V

is less than 21 µS when using the RC4156.

1

65-0748

+125+150

6 REV. 1.0.1 6/13/01

RC4156/RC4157 PRODUCT SPECIFICATION

+12V

20K

8

(+)

Amplitude

Adjust

V4

Triangle

Wave

Output

30K

1K

+15V

V 0.12V~

R

2

3

~

4156/57

A

20K

R1

R2

20K

1

5K

V1

Square Wave

Output

R0

100K

*

10K

6

4156/57

5

C0

B

-12V

R4

1K

V2

7

R3

20K

9

10

1K

+15V

4

4156/57

C

11

-15V

Comparator

* Optional – asymmetric ramp slopes

Integrator

+15V

-15V

Figure 13. Triangle and Square Wave Generator

R1

Figure 14. Triangle Generator—Symmetrical Output Option

Active Filters

The introduction of low-cost quad op amps has had a strong impact on active ﬁlter design. The complex multiplefeedback, single op amp ﬁlter circuits have been rendered obsolete for most applications. State-variable active-ﬁlter circuits using three to four op amps per section offer many advantages over the single op amp circuits. They are relatively insensitive to the passive-component tolerances and variations. The Q, gain, and natural frequency can be independently adjusted. Hybrid construction is very practical because resistor and capacitor values are relatively low and the ﬁlter parameters are determined by resistance ratios rather than by single resistors. A generalized circuit diagram of the 2-pole state-variable active ﬁlter is shown in Figure

15. The particular input connections and component-values can be calculated for speciﬁc applications. An important feature of the state-variable ﬁlter is that it can be inverting or non-inverting and can simultaneously provide three outputs:

5K

13

12

Output

Offset

4156/57

D

14

V3

65-0750

10K

65-2051

lowpass, bandpass, and highpass. A notch ﬁlter can be realized by adding one summing op amp.

The RC4156 was designed and characterized for use in active ﬁlter circuits. Frequency response is fully speciﬁed with minimum values for unity-gain bandwidth, slew-rate, and full-power response. Maximum noise is speciﬁed.

Output swing is excellent with no distortion or clipping. The RC4156 provides full, undistorted response up to 20 kHz and is ideal for use in high-performance audio and telecommunication equipment.

In the state-variable ﬁlter circuit, one ampliﬁer performs a summing function and the other two act as integrators. The choice of passive component values is arbitrary, but must be consistent with the ampliﬁer operating range and input signal

REV. 1.0.1 6/13/01 7

PRODUCT SPECIFICATION RC4156/RC4157

Ts()

a

2

s2a1sa

0

++

s

2

b1sb

0

++

------------------------------------=

Q

ω

0

b

0

------=

R5

100K

R4

10K

V1

R3*

2

4156/57

R7*

3

R6

100K

R8*

V

N

* Input connections are chosen for inverting or non-inverting response. Values of R3,R7,R8 determine gain and Q. ** Values of R1 and R2 determine natural frequency.

1

A

V

Highpass

Ouput

Figure 15. 2-Pole State-Variable Active Filter

characteristics. The values shown for C1, C2, R4, R5 and R6 are arbitrary. Pre-selecting their values will simplify the ﬁlter tuning procedures, but other values can be used if necessary.

The generalized transfer function for the state-variable active ﬁlter is:

9

10

C2

1000 pF

4156/57

C

8

V

LP

Lowpass

Output

65-0751

C1

1000 pF

7

V

BP

Bandpass

Output

R2**

R1**

HP

6

4156/57

5

B

The input conﬁguration determines the polarity (inverting or non-inverting), and the output selection determines the type of ﬁlter response (lowpass, bandpass, or highpass).

Notch and all-pass conﬁgurations can be implemented by adding another summing ampliﬁer.

Filter response is conventionally described in terms of a natural frequency ω0 in radians/sec, and Q, the quality of the complex pole pair. The ﬁlter parameters ω0 and Q relate to the coefﬁcients in T(s) as:

ω

0

and

b0=

R3R5

--------------------R3 R5+

----------------------------------R3R5

R4

---------------------+ R3 R5+

V

s()

HP

R3R4

--------------------R3 R4+

----------------------------------R3R4

R5

---------------------+ R3 R4+

V

LP

Equation 1.

Bandpass ﬁlters are of particular importance in audio and telecommunication equipment. A design approach to bandpass ﬁlters will be shown as an example of the state-variable conﬁguration.

Design Example Bandpass Filter

For the bandpass active ﬁlter (Figure 16) the input signal is applied through R3 to the inverting input of the summing ampliﬁer and the output is taken from the ﬁrst integrator (VBP). The summing ampliﬁer will maintain equal voltage at the inverting and non-inverting inputs (see Equation 1).

R4R5

--------------------R4 R5+

-----------------------------------

s()

R3

R4R5

---------------------+ R4 R5+

V

IN

s()

R7

--------------------R6 R7+

VBPs()+++

8 REV. 1.0.1 6/13/01

RC4156/RC4157 PRODUCT SPECIFICATION

VBPs()

1

R1C1S

------------------

VHPs()–=

ω

0

0.1ω1ω

2

=

Q

1

10

5

R7

--------+

1.1

10

4

R3

--------+

----------------------

ω

0

=

Trim Gain

and Q

R5

100K

R4

R3

V

IN

R7

10K

2

1

3

RC4156/57

A

Set Center Frequency

R6

100K

Figure 16. Bandpass Active Filter

These equations can be combined to obtain the transfer function:

1

-----------------R2C2S

1

---------------

S⋅

R1C1

1



---------------

S



R1C1

VBPs()–=

R4



-------

------------------------------



R5

R1C1R2C2

V

BP

-----------------V

IN

s() s()

and

VLPs()

R4

-------

-------------------------------------------------------------------------------------------------------------------------------------------------------= R7

2

---------------------

S

++

R6 R7+



1



R4

------R5

R3

R4

-------++ R3

1

6

5

RC4156/57

C1

1000 pF

7

B

C2

1000 pF

9

R2R1

10

V

BP

8

RC4156/57

C

65-0752

Deﬁning 1/R1C1 as ω1, 1/R2C2 as ω2, and substituting in the assigned values for R4, R5, and R6, then the transfer function simpliﬁes to:

4

10

--------

ω

s⋅

VBPs()

-----------------V

s()

IN

----------------------------------------------------------------------=

S

2

1.1

----------------------

1

R3

10

--------+

10

--------+

R7

R3

1

4

ω

5

1

s

-------------++

1

ω

1ω2

This is now in a convenient form to look at the centerfrequency ω0 and ﬁlter Q.

ω0109–0.1R1R2=

and

The frequency responses for various values of Q are shown in Figure 17.

0

-10

-20

-30

(dB)

-40

-50

-60

0.1 1.0 10

Q = 0.5

Q = 1.0

Q = 2.0

Q = 5.0

Q = 10

Q = 20

Q = 50

Q = 100

65-0753

ω

o

1

ω

o

V

BP

=

V

IN

1 -

ω

o

Figure 17. Bandpass Transfer Characteristics Normalized

for Unity Gain and Frequency

Q

2

1

+

Q

2

ω

o

REV. 1.0.1 6/13/01 9

PRODUCT SPECIFICATION RC4156/RC4157

These equations suggest a tuning sequence where ω is ﬁrst trimmed via R1 or R2, then Q is trimmed by varying R7 and/or R3. An important advantage of the state-variable bandpass ﬁlter is that Q can be varied without affecting center frequency ω

.

0

This analysis has assumed ideal op amps operating within their linear range, which is a valid design approach for a reasonable range of ω

and Q. At extremes of ω0 and at high

0

values of Q, the op amp parameters become signiﬁcant. A rigorous analysis is very complex, but some factors are particularly important in designing active ﬁlters.

1. The passive component values should be chosen such that all op amps are operating within their linear region for the anticipated range of input signals. Slew rate, output current rating, and common-mode input range must be considered. For the integrators, the current through the feedback capacitor (I = C dV/dt) should be included in the output current computations.

Schematic Diagram (1/4 shown)

2. From the equation for Q, it should seem that inﬁnite Q could be obtained by making R7 zero. But as R7 is made small, the Q becomes limited by the op amp gain at the frequency of interest. The effective closed-loop gain is being increased directly as R7 is made smaller, and the ratio of open-loop gain to closed-loop gain is becoming less. The gain and phase error of the ﬁlter at high Q is very dependent on the op amp open-loop gain at w

.

0

3. The attenuation at extremes of frequency is limited by the op amp gain and unity-gain bandwidth. For integrators, the ﬁnite open-loop op amp gain limits the accuracy at the low-end. The open-loop roll-off of gain limits the ﬁlter attenuation at high frequency.

The RC4156 quad operational ampliﬁer has much better frequency response than a conventional 741 circuit and is ideal for active ﬁlter use. Natural frequencies of up to 10 kHz are readily achieved and up to 20 kHz is practical for some conﬁgurations. Q can range up to 50 with very good accuracy and up to 500 with reasonable response. The extra gain of the RC4156 at high frequencies gives the quad op amp an extra margin of performance in active-ﬁlter circuits.

(1,7,8,14)

Outputs

F1

(4) +V

(11)

-V

s

R1

4900

(2,6,9,13)

- Input

+ Input

(3,5,10,12)

65-0735

Q8

Q4

Q2

R3

18K

Q7

Q5

Q9

Q10

Q3

R4

22K

D2

C1

R9

30

R5

30K

Q13

Q11

Q15

Q12

Q16

Q17

Q14

R6

20

R7 20

R8

150

Q1

Q6

R2

10K

To

D1

10 REV. 1.0.1 6/13/01

RC4156/RC4157 PRODUCT SPECIFICATION

Mechanical Dimensions (continued)

14-Lead Plastic DIP Package

Symbol

A — .210 — 5.33

A1 .015 — .38 — A2 .115 2.93

B .014 .36

B1 .045 .070 1.14 1.78 C .008 .015 .20 .38

D .725 .795 18.42 20.19 D1 .005 — .13 — E E1 e eB — .430 — 10.92

L N

E1

Inches

Min. Max. Min. Max.

.195 4.95

.022 .56

.300 .325 7.62 8.26 .240 .280 6.10 7.11

.100 BSC 2.54 BSC

.115 .200 2.92 5.08

14 14 5

D

7

Millimeters

1

Notes

4

2

Notes:

1.

Dimensioning and tolerancing per ANSI Y14.5M-1982.

2.

"D" and "E1" do not include mold flashing. Mold flash or protrusions shall not exceed .010 inch (0.25mm).

3.

Terminal numbers are shown for reference only.

4.

"C" dimension does not include solder finish thickness.

5.

Symbol "N" is the maximum number of terminals.

8

D1

e

A

A1

B1

14

E

C

L

B

eB

REV. 1.0.1 6/13/01 11

PRODUCT SPECIFICATION RC4156/RC4157

Mechanical Dimensions (continued)

14-Lead SOIC Package

Symbol

A .053 .069 1.35 1.75

A1 .004 .010 0.10 0.25

B .013 0.33

C .008 .010 0.19 0.25 D .336 .345 8.54 8.76

E .150 .158 3.81 4.01

e

H

h

L .016 .050 0.40 1.27

N14 14

α

ccc .004 0.10——

14 8

Inches

Min. Max. Min. Max.

.020 0.51

.050 BSC 1.27 BSC

.228 .244 5.79 6.20

.010 .020 0.25 0.50

0° 8° 0° 8°

Millimeters

EH

17

Notes

5 2

2

3 6

Notes:

1.

Dimensioning and tolerancing per ANSI Y14.5M-1982.

2.

"D" and "E" do not include mold flash. Mold flash or protrusions shall not exceed .010 inch (0.25mm).

3.

"L" is the length of terminal for soldering to a substrate.

4.

Terminal numbers are shown for reference only.

5.

"C" dimension does not include solder finish thickness.

6.

Symbol "N" is the maximum number of terminals.

D

A

e

A1

SEATING

B

PLANE

– C –

LEAD COPLANARITY

ccc C

α

h x 45°

C

L

12 REV. 1.0.1 6/13/01

PRODUCT SPECIFICATION RC4156/RC4157

Ordering Information

Product Number Temperature Range Screening Package Package Marking

RC4156N 0° to 70°C Commercial 14 Pin Plastic DIP RC4156N

RC4157N 0° to 70°C Commercial 14 Pin Plastic DIP RC4157N

RC4156M 0° to 70°C Commercial 14 Pin Wide SOIC RC4156M

RC4157M 0° to 70°C Commercial 14 Pin Wide SOIC RC4157M

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2. A critical component in any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness.

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