Datasheet HV9105P, HV9105PJ, HV9108P, HV9108PJ Datasheet (Supertex)

Page 1
High-Voltage Switchmode Controllers with MOSFET
Ordering Information
HV9105 HV9108
IN
BV
DSS
200V 5.0 10V 120V ±1% 49% HV9105P HV9105PJ
200V 5.0 10V 120V ±1% 99% HV9108P HV9108PJ
R
DS(ON)
Min Max Voltage Duty Cycle 14 Pin Plastic DIP 20 Pin Plastic PLCC
Features
10 to 120V input range
200V, 5 output MOSFET
Current-Mode Control
High Efficiency
CCITT Compatible
Internal Start-up Circuit
Applications
DC/DC Converters
Distributed Power Systems
ISDN Equipment
PBX Systems
Modems
Feedback Max
General Description
The Supertex HV9105 and HV9108 are high-efficiency high voltage SMPS ICs intended for use in power converters requiring extreme efficiency at output power levels of 5.0W or less. The low supply current (0.5mA max) allows them to be used to build supplies which meet CCITT I.430 performance recommenda­tions (60% efficiency at .025W out).
The HV9105/08 provides all the functions necessary to build a single-switch current-mode converter of any common topology, with a minimum of external parts.
In addition to high efficiency, because it uses Supertex’s propri­etary high voltage BiCMOS/DMOS technology, the HV9105/08 offers numerous performance advantages when compared to conventional PWM ICs. Dynamic range is approximately 8 times wider than with bipolar ICs, both response speed and maximum clock rate are faster, and no external power resistors or zeners are necessary for high voltage starting.
Accessory circuits are included to provide either latching or nonlatching shutdown. When shut down, device dissipation is less than 4mW.
The HV9105/08 is intended for operation with input voltages from 10 to 120VDC.
Package OutlinesMOSFET Switch +V
Absolute Maximum Ratings
+VIN, Input Voltage 120V
V
DS
VDD, Logic Voltage 15.0V
Control Inputs -0.3V to VDD+0.3V
ID (Peak) 2.5A
Storage Temperature -65°C to 150°C
Power Dissipation, Plastic DIP 750mW
Power Dissipation, PLCC 1400mW
11/12/01
Supertex Inc. does not recommend the use of its products in life support applications and will not knowingly sell its products for use in such applications unless it receives an adequate "products liability indemnification insurance agreement." Supertex does not assume responsibility for use of devices described and limits its liability to the replacement of devices determined to be defective due to workmanship. No responsibility is assumed for possible omissions or inaccuracies. Circuitry and specifications are subject to change without notice. For the latest product specifications, refer to the Supertex website: http://www.supertex.com. For complete liability information on all Supertex products, refer to the most current databook or to the Legal/Disclaimer page on the Supertex website.
200V
For detailed circuit and application information, please refer to application notes AN-H13 and AN-H21 to AN-H24.
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Page 2
Electrical Characteristics
(V
= 10V, +V
DD
Symbol Parameters Min Typ Max Unit Conditions
Reference
= 48V, Discharge = -V
IN
= 0V, R
IN
= 820K, R
BIAS
= 910KΩ,TA = 25°C, unless otherwise specified)
OSC
HV9105/HV9108
V
REF
Z
OUT
I
SHORT
V
Output Voltage 3.92 4.00 4.08 V RL = 10M
Output Impedance
Short Circuit Current 100 130 µAV
Change in V
REF
Oscillator
f
MAX
f
OSC
Maximum Oscillator Frequency 1.0 3.0 MHz R
Initial Accuracy
Voltage Stability
Temperature Coefficient
PWM
D
MAX
D
MIN
Maximum Duty Cycle
Deadtime
Minimum Duty Cycle 0 %
Minimum Pulse Width 110 175 nsec Before Pulse Drops Out
Error Amplifier
V
FB
Feedback Voltage 3.96 4.00 4.04 V VFB Shorted to Comp
1
with Temperature 0.25 mV/°C
REF
2
1
1
1
HV9105 49.0 49.4 49.6 %
15 30 45 K
32 40 48 KHz
15 % 9.5V < V
170 ppm/°C
HV9108 99.0 99.4 99.6
1
HV9108 100 nsec
1
REF
OSC
= -V
= 0
IN
< 13.5V
DD
I
IN
V
OS
A
VOL
gbw Unity Gain Bandwidth
Z
OUT
I
SOURCE
I
SINK
PSRR Power Supply Rejection
Input Bias Current 25 500 nA V
Input Offset Voltage nulled at trim mV
Open Loop Voltage Gain
Output Impedance
1
1
1
Output Source Current -1.3 -1.0 mA V
Output Sink Current 50 80 µAV
1
Current Limit
V
SOURCE
t
d
Threshold Voltage 1.0 1.2 1.4 V V
Delay to Output
1
Pre-Regulator/Startup
+V
V
TH
V
LOCK
Notes:
1. Guaranteed by design. Not subject to production test.
2. Stray capacitance on OSC IN pin 5pF.
Allowable Input Voltage 120 V I
IN
Input Leakage Current 10 µAV
VDD Pre-regulator Turn-off 7.8 8.6 9.4 V I Threshold Voltage
Undervoltage Lockout 7.0 8.1 8.9 V RL = 100 from Drain to V
60 80 dB
0.5 0.8 MHz
See Fig. 2
See Fig. 1
150 200 ns V
= 4.0V
FB
= 3.4V
FB
= 4.5V
FB
= 0V, RL = 100
FB
= 1.5V, RL = 100
SOURCE
= 10µA
IN
> 9.4V
DD
= 10µA
PREREG
DD
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Page 3
Electrical Characteristics (Continued)
(V
= 10V, +V
DD
Symbol Parameters Min Typ Max Unit Conditions
Supply
= 48V, Discharge = -V
IN
= 0V, R
IN
= 820K, R
BIAS
= 910KΩ,TA = 25°C, unless otherwise specified)
OSC
HV9105/HV9108
I
DD
I
BIAS
V
DD
Supply Current 0.6 mA
Bias Current 7.5 µA
Operating Range 9.0 13.5 V
Logic
t
SD
t
SW
t
RW
t
LW
V
IL
V
IH
I
IH
I
IL
Shutdown Delay Time
Shutdown Pulse Width
RESET Pulse Width
Latching Pulse Width
Input Low Voltage 2.0 V
Input High Voltage 7.0 V
Input High Current 1.0 5.0 µAVIN = 10V
Input Low Current -25 -35 µAVIN = 0V
1
1
1
1
MOSFET Switch
BV
R
DS(ON)
I
DSS
C
DS
Note:
1. Guaranteed by design. Not subject to production test.
Breakdown Voltage 200 240 V V
DSS
Drain-to-Source On-resistance 3.5 5.0 V
OFF State Drain Leakage Current 10 µAV
Drain Capacitance 35 pF V
0.35 mA Shutdown = -V
50 100 ns V
50 ns
50 ns
25 ns
IN
= -V
SOURCE
SOURCE
I
= 100µA
D
SOURCE
SOURCE
V
DRAIN
= 25V, Shutdown = 0V
DS
IN
= Shutdown = 0V,
= 0V, ID = 100mA
= Shutdown = 0V,
= 100V
Truth Table
Shutdown Reset Output
H H Normal Operation
HH → L Normal Operation, No Change
L H Off, Not Latched
L L Off, Latched
L H L Off, Latched, No Change
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Switching Waveforms
1.5V
Source
Drain
Shutdown
Reset
V
DD
50%
0
t
d
0
V
DD
50%
0
V
DD
0
t
10ns
R
50%
HV9105/HV9108
t
V
DD
SHUTDOWN
50%
0
t
SD
V
DD
Drain
0
t
SW
90%90%
50%
t
LW
50%
t
RW
50%
10ns
F
, tF 10ns
t
R
Functional Block Diagram
COMP Discharge
Error Amplifier
+
4V
To Internal Circuits
+
8.6V
BIAS
+V
FB
14
(20)
V
10 (14)
REF
REF GEN
1 (2)
Current
Sources
6 (9)
V
DD
2 (3)
IN
Pre-regulator/Startup
13
(18)9(12)
2V
1.2V
8.1V
+
+
+
OSC
8
(11)
Current-mode
Comparator
C/L
Comparator
Undervoltage Comparator
In
OSC
OSC
Out
(10)
R
S
7
TQ
9108
Q
V
DD
9105
(5) 3
Drain
(8) 5
-V
IN
V
DD
S
Q
R
(7) 4
(16) 11
(17) 12
Source
Shutdown
Reset
Pin numbers in parentheses are for PLCC package.
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+
Reference
V
1
V
2
0.1V swept 10Hz – 1MHz
0.1µF
10.0V
4.00V
100K1%
100K1%
PSRR
Typical Performance Curves
HV9105/HV9108
Fig. 1
Fig. 2
PSRR – Error Amplifier and Reference
0
-10
-20
-30
-40
(dB)()
-50
-60
-70
-80
100KHz1KHz10Hz 100Hz 10KHz 1MHz
Fig. 3
80
70
60
50
40
30
Gain (dB)
20
10
0
-10
100Hz 1KHz 10KHz
Error Amplifier
Open Loop Gain/Phase
100KHz 1MHz
240°
180°
120°
60°
-60°
-120°
-180°
0°
Phase
Frequency
Error Amplifier Output Impedance (Z0)
6
10
5
10
4
10
3
10
Fig. 4
1M
Output Switching Frequency
vs. Oscillator Resistance
HV9105
HV9108
Test Circuits
+10V
(V
)
DD
(FB)
GND
(–V
)
IN
2
10
10
1.0
0.1
.01
100Hz 1KHz 10KHz
Error Amp Z
Reference
0.1µF
100k
OUT
f (Hz)
100KHz
OUT
1MHz
10MHz
10k
10k
100 k
R
OSC
1M
()
1.0V swept 100Hz – 2.2MHz
60.4K
+
Tektronix
P6021 (1 turn
V
1
secondary)
V
2
40.2K
NOTE: Set Feedback Voltage so that V
COMP
= V
± 1mV before connecting transformer
DIVIDE
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Page 6
Technical Description
HV9105/HV9108
Preregulator
The preregulator/startup circuit for the HV9105/08 consists of a high-voltage N-channel depletion-mode DMOS transistor driven by an error amplifier to form a controlled current path between the
terminal and the VDD terminal of the HV9105/08. Maximum
V
IN
current (about 20 mA) occurs when V
rises. This path shuts off altogether when VDD rises to
as V
DD
somewhere between 7.8 and 9.4V, so that if V
= 0, with current reducing
DD
is held at 10 or
DD
12V by an external source (generally the supply the chip is controlling) no current other than leakage is drawn through the high voltage transistor. This minimizes dissipation.
An external capacitor between VDD and VSS is generally required to store energy used by the chip during the time between shutoff of the high voltage path and the V
supplys output rising enough
DD
to take over the powering of the chip. This capacitor generally also serves as the output filter capacitor for that output from the supply.
1.0µF is generally sufficient to assure against double-starting. Capacitors as small as 0.1µF can work when faster response from the V
line is required. The chosen capacitor should have very
DD
good high frequency characteristics and be mounted so that the sum of the lead length between capacitor and IC for both leads is less than 2.5 cm. Stacked polyester or ceramic capacitors work well. Electrolytic capacitors are generally not suitable.
A common resistor divider string is used to monitor V
for both
DD
the undervoltage lockout circuit and the shutoff circuit of the high voltage FET. Setting the undervoltage sense point about 0.6V lower on the string than the FET shutoff point guarantees that the undervoltage lockout always releases before the FET shuts off.
Bias Circuit
An external bias resistor, connected between the bias pin and V is required by the HV9105/08 to set currents in a series of current mirrors used by the analog sections of the chip. Nominal external bias current requirement is 7.5µA, which can be set by a 820K to 1.3M resistor if a 10V V resistor if a 12V V
is used. A precision resistor is NOT required;
DD
is used, or a 1.2M to 2.0M
DD
± 5% is fine.
For extremely low power operation, the value of bias current can be reduced to as low as 4.0µA by further increases in the value of the bias resistor.
SS
Clock Oscillator
The clock oscillator of the HV9105/08 consists of a ring of CMOS inverters, timing capacitors, a capacitor discharge FET, and, in the 50% maximum duty cycle version, a frequency dividing flip­flop. A single external resistor between the OSC In and OSC Out pins is required to set oscillator frequency (see Fig. 4). For the 50% maximum duty cycle versions the ‘Discharge’ pin is internally connected to GND. For the 99% duty cycle version, ‘Discharge’ can either be connected to V through a resistor used to set a deadtime.
One difference exists between the Supertex HV9105/08 and competitive 9105 parts. The oscillator of the Supertex HV9105/08 is shut off when a shutoff command is received. This saves about 100µA of quiescent current, which aids in the construction of power supplies to meet CCITT specification I.430, and in other situations where an absolute minimum of quiescent power dissi­pation is required.
directly or connected to V
SS
SS
Reference
The reference section of the HV9105/08 consists of a stable bandgap reference followed by a buffer amplifier which scales the voltage up to approximately 4.0V. The scaling resistors of the reference buffer amplifier are trimmed during manufacture so that the output of the error amplifier when connected in a gain of -1 configuration is as close to 4.000V as possible. This nulls out any input offset of the error amplifier. As a consequence, even though the observed reference voltage of a specific part may not be exactly 4.0V, the feedback voltage required for proper regulation will be 4.0V.
A resistor of approximately 50K is placed internally between the output of the reference buffer amplifier and the circuitry it feeds (reference output pin and non-inverting input to the error ampli­fier). This allows overriding the internal reference with a low­impedance voltage source 6.0V. In general, because the refer­ence voltage of the Supertex HV9105/08 is not noisy, as some previous devices have been, overriding the reference should seldom be necessary.
Because the reference is a high impedance node, and usually there will be significant electrical noise near it, a bypass capacitor between the reference pin and V
is strongly recommended. The
SS
reference buffer amplifier is intentionally compensated to be stable with a capacitive load of 0.01 to 0.1µF.
Error Amplifier
The error amplifier is a true low-power differential input opera­tional amplifier intended for around-the-amplifier compensation. It is of mixed CMOS-bipolar construction: a PMOS input stage is used so the common-mode range includes ground and the input impedance is very high. This is followed by bipolar gain stages which provide high gain without the electrical noise of all-MOS amplifiers. The amplifier is unity-gain stable.
Current Sense Comparators
The HV9105/08 uses a true dual comparator system with inde­pendent comparators for modulation and current limiting. This allows the designer greater latitude in compensation design, as there are no clamps (except ESD protection) on the compensa­tion pin. Like the error amplifier, the comparators are of low-noise BiCMOS construction.
Remote Shutdown
The shutdown and reset pins can be used to perform either latching or non-latching shutdown of a converter as required. These pins have internal current source pull-ups so they can be driven from open-drain logic. When not used, they should be left open, or connected to V
DD
.
Main Switch
The main switch is a normal N-channel power MOSFET. Unlike the situation with competitive devices, the body diode can be used if desired without destroying the chip.
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Page 7
Pinout
HV9105/HV9108
BIAS
+V
Drain
Source
–V
V
DD
OSC Out
1
2
IN
3
4
5
IN
6
7
14 Pin DIP Package
14
13
12
11
10
9
8
Feedback
COMP
Reset
Shutdown
V
REF
Discharge
OSC In
NC
Feedback
NC
BIAS
+V
COMP
Reset
Shutdown
18 17 16
19
20
1
2
3
IN
4 5 6
NC
15 14
NC
Drain
NC
7 8
Source
–V
REF
V
IN
NC
13
Discharge
12
OSC In
11
OSC Out
10
V
9
DD
20-pin PJ Package
top view
©2001 Supertex Inc. All rights reserved. Unauthorized use or reproduction prohibited.
11/12/01
1235 Bordeaux Drive, Sunnyvale, CA 94089
TEL: (408) 744-0100 FAX: (408) 222-4895
7
www.supertex.com
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