Low offset voltage: 50 μV maximum
Low offset voltage drift: 0.6 μV/°C maximum
Very low bias current: 100 pA maximum
Very high open-loop gain: 2000 V/mV minimum
Low supply current (per amplifier): 625 μA maximum
Operates from ±2 V to ±20 V supplies
High common-mode rejection: 120 dB minimum
APPLICATIONS
Strain gage and bridge amplifiers
High stability thermocouple amplifiers
Instrumentation amplifiers
Photocurrent monitors
High gain linearity amplifiers
Long-term integrators/filters
Sample-and-hold amplifiers
Peak detectors
Logarithmic amplifiers
Battery-powered systems
Precision Operational Amplifier
OP297
PIN CONFIGURATION
1
OUTA
2
–INA
+INA
A
3
4
Figure 1.
60
40
20
0
–20
INPUT CURRENT (pA)
–40
8
V+
OUTB
7
B
6
–INB
5
+INBV–
00300-001
V
= ±15V
S
V
= 0V
CM
I
–
B
IB+
I
OS
GENERAL DESCRIPTION
The OP297 is the first dual op amp to pack precision performance into the space saving, industry-standard 8-lead SOIC
package. The combination of precision with low power and
extremely low input bias current makes the dual OP297 useful
in a wide variety of applications.
Precision performance of the OP297 includes very low offset
(less than 50 V) and low drift (less than 0.6 V/°C). Openloop gain exceeds 2000 V/mV, ensuring high linearity in every
application.
Errors due to common-mode signals are eliminated by the
common-mode rejection of over 120 dB, which minimizes
offset voltage changes experienced in battery-powered systems.
The supply current of the OP297 is under 625 A.
The OP297 uses a super-beta input stage with bias current
cancellation to maintain picoamp bias currents at all temperatures. This is in contrast to FET input op amps whose bias
currents start in the picoamp range at 25°C, but double for
every 10°C rise in temperature, to reach the nanoamp range
above 85°C. Input bias current of the OP297 is under 100 pA at
25°C and is under 450 pA over the military temperature range
per amplifier. This part can operate with supply voltages as low
as ±2 V.
–60
–75–50–250255075100125
TEMPERATURE (° C)
00300-002
Figure 2. Low Bias Current over Temperature
400
1200 UNITS
300
200
NUMBER OF UNI TS
100
0
–100 –80 –60 –40 –20020406080 100
INPUT OFFSET VOLTAGE (µV)
T
A
V
S
V
CM
= 25°C
= ±15V
= 0V
00300-003
Figure 3. Very Low Offset
Combining precision, low power, and low bias current, the
OP297 is ideal for a number of applications, including instrumentation amplifiers, log amplifiers, photodiode preamplifiers,
and long term integrators. For a single device, see the OP97; for
a quad device, see the OP497.
Rev. G
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.
OP297E OP297F OP297G
Parameter Symbol Conditions Min Typ Max Min Typ Max Min Typ Max Unit
Input Offset Voltage VOS 25 50 50 100 80 200 µV
Long-Term Input Voltage
Stability
Input Offset Current IOS VCM = 0 V 20 100 35 150 50 200 pA
Input Bias Current IB VCM = 0 V +20 ±100 +35 ±150 +50 ±200 pA
Input Noise Voltage en
Input Noise Voltage Density en f
f
Input Noise Current Density in f
Input Resistance
Differential Mode RIN 30 30 30 MΩ
Common-Mode R
Large Signal Voltage Gain AVO V
Input Voltage Range
1
Common-Mode Rejection CMRR VCM = ±13 V 120 140 114 135 114 135 dB
Power Supply Rejection PSRR VS = ±2 V to
Output Voltage Swing V
R
Supply Current per Amplifier ISY No load 525 625 525 625 525 625 µA
Supply Voltage VS Operating range ±2 ±20 ±2 ±20 ±2 ±20 V
Slew Rate SR 0.05 0.15 0.05 0.15 0.05 0.15 V/µs
Gain Bandwidth Product GBWP AV = +1 500 500 500 kHz
Channel Separation CS V
OP297E OP297F OP297G
Parameter Symbol Conditions Min Typ Max Min Typ Max Min Typ Max Unit
Input Offset Voltage VOS 35 100 80 300 110 400 V
Average Input Offset Voltage Drift TCVOS 0.2 0.6 0.5 2.0 0.6 2.0 V/°C
Input Offset Current IOS VCM = 0 V 50 450 80 750 80 750 pA
Input Bias Current IB VCM = 0 V +50 ±450 +80 ±750 +80 ±750 pA
Large Signal Voltage Gain AVO V
Input Voltage Range
1
VCM ±13 ±13.5 ±13 ±13.5 ±13 ±13.5 V
OUT
= 2 kΩ
R
L
= ±10 V,
Common-Mode Rejection CMRR VCM = ±13 114 130 108 130 108 130 dB
Power Supply Rejection PSRR VS = ±2.5 V to
±20 V
Output Voltage Swing V
RL = 10 kΩ ±13 ±13.4 ±13 ±13.4 ±13 ±13.4 V
OUT
Supply Current per Amplifier ISY No load 550 750 550 750 550 750 A
Supply Voltage VS Operating range ±2.5 ±20 ±2.5 ±20 ±2.5 ±20 V
1
Guaranteed by CMR test.
1200 3200 1000 2500 800 2500 V/mV
114 108 108 dB
Rev. G | Page 3 of 16
Page 4
OP297
ABSOLUTE MAXIMUM RATINGS
Table 3.
Parameter Rating
Supply Voltage ±20 V
Input Voltage1 ±20 V
Differential Input Voltage1 40 V
Output Short-Circuit Duration Indefinite
Storage Temperature Range
Z-Suffix −65°C to +175°C
P-Suffix, S-Suffix −65°C to +150°C
Operating Temperature Range
OP297E (Z-Suffix) −40°C to +85°C
OP297F, OP297G (P-Suffix, S-Suffix) −40°C to +85°C
Junction Temperature
Z-Suffix −65°C to +175°C
P-Suffix, S-Suffix −65°C to +150°C
Lead Temperature (Soldering, 60 sec) 300°C
1
For supply voltages less than ±20 V, the absolute maximum input voltage is
equal to the supply voltage.
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
THERMAL RESISTANCE
θJA is specified for worst-case mounting conditions, that is, θJA
is specified for device in socket for CERDIP and PDIP packages; θ
is specified for device soldered to printed circuit board
Figure 5. Typical Distribution of Input Offset Voltage
250
1200 UNITS
200
150
100
NUMBER OF UNITS
50
0
–100 –80 –60 –40 –20020406080 100
INPUT BIAS CURRENT (pA)
TA = 25°C
V
= ±15V
S
V
CM
Figure 6. Typical Distribution of Input Bias Current
400
1200 UNITS
300
TA = 25°C
V
= ±15V
S
V
CM
= 0V
= 0V
–60
0300-005
–75–50–250255075100125
TEMPERATURE ( °C)
00300-008
Figure 8. Input Bias, Offset Current vs. Temperature
60
= ±15V
V
S
V
= 0V
CM
40
I
–
B
20
0
INPUT CURRENT (p A)
–20
–40
00300-006
–15–10–5051015
COMMON-MODE VOLTAGE (V)
IB+
I
OS
00300-009
Figure 9. Input Bias, Offset Current vs. Common-Mode Voltage
±3
TA = 25°C
V
= ±15V
S
V
= 0V
CM
±2
200
NUMBER OF UNIT S
100
0
–100 –80 –60 –40 –20020406080 100
INPUT OFFSET CURRENT ( pA)
Figure 7. Typical Distribution of Input Offset Current
00300-007
Rev. G | Page 5 of 16
±1
DEVIATION FROM FI NAL VALUE (µV)
0
01234 5
TIME AFT ER POWER APP LIED (Mi nutes)
Figure 10. Input Offset Voltage Warm-Up Drift
0300-010
Page 6
OP297
10k
BALANCED OR UNBALANCED
V
= ±15V
S
V
= 0V
CM
1k
100
–55°C ≤ TA ≤ +125°C
EFFECTIVE OFFSET VOLTAGE (µV)
TA = +25°C
10
1001k10k100k1M
1010M
SOURCE RESIST ANCE (Ω)
Figure 11. Effective Offset Voltage vs. Source Resistance
0300-011
1300
NO LOAD
TOTAL SUPPLY CURRENT (µA)
1200
1100
1000
900
800
0
±5±10±15
SUPPLY VOLTAGE (V)
= +125°C
T
A
= +25°C
T
A
TA = –55°C
Figure 14. Total Supply Current vs. Supply Voltage
±20
00300-014
100
BALANCED OR UNBALANCED
V
= ±15V
S
V
= 0V
CM
10
1
EFFECTIVE OFFSET VOLTAGE DRIFT (µV/°C)
0.1
100100M
1k10k10 0k1M10M
SOURCE RESIST ANCE (Ω)
Figure 12. Effective TCVOS vs. Source Resistance
35
30
25
20
15
10
VS = ±15V
5
OUTPUT SHORTED
0
TO GROUND
–5
–10
–15
–20
SHORT-CIRCUIT CURRENT (mA)
–25
–30
–35
01234
TIME FROM OUTPUT SHORT (Minutes)
TA = –55°C
TA = +25°C
TA = +125°C
TA = +125°C
TA = +25°C
TA = –55°C
Figure 13. Short-Circuit Current vs. Time, Temperature
160
140
120
100
80
COMMON-MO DE REJECTIO N (dB)
60
40
0300-012
1101001k10k100k1M
FREQUENCY (Hz)
TA = 25°C
V
= ±15V
S
00300-015
Figure 15. Common-Mode Rejection vs. Frequency
160
140
120
100
80
60
POWER SUPPLY REJECTI ON (dB)
40
20
00300-013
1101001k10k100k1M
0.1
FREQUENCY (Hz)
TA = 25°C
V
= ±15V
S
ΔV
= 10V p-p
S
00300-016
Figure 16. Power Supply Rejection vs. Frequency
Rev. G | Page 6 of 16
Page 7
OP297
1k
100
10
TA = 25°C
V
= ±2V TO ±15V
S
VOLTAGE
NOISE
CURRENT
NOISE
1k
100
10
0
RL = 10kΩ
V
= ±15V
S
V
= 0V
CM
TA = +125°C
TA = +25°C
TA = –55°C
1
10M
CURRENT NOISE DENSITY (fA/ √Hz)
00300-017
DIFFERENTIAL INPUT VOLTAGE (10µV/DIV)
–15
Figure 20. Differential Input Voltage vs. Output Voltage
35
TA = 25°C
V
= ±15V
S
30
A
VCL
1% THD
f
= 1kHz
OUT
25
20
15
10
OUTPUT SWING (V p-p)
5
0
101001k10k
00300-018
VOLTAGE NOISE DENSI TY (nV/ √Hz)
1
11
10100k
FREQUENCY (Hz)
Figure 17. Voltage Noise Density and Current Noise Density vs. Frequency
10
TA = 25°C
= ±2V TO ±20V
V
S
1
10Hz
1kHz
1M100k10k1k100
TOTAL NOISE DENSITY (nV/√Hz)
0.01
0.1
1kHz
10Hz
SOURCE RESISTANCE (Ω)
Figure 18. Total Noise Density vs. Source Resistance
10k
TA = –55°C
TA = +25°C
TA = +125°C
1k
VS = ±15V
V
= ±10V
OUT
35
30
25
20
15
–10–5051015
= +1
OUTPUT VOLT AGE (V)
LOAD RESISTANCE (Ω)
Figure 21. Output Swing vs. Load Resistance
TA = 25°C
V
= ±15V
S
A
= +1
VCL
1% THD
f
= 1kHz
OUT
R
= 10kΩ
L
00300-020
00300-021
OPEN-LOOP GAIN (V/mV)
100
1
432
LOAD RESIST ANCE (kΩ)
Figure 19. Open-Loop Gain vs. Load Resistance
51020
87659
0300-019
Rev. G | Page 7 of 16
10
OUTPUT SWING (V p-p)
5
0
1001k10k100k
FREQUENCY (Hz)
Figure 22. Maximum Output Swing vs. Frequency
00300-022
Page 8
OP297
100
80
GAIN
60
PHASE
40
20
OPEN-LOOP GAIN (dB)
0
–20
–40
1k10k100k1M10M100
FREQUENCY (Hz)
Figure 23. Open-Loop Gain, Phase vs. Frequency
70
TA = 25°C
V
= ±15V
S
60
A
= +1
VCL
V
= 100mV p-p
OUT
50
40
30
OVERSHOOT (%)
20
–EDGE
VS = ±15V
C
R
TA = –55°C
TA = +125°C
+EDGE
= 30pF
L
= 1MΩ
L
90
135
180
225
270
PHASE SHIFT (Degrees)
00300-023
1k
TA = 25°C
V
= ±15V
S
100
10
1
0.1
OUTPUT IMPEDANCE (Ω)
0.01
0.001
1001k10k100k1M10
FREQUENCY (Hz)
00300-025
Figure 25. Open-Loop Output Impedance vs. Frequency
10
0
10100
LOAD CAPACITANCE ( pF)
1k10k
Figure 24. Small Signal Overshoot vs. Load Capacitance
0300-024
Rev. G | Page 8 of 16
Page 9
OP297
G
A
APPLICATIONS INFORMATION
Extremely low bias current over a wide temperature range
makes the OP297 attractive for use in sample-and-hold
amplifiers, peak detectors, and log amplifiers that must operate
over a wide temperature range. Balancing input resistances is
unnecessary with the OP297. Offset voltage and TCV
OS
are
degraded only minimally by high source resistance, even
when unbalanced.
The input pins of the OP297 are protected against large differential voltage by back-to-back diodes and current-limiting resistors.
Common-mode voltages at the inputs are not restricted and can
vary over the full range of the supply voltages used.
The OP297 requires very little operating headroom about the
supply rails and is specified for operation with supplies as low as
2 V. Typically, the common-mode range extends to within 1 V
of either rail. The output typically swings to within 1 V of the
rails when using a 10 k load.
AC PERFORMANCE
The ac characteristics of the OP297 are highly stable over its full
operating temperature range. Unity gain small signal response is
shown in Figure 26. Extremely tolerant of capacitive loading on
the output, the OP297 displays excellent response with 1000 pF
loads (see Figure 27).
100
90
100
90
10
0%
20mV
Figure 28. Large Signal Transient Response (A
5µs
VCL
= +1)
0300-028
GUARDING AND SHIELDING
To maintain the extremely high input impedances of the OP297,
care is taken in circuit board layout and manufacturing. Board
surfaces must be kept scrupulously clean and free of moisture.
Conformal coating is recommended to provide a humidity
barrier. Even a clean PCB can have 100 pA of leakage currents
between adjacent traces, therefore guard rings should be used
around the inputs. Guard traces operate at a voltage close to that
on the inputs, as shown in Figure 29, to minimize leakage
currents. In noninverting applications, the guard ring should be
connected to the common-mode voltage at the inverting input.
In inverting applications, both inputs remain at ground, so the
guard trace should be grounded. Guard traces should be placed
on both sides of the circuit board.
UNITY-GAIN FOLLOWER
NONINVERTIN
MPLIFIER
10
10
0%
20mV5µs
Figure 26. Small Signal Transient Response (C
100
90
10
0%
20mV
Figure 27. Small Signal Transient Response (C
= 100 pF, A
L
5µs
= 1000 pF, A
L
VCL
VCL
00300-026
= +1)
00300-027
= +1)
Rev. G | Page 9 of 16
–
1/2
OP297
+
INVERTING AMPLIFIER
8
–
1/2
OP297
+
B
Figure 29. Guard Ring Layout and Considerations
–
1/2
OP297
+
MINI-DIP
BOTTOM VIEW
1
A
00300-029
Page 10
OP297
OPEN-LOOP GAIN LINEARITY
The OP297 has both an extremely high gain of 2000 V/mV
minimum and constant gain linearity. This enhances the
precision of the OP297 and provides for very high accuracy in
high closed-loop gain applications. Figure 30 illustrates the
typical open-loop gain linearity of the OP297 over the military
temperature range.
RL = 10kΩ
= ±15V
V
S
= 0V
V
CM
0
DIFFERENTIAL INPUT VOLTAGE (10µV/DIV)
–15
–10–5051015
TA = +125°C
TA = +25°C
TA = –55°C
OUTPUT VOLT AGE (V)
Figure 30. Open-Loop Linearity of the OP297
00300-030
Rev. G | Page 10 of 16
Page 11
OP297
V
APPLICATION CIRCUITS
PRECISION ABSOLUTE VALUE AMPLIFIER
The circuit in Figure 31 is a precision absolute value amplifier
with an input impedance of 30 MΩ. The high gain and low
TCV
of the OP297 ensure accurate operation with microvolt
OS
input signals. In this circuit, the input always appears as a
common-mode signal to the op amps. The CMR of the OP297
exceeds 120 dB, yielding an error of less than 2 ppm.
+15V
C2
0.1µF
5
6
R2
2kΩ
R3
1kΩ
–
1/2
OP297
+
7
0V < V
OUT
< 10V
R1
1kΩ
C1
30pF
8
2
–
1/2
–15V
4
C3
0.1µF
1
V
IN
+
OP297
3
D1
1N4148
D2
1N4148
Figure 31. Precision Absolute Value Amplifier
PRECISION CURRENT PUMP
Maximum output current of the precision current pump shown
in Figure 32 is ±10 mA. Voltage compliance is ±10 V with
±15 V supplies. Output impedance of the current transmitter
exceeds 3 M with linearity better than 16 bits. R1 through R4
should be matched resistors.
R3
10kΩ
R1
10kΩ
2
–
3
R4
10kΩ
1/2
OP297
+
7
R2
V
IN
10kΩ
Figure 32. Precision Current Pump
1
+15V
8
1/2
OP297
–15V
R5
100kΩ
+
–
5
6
R5
V
IN
= = = 10mA/V
I
OUT
I
OUT
10mA MAX
V
IN
100Ω
00300-032
00300-031
PRECISION POSITIVE PEAK DETECTOR
In Figure 33, the CH must be of polystyrene, Teflon®, or
polyethylene to minimize dielectric absorption and leakage.
The droop rate is determined by the size of C
and the bias
H
current of the OP297.
1kΩ
+15V
1N4148
2
–
OP297
1kΩ
V
3
IN
+
RESET
1/2
1
1kΩ
C
H
1kΩ
2N930
Figure 33. Precision Positive Peak Detector
6
–
OP297
5
+
1/2
–15V
0.1µF
0.1µF
7
V
OUT
SIMPLE BRIDGE CONDITIONING AMPLIFIER
Figure 34 shows a simple bridge conditioning amplifier using
the OP297. The transfer function is
R
R
Δ
V
REF
6
–
OP297
5
+
Δ+
1/2
⎞
⎟
RR
⎠
R + ΔR
8
4
F
R
should
F
R
F
2
–
1/2
1
V
ΔR
OUT
R
F
R
00300-034
OP297
3
+
7
V
= V
OUT
REF
R + ΔR
OUT
⎝
⎛
VV
=
⎜
REF
The REF43 provides an accurate and stable reference voltage for
the bridge. To maintain the highest circuit accuracy, R
be 0.1% or better with a low temperature coefficient.
15
REF43
4
Figure 34. Simple Bridge Condition Amplifier Using the OP297
00300-033
Rev. G | Page 11 of 16
Page 12
OP297
NONLINEAR CIRCUITS
Due to its low input bias currents, the OP297 is an ideal log
amplifier in nonlinear circuits such as the square and square
root circuits shown in Figure 35 and Figure 36. Using the
squaring circuit of Figure 35 as an example, the analysis begins
by writing a voltage loop equation across Transistor Q1,
Transistor Q2, Transistor Q3, and Transistor Q4.
⎞
Vlnlnlnln
T1
⎞
⎞
⎛
I
IN
⎟
⎜
⎟
⎜
I
S1
⎠
⎝
⎛
I
IN
⎟
⎜
V
+
T2
⎟
⎜
I
S
2
⎠
⎝
⎛
I
OUT
⎟
⎜
V
=
T3
⎟
⎜
I
S3
⎠
⎝
All the transistors of the MAT04 are precisely matched and at
the same temperature, so the I
2ln
I
IN
= lnI
OUT
+ lnI
and VT terms cancel, where
S
REF
= ln(I
OUT
× I
REF
)
Exponentiating both sides of the equation leads to
2
()
I
I
OUT
IN
=
I
REF
Op Amp A2 forms a current-to-voltage converter, which gives
V
= R2 × I
OUT
equation for I
V
OUT
. Substituting (VIN/R1) for IIN and the previous
OUT
yields
OUT
2
⎞
⎛
⎜
=
⎜
⎝
V
R2
⎛
⎞
IN
⎟
⎜
⎟
I
⎝
REF
⎠
R1
⎟
⎠
A similar analysis made for the square root circuit of Figure 36
leads to its transfer function
()( )
IV
1
Q1
3
V+
8
–
1/2
OP297
+
4
V–
R1
REFIN
C2
100pF
R2
33kΩ
6
–
1/2
I
OUT
OP297
5
MAT04E
9
R3
50kΩ
+
–15V
R4
50kΩ
I
REF
7
6
Q2
5
8
Q3
10
1
=
R2V
OUT
2
C1
R1
33kΩ
V
IN
100pF
2
3
Figure 35. Squaring Amplifier
⎛
I
REF
⎜
V
+
T4
⎜
I
S4
⎝
7
V
OUT
14
13
Q4
12
R2
33kΩ
C2
100pF
6
–
1/2
7
V
14
12
R4
50kΩ
I
REF
OUT
00300-036
I
OUT
OP297
5
+
MAT04E
1
⎞
⎟
⎟
⎠
R1
33kΩ
V
IN
C1
100pF
2
3
V+
8
–
1/2
OP297
+
4
V–
Q1
3
7
6
Q2
5
10
1
13
Q4
8
9
Q3
R3
50kΩ
–15V
Figure 36. Square Root Amplifier
In these circuits, I
is a function of the negative power supply.
REF
To maintain accuracy, the negative supply should be well regulated. For applications where very high accuracy is required, a
voltage reference can be used to set I
REF
.
An important consideration for the squaring circuit is that a
sufficiently large input voltage can force the output beyond the
operating range of the output op amp. Resistor R4 can be
changed to scale I
or R1; R2 can be varied to keep the output
REF
voltage within the usable range.
Unadjusted accuracy of the square root circuit is better than
0.1% over an input voltage range of 100 mV to 10 V. For a
similar input voltage range, the accuracy of the squaring circuit
is better than 0.5%.
00300-035
Rev. G | Page 12 of 16
Page 13
OP297
OUTLINE DIMENSIONS
0.400 (10.16)
0.365 (9.27)
0.355 (9.02)
0.210 (5.33)
0.150 (3.81)
0.130 (3.30)
0.115 (2.92)
0.022 (0.56)
0.018 (0.46)
0.014 (0.36)
MAX
8
1
0.100 (2.54)
0.070 (1.78)
0.060 (1.52)
0.045 (1.14)
BSC
5
4
0.280 (7.11)
0.250 (6.35)
0.240 (6.10)
0.015
(0.38)
MIN
SEATING
PLANE
0.005 (0.13)
MIN
0.060 (1.52)
MAX
0.015 (0.38)
GAUGE
PLANE
0.325 (8.26)
0.310 (7.87)
0.300 (7.62)
0.430 (10.92)
MAX
0.195 (4.95)
0.130 (3.30)
0.115 (2.92)
0.014 (0.36)
0.010 (0.25)
0.008 (0.20)
CONTROLL ING DIMENS IONS ARE IN INCHES; MILLIMETER DI MENSIONS
(IN PARENTHESES) ARE ROUNDED-OF F INCH EQUI VALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRI ATE FOR USE IN DESIGN.
CORNER LEADS MAY BE CONFIGURED AS WHOL E OR HALF LEADS.
CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.
CONTROLL ING DIMENSI ONS ARE IN MILLIMETERS; INCH DI MENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRI ATE FOR USE IN DESIGN.
5.00 (0.1968)
4.80 (0.1890)
85
1
1.27 (0.0500)
SEATING
PLANE
COMPLIANT TO JEDEC STANDARDS MS-012-A A
BSC
6.20 (0.2441)
5.80 (0.2284)
4
1.75 (0.0688)
1.35 (0.0532)
0.51 (0.0201)
0.31 (0.0122)
0.25 (0.0098)
0.17 (0.0067)
0.50 (0.0196)
0.25 (0.0099)
8°
0°
1.27 (0.0500)
0.40 (0.0157)
45°
012407-A
Figure 39. 8-Lead Standard Small Outline Package [SOIC_N]
Narrow Body
S-Suffix (R-8)
Dimensions shown in millimeters and (inches)
ORDERING GUIDE
Model Temperature Range Package Description Package Options
OP297EZ −40°C to +85°C 8-Lead CERDIP Q-8 (Z-Suffix)
OP297FP −40°C to +85°C 8-Lead PDIP N-8 (P-Suffix)
OP297FPZ
OP297FS −40°C to +85°C 8-Lead SOIC_N R-8 (S-Suffix)
OP297FS-REEL −40°C to +85°C 8-Lead SOIC_N R-8 (S-Suffix)
OP297FS-REEL7 −40°C to +85°C 8-Lead SOIC_N R-8 (S-Suffix)
OP297FSZ
OP297FSZ-REEL
OP297FSZ-REEL7
OP297GP −40°C to +85°C 8-Lead PDIP N-8 (P-Suffix)
OP297GPZ
OP297GS −40°C to +85°C 8-Lead SOIC_N R-8 (S-Suffix)
OP297GS-REEL −40°C to +85°C 8-Lead SOIC_N R-8 (S-Suffix)
OP297GS-REEL7 −40°C to +85°C 8-Lead SOIC_N R-8 (S-Suffix)
OP297GSZ
OP297GSZ-REEL
OP297GSZ-REEL7