ANALOG DEVICES LTC 6101 BCS5 Datasheet

LTC6101/LTC6101HV

TO µP

6101 TA01

LTC2433-1

LTC6101HV

R

OUT

4.99k

R

IN

100

V

OUT

V

+

V

–

OUT

–IN

+IN

V

SENSE

I

LOAD

5V TO 105V

1µF

5V

L
O
A
D

–

+

–

+

V

OUT

= • V

SENSE

= 49.9V

SENSE

R

OUT

R

IN

5.5V
5V

0.5V
0V

500ns/DIV

6101 TA01b

TA = 25°C
V

+

= 12V

R

IN

= 100

R

OUT

= 5k

V

SENSE

+

= V

+

V

OUT

V

SENSE

–

ΔV

SENSE

–

= 100mV

I

OUT

= 100µA

I

OUT

= 0

High Voltage,

High-Side Current Sense

Amplifi er in SOT-23

FEATURES

n

Supply Range:
5V to 100V, 105V Absolute Maximum (LTC6101HV)
4V to 60V, 70V Absolute Maximum (LTC6101)

n

Low Offset Voltage: 300μV Max

n

Fast Response: 1μs Response Time (0V to 2.5V on
a 5V Output Step)

n

Gain Confi gurable with 2 Resistors

n

Low Input Bias Current: 170nA Max

n

PSRR: 118dB Min

n

Output Current: 1mA Max

n

Low Supply Current: 250A, V S = 12V

n

Specifi ed Temperature Range: –40°C to 125°C

n

Operating Temperature Range: –55°C to 125°C

n

Low Profi le (1mm) SOT-23 (ThinSOT™) Package

APPLICATIONS

n

Current Shunt Measurement

n

Battery Monitoring

n

Remote Sensing

n

Power Management

L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks and
ThinSOT is a trademark of Linear Technology Corporation. All other trademarks are the property
of their respective owners.

DESCRIPTION

The LTC®6101/LTC6101HV are versatile, high voltage, high
side current sense amplifi ers. Design fl exibility is provided
by the excellent device characteristics; 300V Max offset
and only 375A (typical at 60V) of current consumption.
The LTC6101 operates on supplies from 4V to 60V and
LTC6101HV operates on supplies from 5V to 100V.

The LTC6101 monitors current via the voltage across an
external sense resistor (shunt resistor). Internal circuitry
converts input voltage to output current, allowing for a
small sense signal on a high common mode voltage to
be translated into a ground referenced signal. Low DC
offset allows the use of a small shunt resistor and large
gain-setting resistors. As a result, power loss in the shunt
is reduced.

The wide operating supply range and high accuracy make
the LTC6101 ideal for a large array of applications from
automotive to industrial and power management. A maxi­mum input sense voltage of 500mV allows a wide range
of currents to be monitored. The fast response makes the
LTC6101 the perfect choice for load current warnings and
shutoff protection control. With very low supply current,
the LTC6101 is suitable for power sensitive applications.

The LTC6101 is available in 5-lead SOT-23 and 8-lead
MSOP packages.

TYPICAL APPLICATION

16-Bit Resolution Unidirectional Output into LTC2433 ADC

Step Response

6101fh

1

LTC6101/LTC6101HV

ABSOLUTE MAXIMUM RATINGS

(Note 1)

Total Supply Voltage (V+ to V–)

LTC6101 ............................................................... 70V

LTC6101HV ........................................................ 105V

+

Minimum Input Voltage (–IN Pin) .................... (V

– 4V)

Maximum Output Voltage (Out Pin) ............................9V

Input Current ....................................................... ±10mA

–

Output Short-Circuit Duration (to V

) .............. Indefi nite

Operating Temperature Range

LTC6101C/LTC6101HVC .......................– 40°C to 85°C

PIN CONFIGURATION

LTC6101I/LTC6101HVI ......................... –40°C to 85°C

LTC6101H/LTC6101HVH ................... –55°C to 125°C

Specifi ed Temperature Range (Note 2)

LTC6101C/LTC6101HVC ........................... 0°C to 70°C

LTC6101I/LTC6101HVI ......................... –40°C to 85°C

LTC6101H/LTC6101HVH ................... –40°C to 125°C

Storage Temperature Range .................. –65°C to 150°C

Lead Temperature (Soldering, 10 sec) ................. 300°C

TOP VIEW

–IN

1

NC

2

NC

3

OUT

4

MS8 PACKAGE

8-LEAD PLASTIC MSOP

T

= 150°C, θJA = 300°C/ W

JMAX

8

+IN

+

7

V

6

NC

–

5

V

OUT 1

TOP VIEW

V– 2

–IN 3

S5 PACKAGE

5-LEAD PLASTIC TSOT-23

T

= 150°C, θJA = 250°C/ W

JMAX

5 V

4 +IN

+

ORDER INFORMATION

LEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE

LTC6101ACMS8#PBF LTC6101ACMS8#TRPBF LTBSB 8-Lead Plastic MSOP 0°C to 70°C

LTC6101AIMS8#PBF LTC6101AIMS8#TRPBF LTBSB 8-Lead Plastic MSOP –40°C to 85°C

LTC6101AHMS8#PBF LTC6101AHMS8#TRPBF LTBSB 8-Lead Plastic MSOP –40°C to 125°C

LTC6101HVACMS8#PBF LTC6101HVACMS8#TRPBF LTBSX 8-Lead Plastic MSOP 0°C to 70°C

LTC6101HVAIMS8#PBF LTC6101HVAIMS8#TRPBF LTBSX 8-Lead Plastic MSOP –40°C to 85°C

LTC6101HVAHMS8#PBF LTC6101HVAHMS8#TRPBF LTBSX 8-Lead Plastic MSOP –40°C to 125°C

2

6101fh

LTC6101/LTC6101HV

ORDER INFORMATION

Lead Free Finish

TAPE AND REEL (MINI) TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION SPECIFIED TEMPERATURE RANGE

LTC6101ACS5#TRMPBF LTC6101ACS5#TRPBF LTBND 5-Lead Plastic TSOT-23 0°C to 70°C

LTC6101AIS5#TRMPBF LTC6101AIS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 85°C

LTC6101AHS5#TRMPBF LTC6101AHS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 125°C

LTC6101BCS5#TRMPBF LTC6101BCS5#TRPBF LTBND 5-Lead Plastic TSOT-23 0°C to 70°C

LTC6101BIS5#TRMPBF LTC6101BIS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 85°C

LTC6101BHS5#TRMPBF LTC6101BHS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 125°C

LTC6101CCS5#TRMPBF LTC6101CCS5#TRPBF LTBND 5-Lead Plastic TSOT-23 0°C to 70°C

LTC6101CIS5#TRMPBF LTC6101CIS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 85°C

LTC6101CHS5#TRMPBF LTC6101CHS5#TRPBF LTBND 5-Lead Plastic TSOT-23 –40°C to 125°C

LTC6101HVACS5#TRMPBF LTC6101HVACS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 0°C to 70°C

LTC6101HVAIS5#TRMPBF LTC6101HVAIS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 85°C

LTC6101HVAHS5#TRMPBF LTC6101HVAHS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 125°C

LTC6101HVBCS5#TRMPBF LTC6101HVBCS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 0°C to 70°C

LTC6101HVBIS5#TRMPBF LTC6101HVBIS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 85°C

LTC6101HVBHS5#TRMPBF LTC6101HVBHS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 125°C

LTC6101HVCCS5#TRMPBF LTC6101HVCCS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 0°C to 70°C

LTC6101HVCIS5#TRMPBF LTC6101HVCIS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 85°C

LTC6101HVCHS5#TRMPBF LTC6101HVCHS5#TRPBF LTBSZ 5-Lead Plastic TSOT-23 –40°C to 125°C
TRM = 500 pieces. *Temperature grades are identifi ed by a label on the shipping container.
Consult LTC Marketing for parts specifi ed with wider operating temperature ranges.

Consult LTC Marketing for information on lead based fi nish parts.
For more information on lead free part marking, go to:

For more information on tape and reel specifi cations, go to: http://www.linear.com/tapeandreel/

http://www.linear.com/leadfree/

6101fh

3

LTC6101/LTC6101HV

ELECTRICAL CHARACTERISTICS

(LTC6101) The ● denotes the specifi cations which apply over the full
specifi ed temperature range, otherwise specifi cations are at T

= 25°C, RIN = 100Ω, R

A

= 10k, V

OUT

details), 4V ≤ VS ≤ 60V unless otherwise noted.

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

V

S

V

OS

∆V

/∆T Input Offset Voltage Drift V

OS

I

B

I

OS

V

SENSE(MAX)

PSRR Power Supply Rejection Ratio V

V

OUT

V

OUT (0)

I

OUT

t

r

BW Signal Bandwidth I

I

S

Supply Voltage Range

Input Offset Voltage V

= 5mV, Gain = 100, LTC6101A

SENSE

V

= 5mV, Gain = 100, LTC6101AC, LTC6101AI

SENSE

V

= 5mV, Gain = 100, LTC6101AH

SENSE

V

= 5mV, Gain = 100, LTC6101B

SENSE

V

= 5mV, Gain = 100, LTC6101C

SENSE

= 5mV, LTC6101A

SENSE

V

= 5mV, LTC6101B

SENSE

V

= 5mV, LTC6101C

SENSE

Input Bias Current RIN = 1M

Input Offset Current RIN = 1M

Input Sense Voltage Full Scale VOS within Specifi cation, RIN = 1k (Note 3)

= 6V to 60V, V

S

V

= 4V to 60V, V

S

Maximum Output Voltage 12V ≤ VS ≤ 60V, V

V

= 6V, V

S

V

Minimum Output Voltage V

V
V

V

V

SENSE

= 4V, V

S

SENSE

= 0V, Gain = 100, LTC6101A

SENSE

= 0V, Gain = 100, LTC6101AC, LTC6101AI

SENSE

= 0V, Gain = 100, LTC6101AH

SENSE

= 0V, Gain = 100, LTC6101B

SENSE

= 0V, Gain = 100, LTC6101C

SENSE

Maximum Output Current 6V ≤ VS ≤ 60V, R

V

= 4V, V

S

SENSE

Input Step Response
(to 2.5V on a 5V Output Step)

Supply Current VS = 4V, I

∆V

= 100mV Transient, 6V ≤ VS ≤ 60V, Gain = 50

SENSE

V

= 4V

S

= 200A, R

OUT

I

= 1mA, R

OUT

= 0, R

OUT

V

= 6V, I

S

V

= 12V, I

S

V

= 60V, I

S

OUT

= 0, R

OUT

OUT

= 5mV, Gain = 100

SENSE

= 5mV, Gain = 100

SENSE

= 88mV

SENSE

= 330mV, RIN = 1k, R
= 550mV, RIN = 1k, R

= 2k, V

OUT

SENSE

= 550mV, Gain = 2, R

= 100, R

IN

= 100, R

IN

= 0, R

= 0, R

IN

IN

IN

IN

= 1M

= 1M

= 1M

= 1M

OUT

OUT

= 5k

= 5k

= 10k

OUT

= 2k

OUT

= 110mV, Gain = 20

= 2k

OUT

LTC6101AI, LTC6101AC, LTC6101BI, LTC6101BC,
LTC6101CI, LTC6101CC
LTC6101AH, LTC6101BH, LTC6101CH

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

+

= V+ (see Figure 1 for

SENSE

460V

±85 ±300

±450
±535

±150 ±450

±810

±400 800

1200

±1
±3
±5

100 170

245

µV
µV
µV

µV
µV

µV
µV

µV/°C
µV/°C
µV/°C

nA
nA

±2 ±15 nA

500 mV

118
115

110
105

140 dB

dB

133 dB

dB

8
3
1

030

45

53.5

mV
mV
mV

04581mV

mV

0150

250

1

0.5

mV
mV

mA
mA

1

1.5

140
200

220 450

475

240 475

525

250 500

590

375 640

690
720

kHz
kHz

µA
µA

µA
µA

µA
µA

µA

µA
µA

V
V
V

µs
µs

4

6101fh

LTC6101/LTC6101HV

ELECTRICAL CHARACTERISTICS

(LTC6101HV) The ● denotes the specifi cations which apply over the full
specifi ed temperature range, otherwise specifi cations are at TA = 25°C, RIN = 100Ω, R

= 10k, V

OUT

details), 5V ≤ VS ≤ 100V unless otherwise noted.

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

V

S

V

OS

∆V

/∆T Input Offset Voltage Drift V

OS

I

B

I

OS

V

SENSE(MAX)

PSRR Power Supply Rejection Ratio V

V

OUT

V

OUT (0)

I

OUT

t

r

BW Signal Bandwidth I

I

S

Supply Voltage Range

Input Offset Voltage V

= 5mV, Gain = 100, LTC6101HVA

SENSE

V

= 5mV, Gain = 100, LTC6101HVAC, LTC6101HVAI

SENSE

V

= 5mV, Gain = 100, LTC6101HVAH

SENSE

V

= 5mV, Gain = 100, LTC6101HVB

SENSE

V

= 5mV, Gain = 100, LTC6101HVC

SENSE

= 5mV, LTC6101HVA

SENSE

V

= 5mV, LTC6101HVB

SENSE

V

= 5mV, LTC6101HVC

SENSE

Input Bias Current RIN = 1M

Input Offset Current RIN = 1M

Input Sense Voltage Full Scale VOS within Specifi cation, RIN = 1k (Note 3)

= 6V to 100V, V

S

V

= 5V to 100V, V

S

Maximum Output Voltage 12V ≤ VS ≤ 100V, V

V

= 5V, V

S

SENSE

Minimum Output Voltage V

= 0V, Gain = 100, LTC6101HVA

SENSE

V

= 0V, Gain = 100, LTC6101HVAC, LTC6101HVAI

SENSE

V

= 0V, Gain = 100, LTC6101HVAH

SENSE

V

= 0V, Gain = 100, LTC6101HVB

SENSE

V

= 0V, Gain = 100, LTC6101HVC

SENSE

Maximum Output Current 5V ≤ VS ≤ 100V, R

Input Step Response
(to 2.5V on a 5V Output Step)

Supply Current VS = 5V, I

∆V

= 100mV Transient, 6V ≤ VS ≤ 100V, Gain = 50

SENSE

V

= 5V

S

= 200A, R

OUT

I

= 1mA, R

OUT

V

= 6V, I

S

V

= 12V, I

S

V

= 60V, I

S

OUT

OUT

OUT

OUT

IN

= 0, R

= 0, R

= 0, R

= 0, R

= 5mV, Gain = 100

SENSE

= 5mV, Gain = 100

SENSE

= 88mV

SENSE

= 330mV, RIN = 1k, R

= 2k, V

OUT

= 100, R

IN

= 100, R

= 1M

IN

= 1M

IN

IN

IN

OUT

= 1M

= 1M

= 110mV, Gain = 20

SENSE

= 5k

OUT

= 5k

OUT

= 10k

LTC6101HVI, LTC6101HVC
LTC6101HVH

V

= 100V, I

S

OUT

= 0, R

IN

= 1M
LTC6101HVAI, LTC6101HVAC, LTC6101HVBI,
LTC6101HVBC, LTC6101HVCI, LTC6101HVCC
LTC6101HVAH, LTC6101HVBH, LTC6101HVCH

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

●

+

= V+ (see Figure 1 for

SENSE

5 100 V

±85 ±300

±450
±535

±150 ±450

±810

±400 800

1200

±1
±3
±5

100 170

245

±2 ±15 nA

500 mV

118

140 dB

115

110

133 dB

105

8
3

030

45

53.5

04581mV

0 150

250

1 mA

1

1.5

140
200

200 450

475

220 475

525

230 500

590

350 640

690
720

350 640

690
720

µV
µV
µV

µV
µV

µV
µV

µV/°C
µV/°C
µV/°C

nA
nA

dB

dB

mV
mV
mV

mV

mV
mV

µs
µs

kHz
kHz

µA
µA

µA
µA

µA
µA

µA
µA
µA

µA

µA
µA

V
V

6101fh

5

LTC6101/LTC6101HV

44010 20 30 50 10060 70 80 90

V

SUPPLY

(V)

MAXIMUM V

SENSE

(V)

2.5

2

1.5

1

0.5

0

6101 G05

TA = 125°C

TA = 85°C

TA = 70°C

TA = 0°C

TA = –40°C

RIN = 3k
R

OUT

= 3k

TA = 25°C

LTC6101
LTC6101HV

TEMPERATURE (°C)

12

10

8

6

4

2

0

–40 40 80 120100–20

6101 G06

020 60

MAXIMUM OUTPUT (V)

VS = 60V

VS = 12V

VS = 6V

VS = 4V

TEMPERATURE (°C)

7

6

5

4

3

2

1

0

–40 40 80 120100–20

6101 G07

020 60

MAXIMUM I

OUT

(mA)

VS = 12V

VS = 60V

VS = 6V

VS = 4V

INPUT OFFSET (µV)

800

600

400

200

0

–200

–400

–600

–800

–1000

6101 G01

TEMPERATURE (°C)

–40 12004080

–20 20 60 100

A GRADE
B GRADE
C GRADE

RIN = 100
R

OUT

= 5k

V

IN

= 5mV

REPRESENTATIVE

UNITS

TEMPERATURE (°C)

12

10

8

6

4

2

0

–40 40 80 120100–20

6101 G20

020 60

MAXIMUM OUTPUT (V)

VS = 100V

VS = 12V

VS = 5V

VS = 6V

VS = 4V

ELECTRICAL CHARACTERISTICS

Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.

Note 2: The LTC6101C/LTC6101HVC are guaranteed to meet specifi ed
performance from 0°C to 70°C. The LTC6101C/LTC6101HVC are designed,

characterized and expected to meet specifi ed performance from –40°C to
85°C but are not tested or QA sampled at these temperatures. LTC6101I/
LTC6101HVI are guaranteed to meet specifi ed performance from –40°C
to 85°C. The LTC6101H/LTC6101HVH are guaranteed to meet specifi ed
performance from –40°C to 125°C.

Note 3: R

OUT

TYPICAL PERFORMANCE CHARACTERISTICS

Input VOS vs Temperature Input VOS vs Supply Voltage Input Sense Range

40

20

0

–20

–40

–60

–80

INPUT OFFSET (µV)

–100

RIN = 100

= 5k

R

OUT

–120

–140

= 5mV

V

IN

43211 18 25 39 46 53 60

V

SUPPLY

TA = 0°C

TA = –40°C

TA = 25°C

TA = 85°C

TA = 125°C

(V)

= 10k for 6V ≤ VS ≤ 100V, R

6101 G02

= 2k for VS = 4V.

OUT

LTC6101: V
vs Temperature

6

Maximum

OUT

LTC6101HV: V

OUT

vs Temperature

Maximum

LTC6101: I

Maximum

OUT

vs Temperature

6101fh

TYPICAL PERFORMANCE CHARACTERISTICS

SUPPLY VOLTAGE (V)

0

SUPPLY CURRENT (µA)

450

400

350

300

250

200

150

100

50

0

32

6101 G11

816

48 56

244028

412

44 52

20

36 60

–40°C

0°C

25°C

70°C

85°C

125°C

VIN = 0
R

IN

= 1M

V

+

V+-10mV

0.5V

0V

TIME (10µs/DIV)

6101 G12

TA = 25°C
V

+

= 12V

R

IN

= 100

R

OUT

= 5k

V

SENSE

+

= V

+

V

SENSE

–

V

OUT

V+-10mV

V

+

-20mV

1V

0.5V

TIME (10µs/DIV)

6101 G13

V

OUT

V

SENSE

–

TA = 25°C
V

+

= 12V

R

IN

= 100

R

OUT

= 5k

V

SENSE

+

= V

+

GAIN (dB)

FREQUENCY (Hz)

1k

40

35

30

25

20

15

10

5

0

–5

–10

10k 100k 1M

6101 G09

TA = 25°C
R

IN

= 100

R

OUT

= 4.99k

I

OUT

= 200µA

I

OUT

= 1mA

TEMPERATURE (°C)

160

140

120

100

80

60

40

20

0

–40 40 80 120100–20

6101 G10

020 60

I

B

(nA)

VS = 6V TO 100V

VS = 4V

INPUT VOLTAGE (V)

0.1

OUTPUT ERROR (%)

1

10

100

0 0.2 0.3 0.4

0.01

0.1

0.50.15 0.25 0.350.05 0.45

C GRADE

B GRADE

A GRADE

TA = 25°C

GAIN =10

TEMPERATURE (°C)

7

6

5

4

3

2

1

0

–40 40 80 120100–20

6101 G21

020 60

MAXIMUM I

OUT

(mA)

VS = 12V

VS = 100V

VS = 6V

VS = 5V

VS = 4V

SUPPLY VOLTAGE (V)

0

SUPPLY CURRENT (µA)

600

500

400

300

200

100

0

6101 G22

60

10 3020 40

80 90

50

70 100

–40°C

0°C

85°C

125°C

VIN = 0
R

IN

= 1M

70°C

25°C

LTC6101/LTC6101HV

LTC6101HV: I

Maximum

OUT

vs Temperature

Input Bias Current
vs Temperature

Output Error Due to Input Offset
vs Input Voltage

LTC6101: Supply Current
vs Supply Voltage

Gain vs Frequency

LTC6101HV: Supply Current
vs Supply Voltage

Step Response 0mV to 10mV Step Response 10mV to 20mV

6101fh

7

LTC6101/LTC6101HV

FREQUENCY (Hz)

PSRR (dB)

0.1 1 10 100 1k 10k 100k 1M

6101 G19

160

140

120

100

80

60

40

20

0

RIN = 100
R

OUT

= 10k

C

OUT

= 5pF
GAIN = 100
I

OUTDC

= 100µA

V

INAC

= 50mVp

LTC6101HV,
V

+

= 5V

LTC6101,
LTC6101HV,
V

+

= 12V

LTC6101,
V

+

= 4V

V

+

V+-100mV

5V

0V

TIME (10µs/DIV)

6101 G14

V

OUT

C

LOAD

= 1000pF

C

LOAD

= 10pF

V

SENSE

–

TA = 25°C
V

+

= 12V

R

IN

= 100

R

OUT

= 5k

V

SENSE

+

= V

+

V

+

V+-100mV

5V

0V

TIME (100µs/DIV)

6101 G15

V

OUT

V

SENSE

–

TA = 25°C
V

+

= 12V

C

LOAD

= 2200pF

R

IN

= 100

R

OUT

= 5k

V

SENSE

+

= V

+

5.5V
5V

0.5V
0V

TIME (500ns/DIV)

6101 G16

V

OUT

V

SENSE

–

ΔV

SENSE

–

=100mV

I

OUT

= 100µA

I

OUT

= 0

TA = 25°C
V

+

= 12V

R

IN

= 100

R

OUT

= 5k

V

SENSE

+

= V

+

5.5V
5V

0.5V
0V

TIME (500ns/DIV)

6101 G17

V

OUT

ΔV

SENSE

–

=100mV

I

OUT

= 100µ

I

OUT

= 0

TA = 25°C
V

+

= 12V

R

IN

= 100

R

OUT

= 5k

V

SENSE

+

= V

+

TYPICAL PERFORMANCE CHARACTERISTICS

Step Response 100mV Step Response 100mV

Step Response Falling Edge

Step Response Rising Edge

PSRR vs Frequency

8

6101fh

–

+

V

+

V

–

10V

OUT

6101 BD

LTC6101/LTC6101HV

V

BATTERY

I

OUT

V

SENSE

R

SENSE

I

LOAD

R

OUT

R

IN

–

+

L
O
A
D

V

OUT

= V

SENSE

x

R

OUT

R

IN

5k

5k

10V

–IN

+IN

PIN FUNCTIONS

OUT: Current Output. OUT will source a current that is
proportional to the sense voltage into an external resistor.

–

: Negative Supply (or Ground for Single-Supply

V

Operation).

–

–IN: The internal sense amplifi er will drive IN

+

potential as IN
the output current I
developed across the external R

. A resistor (RIN) tied from V+ to IN– sets

OUT

= V

SENSE/RIN

. V

SENSE

SENSE

(Figure 1).

to the same

is the voltage

+IN: Must be tied to the system load end of the sense
resistor, either directly or through a resistor.

BLOCK DIAGRAM

LTC6101/LTC6101HV

+

: Positive Supply Pin. Supply current is drawn through

V
this pin. The circuit may be confi gured so that the
LTC6101 supply current is or is not monitored along
with the system load current. To monitor only system

load current, connect V
sense resistor. To monitor the total current, including the
LTC6101 current, connect V
of the sense resistor.

+

to the more positive side of the

+

to the more negative side

Figure 1. LTC6101/LTC6101HV Block Diagram and Typical Connection

APPLICATIONS INFORMATION

The LTC6101 high side current sense amplifi er (Figure 1)
provides accurate monitoring of current through a user­selected sense resistor. The sense voltage is amplifi ed by
a user-selected gain and level shifted from the positive
power supply to a ground-referred output. The output
signal is analog and may be used as is or processed with
an output fi lter.

Theory of Operation

An internal sense amplifi er loop forces IN
same potential as IN+. Connecting an external resis-

–

to have the

tor, R

, between IN– and V+ forces a potential across

IN

RIN that is the same as the sense voltage across
R

. A corresponding current, V

SENSE

SENSE/RIN

fl ow through RIN. The high impedance inputs of the
sense amplifi er will not conduct this input current,
so it will fl ow through an internal MOSFET to the output pin.

The output current can be transformed into a voltage by
adding a resistor from OUT to V–. The output voltage is
then VO = V– + I

OUT

• R

OUT

.

, will

6101fh

9

LTC6101/LTC6101HV

LTC6101

R

OUT

V

OUT

6101 F02

R

IN

V

+

LOAD

R

SENSE

–

+

V

+

V

–

OUT

–IN+IN

APPLICATIONS INFORMATION

Useful Gain Confi gurations

Gain R

20 499 10k 250mV 500µA

50 200 10k 100mV 500µA

100 100 10k 50mV 500µA

R

IN

OUTVSENSE

at V

OUT

= 5V I

OUT

at V

OUT

Selection of External Current Sense Resistor

The external sense resistor, R

, has a signifi cant effect

SENSE

on the function of a current sensing system and must be
chosen with care.

First, the power dissipation in the resistor should be
considered. The system load current will cause both heat
and voltage loss in R

. As a result, the sense resis-

SENSE

tor should be as small as possible while still providing
the input dynamic range required by the measurement.
Note that input dynamic range is the difference between
the maximum input signal and the minimum accurately
reproduced signal, and is limited primarily by input DC
offset of the internal amplifi er of the LTC6101. In addition,
R

SENSE

must be small enough that V

does not exceed

SENSE

the maximum input voltage specifi ed by the LTC6101, even
under peak load conditions. As an example, an application
may require that the maximum sense voltage be 100mV.
If this application is expected to draw 2A at peak load,
R

Once the maximum R

should be no more than 50m.

SENSE

value is determined, the mini-

SENSE

mum sense resistor value will be set by the resolution or
dynamic range required. The minimum signal that can be
accurately represented by this sense amp is limited by the
input offset. As an example, the LTC6101B has a typical
input offset of 150µV. If the minimum current is 20mA, a
sense resistor of 7.5m will set V

to 150µV. This is

SENSE

the same value as the input offset. A larger sense resistor
will reduce the error due to offset by increasing the sense
voltage for a given load current.

= 5V

Peak dissipation is 200mW. If a 5m sense resistor is
employed, then the effective current error is 30mA, while
the peak sense voltage is reduced to 10mV at 2A, dis­sipating only 20mW.

The low offset and corresponding large dynamic range of
the LTC6101 make it more fl exible than other solutions in
this respect. The 150µV typical offset gives 60dB of dy­namic range for a sense voltage that is limited to 150mV
max, and over 70dB of dynamic range if the rated input
maximum of 500mV is allowed.

Sense Resistor Connection

–

Kelvin connection of the IN

and IN+ inputs to the sense
resistor should be used in all but the lowest power ap­plications. Solder connections and PC board interconnec­tions that carry high current can cause signifi cant error
in measurement due to their relatively large resistances.
One 10mm x 10mm square trace of one-ounce copper
is approximately 0.5m. A 1mV error can be caused by
as little as 2A fl owing through this small interconnect.
This will cause a 1% error in a 100mV signal. A 10A load
current in the same interconnect will cause a 5% error
for the same 100mV signal. By isolating the sense traces
from the high-current paths, this error can be reduced
by orders of magnitude. A sense resistor with integrated
Kelvin sense terminals will give the best results. Figure 2
illustrates the recommended method.

Choosing a 50m R
and provide a system that has 100mV across the sense
resistor at peak load (2A), while input offset causes an
error equivalent to only 3mA of load current.

10

will maximize the dynamic range

SENSE

Figure 2. Kelvin Input Connection Preserves
Accuracy Despite Large Load Current

6101fh

APPLICATIONS INFORMATION

6101 F03b

–

+

–

+

–

+

R

5

7.5k

V

IN

301301

V

OUT

I

LOAD

LTC6101

R

SENSE LO

100m

M1
Si4465

10k

CMPZ4697

7.5k

V

IN

1.74M

4.7k

Q1
CMPT5551

40.2k

3

4

5

6

12

8

7

619k

HIGH

RANGE

INDICATOR

(I

LOAD

> 1.2A)

V

LOGIC

(3.3V TO 5V)

LOW CURRENT RANGE OUT

2.5V/A

(

V

LOGIC

+5V) ≤ VIN ≤ 60V

0 ≤ I

LOAD

≤ 10A

HIGH CURRENT RANGE OUT
250mV/A

301 301

LTC6101

R

SENSE HI

10m

V

LOGIC

BAT54C

LTC1540

V

+

V

–

OUT

–IN+IN

V

+

V

–

OUT

–IN+IN

V

+

LOAD

D

SENSE

6101 F03a

R

SENSE

LTC6101/LTC6101HV

Selection of External Input Resistor, R

IN

The external input resistor, RIN, controls the transconduc­tance of the current sense circuit. Since I
transconductance g
then I

R

IN

= V

OUT

SENSE

should be chosen to allow the required resolution

= 1/RIN. For example, if R

m

/100 or I

= 1mA for V

OUT

OUT

SENSE

= V

SENSE/RIN

IN

= 100mV.

,

= 100,

while limiting the output current. At low supply voltage,

may be as much as 1mA. By setting RIN such that

I

OUT

the largest expected sense voltage gives I

= 1mA, then

OUT

the maximum output dynamic range is available. Output
dynamic range is limited by both the maximum allowed
output current and the maximum allowed output voltage, as
well as the minimum practical output signal. If less dynamic
range is required, then R

can be increased accordingly,

IN

reducing the max output current and power dissipation.
If low sense currents must be resolved accurately in a
system that has very wide dynamic range, a smaller R

IN

than the max current spec allows may be used if the max
current is limited in another way, such as with a Schottky
diode across R

(Figure 3a). This will reduce the high

SENSE

current measurement accuracy by limiting the result, while
increasing the low current measurement resolution.

Figure 3a. Shunt Diode Limits Maximum Input Voltage to Allow
Better Low Input Resolution Without Overranging

This approach can be helpful in cases where occasional
large burst currents may be ignored. It can also be used
in a multirange confi guration where a low current circuit
is added to a high current circuit (Figure 3b). Note that
a comparator (LTC1540) is used to select the range, and
transistor M1 limits the voltage across R

SENSE LO

.

Care should be taken when designing the board layout
for R

especially for small R

IN,

connect impedances will increase the effective R

values. All trace and inter-

IN

IN

value,
causing a gain error. In addition, internal device resistance
will add approximately 0.2 to R

IN

.

Figure 3b. Dual LTC6101s Allow High-Low Current Ranging

6101fh

11

LTC6101/LTC6101HV

V

OUT=IOUT

•

R

OUT•RIN(DRIVEN)

R

OUT

+ R

IN(DRIVEN)

=I

OUT•ROUT

•

100

101

= 0.99 •I

OUT•ROUT

LTC6101

R

OUT

V

OUT

6101 F04

R

IN

–

V

+

LOAD

R

SENSE

R

IN

+

–

+

R

IN

+ =

R

IN

–

–

R

SENSE

V

+

V

–

OUT

–IN+IN

APPLICATIONS INFORMATION

Selection of External Output Resistor, R

The output resistor, R
rent is converted to voltage. V

, determines how the output cur-

OUT

is simply I

OUT

OUT

OUT

• R

OUT

.

In choosing an output resistor, the max output voltage
must fi rst be considered. If the circuit that is driven by
the output does not limit the output voltage, then R

OUT

must be chosen such that the max output voltage does
not exceed the LTC6101 max output voltage rating. If the
following circuit is a buffer or ADC with limited input range,
then R

must be chosen so that I

OUT

OUT(MAX)

• R

OUT

is less

than the allowed maximum input range of this circuit.

In addition, the output impedance is determined by R

OUT

. If
the circuit to be driven has high enough input impedance,
then almost any useful output impedance will be accept­able. However, if the driven circuit has relatively low input
impedance, or draws spikes of current, such as an ADC
might do, then a lower R

value may be required in order

OUT

to preserve the accuracy of the output. As an example, if
the input impedance of the driven circuit is 100 times R
then the accuracy of V

will be reduced by 1% since:

OUT

OUT

,

Error Sources

The current sense system uses an amplifi er and resistors
to apply gain and level shift the result. The output is then
dependent on the characteristics of the amplifi er, such as
gain and input offset, as well as resistor matching.

Output Error, E
Voltage, V

E

OUT(VOS)

OS

, Due to the Amplifi er DC Offset

OUT

= VOS • (R

OUT/RIN

)

The DC offset voltage of the amplifi er adds directly to the
value of the sense voltage, V

. This is the dominant

SENSE

error of the system and it limits the available dynamic
range. The paragraph “Selection of External Current Sense
Resistor” provides details.

Output Error, E

(+) and IB(–)

I

B

The bias current I
internal op amp. I

E

OUT(IBIAS)

Since I

E

(+) ≈ IB(–) = I

B

OUT(IBIAS)

For instance if I

, Due to the Bias Currents,

OUT

(+) fl ows into the positive input of the

B

(–) fl ows into the negative input.

B

= R

≈ –R

((IB(+) • (R

OUT

BIAS

• I

OUT

BIAS

is 100nA and R

BIAS

, if R

SENSE/RIN

<< RIN then,

SENSE

OUT

) – IB(–))

is 1k, the output

error is 0.1mV.

Note that in applications where R
a voltage offset in R

(–) and E

I

B

, the bias current error can be similarly reduced if an

R

IN

external resistor R

OUT(IBIAS)

IN

that cancels the error due to

SENSE

≈ 0. In applications where R

(+) = (RIN – R

≈ RIN, IB(+) causes

SENSE

) is connected as

SENSE

SENSE

<

shown in Figure 4 below. Under both conditions:

E

OUT(IBIAS)

= ± R

• IOS; IOS = IB(+) – IB(–)

OUT

Ideally, the circuit output is:

R

V

= V

OUT

In this case, the only error is due to resistor mismatch,
which provides an error in gain only. However, offset
voltage, bias current and fi nite gain in the amplifi er cause
additional errors:

12

SENSE

•
R

OUT

;V

IN

SENSE

= R

SENSE•ISENSE

Figure 4. Second Input R Minimizes
Error Due to Input Bias Current

6101fh

APPLICATIONS INFORMATION

LTC6101/LTC6101HV

If the offset current, IOS, of the LTC6101 amplifi er is 2nA,
the 100 microvolt error above is reduced to 2 microvolts.
Adding R
range of the circuit. For less sensitive designs, R

+

as described will maximize the dynamic

IN

IN

+

is

not necessary.

Example:

If an I

range = (1A to 1mA) and (V

SENSE

OUT/ISENSE

) =

3V/1A

Then, from the Electrical Characteristics of the LTC6101,
R

SENSE

≈ V

SENSE

(max) / I

(max) = 500mV/1A =

SENSE

500m

Gain = R

OUT/RIN

= V

(max) / V

OUT

SENSE

(max) =

3V/500mV = 6

If the maximum output current, I
R

equals 3V/1mA ≈ 3.01 k (1% value) and R

OUT

, is limited to 1mA,

OUT

IN

=

3k/6 ≈ 499 (1% value).

The output error due to DC offset is ±900µVolts (typ) and
the error due to offset current, IOS is 3k x 2nA = ±6µVolts
(typical), provided R

IN

+

= R

IN

–

.

The maximum output error can therefore reach ±906µVolts
or 0.03% (–70dB) of the output full scale. Considering
the system input 60dB dynamic range (I

SENSE

= 1mA to
1A), the 70dB performance of the LTC6101 makes this
application feasible.

Output Error, E

, Due to the Finite DC Open Loop

OUT

Gain, AOL, of the LTC6101 Amplifi er

This error is inconsequential as the AOL of the LTC6101
is very large.

Output Current Limitations Due to Power Dissipation

The LTC6101 can deliver up to 1mA continuous current to
the output pin. This current fl ows through RIN and enters the
current sense amp via the IN(–) pin. The power dissipated
in the LTC6101 due to the output signal is:

P

Since V

OUT

= (V

–IN

– V

–IN

≈ V+, P

OUT

OUT

) • I

OUT

≈ (V+ – V

OUT

) • I

OUT

There is also power dissipated due to the quiescent sup­ply current:

P

Q

= IDD • V

+

The total power dissipated is the output dissipation plus
the quiescent dissipation:

P

TOTAL

= P

OUT

+ P

Q

At maximum supply and maximum output current, the
total power dissipation can exceed 100mW. This will
cause signifi cant heating of the LTC6101 die. In order to
prevent damage to the LTC6101, the maximum expected
dissipation in each application should be calculated. This
number can be multiplied by the θJA value listed in the
package section on page 2 to fi nd the maximum expected
die temperature. This must not be allowed to exceed 150°C,
or performance may be degraded.

As an example, if an LTC6101 in the S5 package is to be
run at 55V ±5V supply with 1mA output current at 80°C:

• V

+ T

• V

+

RISE

+

(MAX)

(MAX)

= 41.4mW

= 60mW

P

Q(MAX)

P

OUT(MAX)

T

RISE

T

MAX

T

MAX

P

TOTAL(MAX)

= I

DD(MAX)

= I

OUT

= θJA • P

= T

TOTAL(MAX)

AMBIENT

must be < 150°C

≈ 96mW and the max die temp

will be 104°C

If this same circuit must run at 125°C, the max die
temp will increase to 150°C. (Note that supply current,
and therefore P

, is proportional to temperature. Refer

Q

to Typical Performance Characteristics section.) In this
condition, the maximum output current should be reduced
to avoid device damage. Note that the MSOP package
has a larger θ

than the S5, so additional care must be

JA

taken when operating the LTC6101A/LTC6101HVA at high
temperatures and high output currents.

The LTC6101HV can be used at voltages up to 105V. This
additional voltage requires that more power be dissipated
for a given level of current. This will further limit the allowed
output current at high ambient temperatures.

It is important to note that the LTC6101 has been designed
to provide at least 1mA to the output when required, and
can deliver more depending on the conditions. Care must
be taken to limit the maximum output current by proper
choice of sense resistor and, if input fault conditions exist,
external clamps.

6101fh

13

LTC6101/LTC6101HV

LTC6101

R

OUT

V

OUT

6101 F05

R

IN

LOAD

V

+

R

SENSE

V

BATTERY

–

+

V

+

V

–

OUT

–IN+IN

APPLICATIONS INFORMATION

Output Filtering

The output voltage, V

, is simply I

OUT

OUT

• Z

OUT

. This
makes fi ltering straightforward. Any circuit may be used
which generates the required Z
response. For example, a capacitor in parallel with R

to get the desired fi lter

OUT

OUT

will give a low pass response. This will reduce unwanted
noise from the output, and may also be useful as a charge
reservoir to keep the output steady while driving a switch­ing circuit such as a mux or ADC. This output capacitor
in parallel with an output resistor will create a pole in the
output response at:

f

=

–3dB

2•π •R

1

OUT•COUT

Useful Equations

Input Voltage: V

Voltage Gain:

V

Current Gain:

I

I

SENSE

Transconductance:

Transimpedance:

SENSE

V

OUT

SENSE

OUT

V

I

SENSE

= I

SENSE•RSENSE

R

OUT

=

R

IN

R

SENSE

=

R

IN

I

OUT

SENSE

= R

=

SENSE

V

OUT

1

R

IN

R

OUT

•
R

IN

Input Common Mode Range

The inputs of the LTC6101 can function from 1.5V below
the positive supply to 0.5V above it. Not only does this
allow a wide V

range, it also allows the input refer-

SENSE

ence to be separate from the positive supply (Figure 5).
Note that the difference between V

and V+ must be no

BATT

more than the common mode range listed in the Electrical
Characteristics table. If the maximum V

is less than

SENSE

500mV, the LTC6101 may monitor its own supply current,
as well as that of the load (Figure 6).

Figure 5. V+ Powered Separately from

R

Load Supply (V

+

V

SENSE

LOAD

R

IN

–

V

BATT

+

)

–IN+IN

–

+

V

14

LTC6101

OUT

V

OUT

R

OUT

6101 F06

Figure 6. LTC6101 Supply Current
Monitored with Load

6101fh

APPLICATIONS INFORMATION

6101 F07

LTC6101

R2

4.99k

D1

R1
100

V

BATT

R

SENSE

L

O

A

D

–

+

V

+

V

–

OUT

–IN+IN

6101 F08

ADC

LTC6101

R2

4.99k

D1

R1
100

V

BATT

R3

1k

R

SENSE

L

O

A

D

–

+

V

+

V

–

OUT

–IN+IN

LTC6101/LTC6101HV

Reverse Supply Protection

Some applications may be tested with reverse-polarity
supplies due to an expectation of this type of fault during
operation. The LTC6101 is not protected internally from
external reversal of supply polarity. To prevent damage that
may occur during this condition, a Schottky diode should
be added in series with V

–

(Figure 7). This will limit the
reverse current through the LTC6101. Note that this diode
will limit the low voltage performance of the LTC6101 by
effectively reducing the supply voltage to the part by V

.

D

In addition, if the output of the LTC6101 is wired to a device
that will effectively short it to high voltage (such as through
an ESD protection clamp) during a reverse supply condi­tion, the LTC6101’s output should be connected through
a resistor or Schottky diode (Figure 8).

Response Time

The LTC6101 is designed to exhibit fast response to inputs
for the purpose of circuit protection or signal transmission.
This response time will be affected by the external circuit
in two ways, delay and speed.

If the output current is very low and an input transient
occurs, there may be an increased delay before the output
voltage begins changing. This can be improved by increas­ing the minimum output current, either by increasing
R

or decreasing RIN. The effect of increased output

SENSE

current is illustrated in the step response curves in the
Typical Performance Characteristics section of this data
sheet. Note that the curves are labeled with respect to the
initial output currents.

The speed is also affected by the external circuit. In this
case, if the input changes very quickly, the internal ampli­fi er will slew the gate of the internal output FET (Figure

1) in order to maintain the internal loop. This results in
current fl owing through R

and the internal FET. This

IN

current slew rate will be determined by the amplifi er and
FET characteristics as well as the input resistor, R
ing a smaller R

will allow the output current to increase

IN

IN

. Us-

more quickly, decreasing the response time at the output.
This will also have the effect of increasing the maximum
output current. Using a larger R
sponse time, since V
increasing R

will both have the effect of increasing the

OUT

OUT

= I

OUT

will decrease the re-

OUT

• R

. Reducing RIN and

OUT

voltage gain of the circuit.

Figure 7. Schottky Prevents Damage During Supply Reversal

Figure 8. Additional Resistor R3 Protects
Output During Supply Reversal

6101fh

15

LTC6101/LTC6101HV

L
O
A
D

CHARGER

–

+

–

+

+

–

+

–

V

OUT D

= I

DISCHARGE • RSENSE

( )

WHEN I

DISCHARGE

≥ 0DISCHARGING:

R

OUT D

R

IN D

V

OUT C

= I

CHARGE • RSENSE

( )

WHEN I

CHARGE

≥ 0CHARGING:

R

OUT C

R

IN C

6101 TA02

V

BATT

R

IN C

100

LTC6101

R

IN D

100

R

IN C

100

LTC6101

V

OUT D

R

OUT D

4.99k

R

OUT C

4.99k

V

OUT C

R

IN D

100

I

DISCHARGE

R

SENSE

I

CHARGE

V

+

V

–

OUT

–IN+IN

V

+

V

–

OUT

–IN +IN

–

+

6101 TA04

R

L

V

O

4.75k4.75k

V

S

LASER MONITOR

PHOTODIODE

CMPZ4697*
(10V)

10k

i

PD

LTC6101

VO = I

PD • RL

*VZ SETS PHOTODIODE BIAS
V

Z

+ 4 ≤ VS ≤ VZ + 60

V

+

V

–

OUT

–IN+IN

TYPICAL APPLICATIONS

Bidirectional Current Sense Circuit with Separate Charge/Discharge Output

16

LTC6101 Monitors Its Own Supply Current High-Side-Input Transimpedance Amplifi er

I

LOAD

L
O
A
D

V

–

V

= 49.9 • R

OUT

R

SENSE

+

–

LTC6101

SENSE

(I

LOAD

+ I

–IN+IN

+

V

OUT

4.99k

SUPPLY

I

R1
100

SUPPLY

V

BATT

+

R2

)

–

V

OUT

6101 TA03

6101fh

TO µP

6101 TA06

LTC2433-1

LTC6101

R

OUT

4.99k

R

IN

100

V

OUT

V

SENSE

I

LOAD

4V TO 60V

1µF

5V

L
O
A
D

–

+

–

+

V

OUT

= • V

SENSE

= 49.9V

SENSE

R

OUT

R

IN

ADC FULL-SCALE = 2.5V

21

9

8

7

1063

4

5

V

CC

SCK

REF

+

REF–GND

IN

+

IN

–

C

C

F

O

SDD

V

+

V

–

OUT

–IN+IN

6101 TA07

L
O
A
D

FAULT

OFF ON

15

4.99k

V

O

R

S

3

4

47k

2

8

6

100

100

1%

10µF

63V

1µF

14V

V

LOGIC

SUB85N06-5

V

O

= 49.9 • RS • I

L

FOR RS = 5m,
V

O

= 2.5V AT IL = 10A (FULL SCALE)

LT1910 LTC6101

I

L

V

+

V

–

OUT

–IN

+IN

TYPICAL APPLICATIONS

16-Bit Resolution Unidirectional Output into LTC2433 ADC

LTC6101/LTC6101HV

Intelligent High-Side Switch with Current Monitor

6101fh

17

LTC6101/LTC6101HV

6101 TA08

LTC6101HV

R

IN

V

–

V

–

V

SENSE

R

SENSE

I

SENSE

LOAD

+

–

–+

V

OUT

= V

LOGIC – ISENSE

• • N • R

OUT

R

SENSE

R

IN

N = OPTOISOLATOR CURRENT GAIN

V

S

ANY OPTOISOLATOR

R

OUT

V

OUT

V

LOGIC

V

+

V

–

OUT

–IN +IN

6101 TA09

LTC6101

R

IN

100

V

OUT

R

OUT

4.99k

L

O

A

D

–

+

V

OUT

= • V

SENSE

= 49.9 V

SENSE

R

OUT

R

IN

M1 AND M2 ARE FQD3P50 TM

M1

M2

62V
CMZ5944B

500V

2M

V

SENSE

R

SENSE

I

SENSE

+–

DANGER! Lethal Potentials Present — Use Caution

DANGER!!

HIGH VOLTAGE!!

V

+

V

–

OUT

–IN+IN

TYPICAL APPLICATIONS

48V Supply Current Monitor with Isolated Output with 105V Survivability

18

Simple 500V Current Monitor

6101fh

LTC6101/LTC6101HV

MSOP (MS8) 0307 REV F

0.53 ± 0.152
(.021 ± .006)

SEATING

PLANE

NOTE:

1. DIMENSIONS IN MILLIMETER/(INCH)

2. DRAWING NOT TO SCALE

3. DIMENSION DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS.
MOLD FLASH, PROTRUSIONS OR GATE BURRS SHALL NOT EXCEED 0.152mm (.006") PER SIDE

4. DIMENSION DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS.
INTERLEAD FLASH OR PROTRUSIONS SHALL NOT EXCEED 0.152mm (.006") PER SIDE

5. LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.102mm (.004") MAX

0.18

(.007)

0.254

(.010)

1.10

(.043)

MAX

0.22 – 0.38

(.009 – .015)

TYP

0.1016 ± 0.0508
(.004 ± .002)

0.86

(.034)

REF

0.65

(.0256)

BSC

0° – 6° TYP

DETAIL “A”

DETAIL “A”

GAUGE PLANE

12

3

4

4.90 ± 0.152
(.193 ± .006)

8

7

6

5

3.00 ± 0.102

(.118 ± .004)

(NOTE 3)

3.00 ± 0.102

(.118 ± .004)

(NOTE 4)

0.52

(.0205)

REF

5.23

(.206)

MIN

3.20 – 3.45

(.126 – .136)

0.889 ± 0.127
(.035 ± .005)

RECOMMENDED SOLDER PAD LAYOUT

0.42 ± 0.038

(.0165 ± .0015)

TYP

0.65

(.0256)

BSC

PACKAGE DESCRIPTION

Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.

MS8 Package

8-Lead Plastic MSOP

(Reference LTC DWG # 05-08-1660 Rev F)

6101fh

19

LTC6101/LTC6101HV

PACKAGE DESCRIPTION

Please refer to http://www.linear.com/designtools/packaging/ for the most recent package drawings.

S5 Package

5-Lead Plastic TSOT-23

(Reference LTC DWG # 05-08-1635)

0.62
MAX

3.85 MAX

0.20 BSC

DATUM ‘A’

NOTE:

1. DIMENSIONS ARE IN MILLIMETERS

2. DRAWING NOT TO SCALE

3. DIMENSIONS ARE INCLUSIVE OF PLATING

4. DIMENSIONS ARE EXCLUSIVE OF MOLD FLASH AND METAL BURR

5. MOLD FLASH SHALL NOT EXCEED 0.254mm

6. JEDEC PACKAGE REFERENCE IS MO-193

2.62 REF

RECOMMENDED SOLDER PAD LAYOUT

PER IPC CALCULATOR

0.30 – 0.50 REF

0.95
REF

1.22 REF

1.4 MIN

0.09 – 0.20
(NOTE 3)

2.80 BSC

1.50 – 1.75
(NOTE 4)

1.00 MAX

PIN ONE

0.95 BSC

0.80 – 0.90

2.90 BSC
(NOTE 4)

0.30 – 0.45 TYP
5 PLCS (NOTE 3)

0.01 – 0.10

1.90 BSC

S5 TSOT-23 0302 REV B

20

6101fh

LTC6101/LTC6101HV

REVISION HISTORY

REV DATE DESCRIPTION PAGE NUMBER

H 03/12 Updated Features

Updated Absolute Maximum Ratings and changed Order Information
Changed operating temperature range to specifi ed temperature range in Electrical Characteristics header
Changed T

value in curve G02 from 45°C to 25°C

A

(Revision history begins at Rev H)

1
2

4, 5

6

Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa­tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.

6101fh

21

LTC6101/LTC6101HV

L
O
A
D

CHARGER

–

+

–

+

+

–

V

OUT

= I

DISCHARGE • RSENSE

( )

WHEN I

DISCHARGE

≥ 0DISCHARGING:

R

OUT

R

IN D

V

OUT

= I

CHARGE • RSENSE

( )

WHEN I

CHARGE

≥ 0CHARGING:

R

OUT

R

IN C

6101 TA05

V

BATT

R

IN C

LTC6101

R

IN D

R

IN C

LTC6101

R

OUT

V

OUT

R

IN D

I

DISCHARGE

I

CHARGE

R

SENSE

V

+

V

–

OUT OUT

–IN+IN

V

+

V

–

–IN +IN

TYPICAL APPLICATION

Bidirectional Current Sense Circuit with Combined Charge/Discharge Output

RELATED PARTS

PART NUMBER DESCRIPTION COMMENTS

LT1636 Rail-to-Rail Input/Output, Micropower Op Amp V

LT1637/LT1638/

Single/Dual/Quad, Rail-to-Rail, Micropower Op Amp V

LT1639

LT1787/LT1787HV Precision, Bidirectional, High Side Current Sense Amplifi er 2.7V to 60V Operation, 75µV Offset, 60µA Current Draw

LTC1921 Dual –48V Supply and Fuse Monitor ±200V Transient Protection, Drives Three Optoisolators for Status

LT1990 High Voltage, Gain Selectable Difference Amplifi er ±250V Common Mode, Micropower, Pin Selectable Gain = 1, 10

LT1991 Precision, Gain Selectable Difference Amplifi er 2.7V to ±18V, Micropower, Pin Selectable Gain = –13 to 14

LTC2050/LTC2051/
LTC2052

LTC4150 Coulomb Counter/Battery Gas Gauge Indicates Charge Quantity and Polarity

Single/Dual/Quad Zero-Drift Op Amp 3µV Offset, 30nV/°C Drift, Input Extends Down to V–

LT6100 Gain-Selectable High-Side Current Sense Amplifi er 4.1V to 48V Operation, Pin-Selectable Gain: 10, 12.5, 20, 25, 40, 50V/V

22

Linear Technology Corporation

1630 McCarthy Blvd., Milpitas, CA 95035-7417

[phone] ● FAX: [phone]

●

www.linear.com

Extends 44V above VEE, 55µA Supply Current,

CM

Shutdown Function

Extends 44V above VEE, 0.4V/µs Slew Rate, >1MHz

CM

Bandwidth, <250µA Supply Current per Amplifi er

© LINEAR TECHNOLOGY CORPORATION 2005

LT 0312 REV H • PRINTED IN USA

6101fh