TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
1
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
D
High-Fidelity Line-Out/HP Driver
D
75-mW Stereo Output
D
PC Power Supply Compatible
D
Pop Reduction Circuitry
D
Internal Mid-Rail Generation
D
Thermal and Short-Circuit Protection
D
Surface-Mount Packaging
D
Pin Compatible With TPA302
description
The TPA152 is a stereo audio power amplifier capable of less than 0.1% THD+N at 1 kHz when delivering
75 mW per channel into a 32-Ω load. THD+N is less than 0.2% across the audio band of 20 to 20 kHz. For
10 kΩ loads, the THD+N performance is better than 0.005% at 1 kHz, and less than 0.01% across the audio
band of 20 to 20 kHz.
The TP A152 is ideal for use as an output buffer for the audio CODEC in PC systems. It is also excellent for use
where a high-performance head phone/line-out amplifier is needed. Depop circuitry is integrated to reduce
transients during power up, power down, and mute mode.
Amplifier gain is externally configured by means of two resistors per input channel and does not require external
compensation for settings of 1 to 10. The TP A152 is packaged in the 8-pin SOIC (D) package that reduces board
space and facilitates automated assembly.
typical application circuit
Stereo
RLR
L
C
C
C
C
VO1
VO2
BYPASS
IN2–
IN1–
C
B
R
F
R
F
R
I
R
I
C
I
C
I
R
L
Stereo Audio
Input
Mute
Control
From System
Control
C
B
V
DD
4
3
2
1
8
6
5
Depop
Circuitry
–
–
+
+
R
C
R
C
Copyright 2000, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of Texas Instruments
standard warranty. Production processing does not necessarily include
testing of all parameters.
1
2
3
4
8
7
6
5
VO1
MUTE
BYPASS
IN2–
IN1–
GND
V
DD
VO2
D PACKAGE
(TOP VIEW)
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
2
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
AVAILABLE OPTIONS
PACKAGED DEVICE
T
A
SMALL OUTLINE
–40°C to 85°C TPA152D
†
†
The D packages are available taped and reeled. T o
order a taped and reeled part, add the suffix R
(e.g., TPA152DR)
Terminal Functions
TERMINAL
NAME NO.
I/O
DESCRIPTION
BYPASS 3 BYPASS is the tap to the voltage divider for internal mid-supply bias. This terminal should be connected to a 0.1-µF
to 1-µF capacitor.
GND 7 GND is the ground connection.
IN1– 8 I IN1– is the inverting input for channel 1.
IN2– 4 I IN2– is the inverting input for channel 2.
MUTE 2 I A logic high puts the device into MUTE mode.
V
DD
6 I VDD is the supply voltage terminal.
VO1 1 O VO1 is the audio output for channel 1.
VO2 5 O VO2 is the audio output for channel 1.
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
3
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
absolute maximum ratings over operating free-air temperature range (unless otherwise noted)
‡
Supply voltage, VDD 6 V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Input voltage , VI –0.3 V to VDD + 0.3 V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Continuous total power dissipation internally limited (See Dissipation Rating Table). . . . . . . . . . . . . . . . . . . . .
Operating junction temperature range, T
J
–40°C to 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Operating case temperature range, TC –40°C to 125°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Storage temperature range, T
stg
–65°C to 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds 260°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
†
Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
DISSIPATION RATING TABLE
PACKAGE
TA ≤ 25°C DERATING FACTOR TA = 70°C TA = 85°C
D 724 mW 5.8 mW/°C 464 mW 376 mW
recommended operating conditions
MIN MAX UNIT
Supply voltage, V
DD
4.5 5.5 V
Operating free-air temperature, T
A
–40 85 °C
dc electrical characteristics at TA = 25°C, VDD = 5 V
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
V
OO
Output offset voltage 10 mV
Supply ripple rejection ratio VDD = 4.9 V to 5.1 V 81 dB
I
DD
Supply current See Figure 13 5.5 14 mA
I
DD(MUTE)
Supply current in MUTE 5.5 14 mA
Z
I
Input impedance >1 MΩ
ac operating characteristics VDD = 5 V, TA = 25°C, RL = 32 Ω (unless otherwise noted)
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
P
O
Output power (each channel) THD ≤ 0.03%, Gain = 1, See Figure 1 75
†
mW
THD+N Total harmonic distortion plus noise
PO = 75 mW, 20 Hz–20 kHz, Gain = 1,
See Figure 2
0.2%
B
OM
Maximum output power bandwidth AV = 5, THD <0.6%, See Figure 2 >20 kHz
Phase margin Open loop, See Figure 16 80°
Supply ripple rejection ratio 1 kHz, CB = 1 µF, See Figure 12 65 dB
Mute attenuation See Figure 15 110 dB
Ch/Ch output separation See Figure 13 102 dB
Signal-to-Noise ratio VO = 1 V
(rms)
, Gain = 1 See Figure 11 104 dB
V
n
Noise output voltage See Figure 10 6 µV(rms)
†
Measured at 1 kHz.
NOTES: 1. The dc output voltage is approximately VDD/2.
2. Output power is measured at the output pins of the IC at 1 kHz.
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
4
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
ac operating characteristics VDD = 5 V, TA = 25°C, RL = 10 kΩ
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
p
VI = 1 V
(rms)
, 20 Hz–20 kHz,Gain = 1,
See Figure 6
0.005%
THD+N
Total harmonic distortion plus noise
V
O(PP)
= 4 V, 20 Hz–20 kHz, Gain = 1,
See Figure 8
0.005%
B
OM
Maximum output power bandwidth G = 5, THD <0.02%, See Figure 6 >20 kHz
Phase margin Open loop, See Figure 16 80°
k
SVR
Supply voltage rejection ratio 1 kHz, CB = 1 µF, See Figure 12 65 dB
Mute attenuation See Figure 15 110 dB
Ch/Ch output separation See Figure 13 102 dB
Signal-to-Noise ratio VO = 1 V
(rms)
, Gain = 1, See Figure 11 104 dB
V
n
Noise output voltage See Figure 10 6 µV(rms)
†
Measured at 1 kHz.
TYPICAL CHARACTERISTICS
Table of Graphs
FIGURE
THD+N Total harmonic distortion plus noise vs Output power 1, 4
THD+N Total harmonic distortion plus noise vs Frequency 2, 3, 6, 8, 9
THD+N Total harmonic distortion plus noise vs Output voltage 5, 7
V
n
Output noise voltage vs Frequency 10
SNR Signal-to-noise ratio vs Gain 11
Supply ripple rejection ratio vs Frequency 12
Crosstalk vs Frequency 13, 14
Mute Attenuation vs Frequency 15
Open-loop gain and phase vs Frequency 16, 17
Closed-loop gain and phase vs Frequency 18
I
DD
Supply current vs Supply voltage 19
P
O
Output power vs Load resistance 20
P
D
Power dissipation vs Output power 21
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
5
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
Figure 1
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
OUTPUT POWER
PO – Output Power – mW
1102030 60705040
80
0.1
0.01
0.001
1
2
90
f = 1 kHz
AV = –1 V/V
THD+N –Total Harmonic Distortion + Noise – %
Figure 2
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
PO = 75 mW
RL = 32 Ω
AV =– 2 V/V
AV = –5 V/V
AV = –1 V/V
0.1
0.01
0.001
1
2
THD+N –Total Harmonic Distortion + Noise – %
f – Frequency – Hz
20 100 1k 10k 20k
Figure 3
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
AV = –1 V/V
RL = 32 Ω
0.1
0.01
0.001
0.3
THD+N –Total Harmonic Distortion + Noise – %
f – Frequency – Hz
20 100 1k 10k 20k
PO = 75 mW
PO = 25 mW
PO = 50 mW
Figure 4
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
OUTPUT POWER
0.1
0.01
0.001
1
2
THD+N –Total Harmonic Distortion + Noise – %
0.1 1 10 100
RL = 32 Ω
20 kHz
1 kHz
20 Hz
PO – Output Power – mW
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
6
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
Figure 5
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
OUTPUT VOLTAGE
VO – Output Voltage – V
(rms)
0 0.2 0.4 0.6 1.2 1.410.8
1.6
0.1
0.01
0.001
1
2
1.8
f = 1 kHz
AV = –1 V/V
RL = 10 kΩ
THD+N –Total Harmonic Distortion + Noise – %
Figure 6
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
VO = 1 V
(rms)
RL = 10 kΩ
AV = –5 V/V
0.01
0.001
0.1
THD+N –Total Harmonic Distortion + Noise – %
f – Frequency – Hz
20 100 1k 10k 20k
AV = –2 V/V
AV = –1 V/V
Figure 7
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
OUTPUT VOLTAGE
VO – Output Voltage – V
(rms)
0.1 0.2 0.4 1
2
0.1
0.01
0.001
1
2
AV = –1 V/V
RL = 10 kΩ
THD+N –Total Harmonic Distortion + Noise – %
f = 20 kHz
f = 20 Hz
f = 1 kHz
Figure 8
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
V
O(PP)
= 4 V
AV = –1 V/V
RL = 10 kΩ
0.01
0.001
0.1
THD+N –Total Harmonic Distortion + Noise – %
f – Frequency – Hz
20 100 1k 10k 20k
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
7
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
Figure 9
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
VI = 1 V
(rms)
AV = –1 V/V
0.01
0.001
0.1
THD+N –Total Harmonic Distortion + Noise – %
f – Frequency – Hz
20 100 1k 10k 20k
RL = 32 Ω
RL = 10,47, and 100 kΩ
Figure 10
OUTPUT NOISE VOLTAGE
vs
FREQUENCY
VDD = 5 V
BW = 10 Hz to 22 kHz
RL = 32 Ω to 10 kΩ
AV = –1 V/V
10
1
20
f – Frequency – Hz
20 100 1k 10k 20k
– Output Noise Voltage – VµV
n
Figure 11
Gain – V/V
SIGNAL-TO-NOISE RATIO
vs
GAIN
1234 7865
105
95
85
80
100
90
110
9
RL = 10 kΩ
SNR – Signal-to-Noise Ratio – dB
10
RI = 20 kΩ
RL = 32 Ω
Figure 12
Supply Ripple Rejection Ratio – dB
SUPPLY RIPPLE REJECTION RATIO
vs
FREQUENCY
f – Frequency – Hz
20 100 1k 10k 20k
–50
–70
–90
–100
–60
–80
0
–20
–40
–10
–30
VDD = 5 V
RL = 32 Ω to 10 kΩ
CB = 0.1 µF
CB = 1 µF
CB = 2.5 V
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
8
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
Figure 13
Crosstalk – dB
CROSSTALK
vs
FREQUENCY
f – Frequency – Hz
20 100 1k 10k 20k
–90
–120
–100
–110
–60
–70
–80
PO = 75 mW
VDD = 5 V
RL = 32 Ω
CB = 1 µF
AV = –1 V/V
Right to Left
Left to Right
Figure 14
Crosstalk – dB
CROSSTALK
vs
FREQUENCY
f – Frequency – Hz
20 100 1k 10k 20k
–90
–130
–100
–110
–60
–70
–80
VO = 1 V
VDD = 5 V
RL = 10 kΩ
CB = 1 µF
AV = –1 V/V
Right to Left
Left to Right
–120
Mute Attenuation – dB
MUTE ATTENUATION
vs
FREQUENCY
f – Frequency – Hz
20 100 1k 10k 20k
–100
–140
–110
–120
–70
–80
90
VDD = 5 V
RL = 32Ω
CB = 1 µF
–130
Figure 15
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
9
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
Figure 16
OPEN-LOOP GAIN AND PHASE
vs
FREQUENCY
60
20
–20
10k 1M
f – Frequency – Hz
80
40
0
100k 10M 100M1k
Open-Loop Gain – dB
100
20
0
40
Phase –
°
60
80
No Load
100
120
140
160
100
CLOSED-LOOP GAIN AND PHASE
vs
FREQUENCY
–0.2
–0.6
–1
10k 1M
f – Frequency – Hz
0
–0.4
–0.8
100k1k
Closed-Loop Gain – dB
0.2
160
155
165
Phase –
°
170
175
180
185
10
RI = 20 kΩ
Rf = 20 kΩ
RL = 32 Ω
CI = 1 µF
AV = –1 V/V
0.6
0.8
0.4
1
100
Figure 17
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
10
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
Figure 18
CLOSED-LOOP GAIN AND PHASE
vs
FREQUENCY
–0.2
–0.6
–1
10k 1M
f – Frequency – Hz
0
–0.4
–0.8
100k1k
Closed-Loop Gain – dB
0.2
160
155
165
Phase –
°
170
175
180
185
10
RI = 20 kΩ
Rf = 20 kΩ
RL = 10 kΩ
CI = 1 µF
AV = –1 V/V
0.6
0.8
0.4
1
100
Figure 19
VDD – Supply Voltage – V
SUPPLY CURRENT
vs
SUPPLY VOLTAGE
9
7
5
3
5
8
6
4
5.5
10
4.5
I
DD
– Supply Current – mA
Figure 20
RL – Load Resistance – Ω
OUTPUT POWER
vs
LOAD RESISTANCE
30 50 70 90 150 170130110 190
70
50
30
10
60
40
20
90
80
210
THD+N = 0.1%
AV = –1 V/V
– Output Power – mWP
O
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
11
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
Figure 21
POWER DISSIPATION
vs
OUTPUT POWER
100
80
40
0
60
20
0 5 10 15
PO – Output Power – mW
2520
P
D
– Power Dissipation – mW
RL = 32 Ω
APPLICATION INFORMATION
selection of components
Figure 22 is a schematic diagram of a typical application circuit.
8
7
6
5
GND
V
DD
IN1–
4
1
2
3
VO1
MUTE
IN2–
R
I
20 kΩ
Audio Input 1
C
I
1 µF
IN2
VO2
R
F
20 kΩ
Shutdown
(from System Control)
R
I
20 kΩ
Audio Input 2
C
I
1 µF
R
F
20 kΩ
C
C
330 µF
R
C
†
100 Ω
C
C
330 µF
V
DD
1 µF
HP
Jack
R
L
32 Ω
R
L
32 Ω
C
B
1 µF
R
O
†
20 kΩ
R
C
†
100 Ω
R
O
†
20 kΩ
†
These resistors are optional. Adding these resistors improves the depop performance of the TPA152.
Figure 22. TPA152 Typical Application Circuit
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
12
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
APPLICATION INFORMATION
gain setting resistors, RF and R
I
The gain for the TPA152 is set by resistors RF and RI according to equation 1.
(1)
Gain
+*
ǒ
R
F
R
I
Ǔ
Given that the TPA152 is a MOS amplifier, the input impedance is very high, consequently input leakage
currents are not generally a concern although noise in the circuit increases as the value of RF increases. In
addition, a certain range of R
F
values are required for proper start-up operation of the amplifier. Taken together
it is recommended that the effective impedance seen by the inverting node of the amplifier be set between 5
kΩ and 20 kΩ. The effective impedance is calculated in equation 2.
(2)
Effective Impedance
+
RFR
I
RF)
R
I
As an example, consider an input resistance of 20 kΩ and a feedback resistor of 20 kΩ. The gain of the amplifier
would be – 1 and the effective impedance at the inverting terminal would be 10 kΩ, which is within the
recommended range.
For high performance applications, metal film resistors are recommended because they tend to have lower
noise levels than carbon resistors. For values of R
F
above 50 kΩ, the amplifier tends to become unstable due
to a pole formed from RF and the inherent input capacitance of the MOS input structure. For this reason, a small
compensation capacitor of approximately 5 pF should be placed in parallel with RF. This, in effect, creates a
low-pass filter network with the cutoff frequency defined in equation 3.
(3)
f
c(lowpass)
+
1
2pRFC
F
For example if RF is 100 kΩ and CF is 5 pF then f
co(lowpass)
is 318 kHz, which is well outside the audio range.
input capacitor, C
I
In the typical application, an input capacitor, CI, is required to allow the amplifier to bias the input signal to the
proper dc level for optimum operation. In this case, CI and RI form a high-pass filter with the corner frequency
determined in equation 4.
(4)
f
c(highpass)
+
1
2pRIC
I
The value of CI is important to consider as it directly affects the bass (low frequency) performance of the circuit.
Consider the example where RI is 20 kΩ and the specification calls for a flat bass response down to 20 Hz.
Equation 4 is reconfigured as equation 5.
(5)
C
I
+
1
2pRIf
c(highpass)
In this example, CI is 0.40 µF, so one would likely choose a value in the range of 0.47 µF to 1 µF. A further
consideration for this capacitor is the leakage path from the input source through the input network (R
I
, CI) and
the feedback resistor (RF) to the load. This leakage current creates a dc offset voltage at the input to the amplifier
that reduces useful headroom, especially in high-gain applications (> 10). For this reason a low-leakage
tantalum or ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the
capacitor should face the amplifier input in most applications, as the dc level there is held at V
DD
/2, which is
likely higher that the source dc level. Please note that it is important to confirm the capacitor polarity in the
application.
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
13
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
APPLICATION INFORMATION
power supply decoupling, C
S
The TP A152 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling to
ensure that the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also
prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is
achieved by using two capacitors of different types that target different types of noise on the power supply leads.
For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance
(ESR) ceramic capacitor, typically 0.1 µF, placed as close as possible to the device V
DD
lead, works best. For
filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF or greater placed near
the power amplifier is recommended.
midrail bypass capacitor, C
B
The midrail bypass capacitor, CB, serves several important functions. During startup or recovery from shutdown
mode, CB determines the rate at which the amplifier starts up. This helps to push the start-up pop noise into
the subaudible range (so slow it can not be heard). The second function is to reduce noise produced by the
power supply caused by coupling into the output drive signal. This noise is from the midrail generation circuit
internal to the amplifier. The capacitor is fed from a 160-kΩ source inside the amplifier . To keep the start-up pop
as low as possible, the relationship shown in equation 6 should be maintained.
(6)
1
ǒ
CB
160 kΩ
Ǔ
v
1
ǒ
CIR
I
Ǔ
As an example, consider a circuit where CB is 1 µF, CI is 1 µF and RI is 20 kΩ. Inserting these values into the
equation 9 results in:
6.25v50
which satisfies the rule. Bypass capacitor, CB, values of 0.1 µF to 1 µF ceramic or tantalum low-ESR capacitors
are recommended for the best THD and noise performance.
output coupling capacitor, C
C
In the typical single-supply single-ended (SE) configuration, an output coupling capacitor (CC) is required to
block the dc bias at the output of the amplifier thus preventing dc currents in the load. As with the input coupling
capacitor, the output coupling capacitor and impedance of the load form a high-pass filter governed by
equation 7.
(7)
f
c(high)
+
1
2pR
L
C
C
The main disadvantage, from a performance standpoint, is that the load impedances are typically small, which
drive the low-frequency corner higher. Large values of C
C
are required to pass low frequencies into the load.
Consider the example where a CC of 68 µF is chosen and loads vary from 32 Ω to 47 kΩ. Table 1 summarizes
the frequency response characteristics of each configuration.
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
14
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
APPLICATION INFORMATION
Table 1. Common Load Impedances vs Low Frequency Output Characteristics in SE Mode
R
L
C
C
LOWEST FREQUENCY
32 Ω 68 µF
73 Hz
10,000 Ω 68 µF 0.23 Hz
47,000 Ω 68 µF 0.05 Hz
As Table 1 indicates, headphone response is adequate and drive into line level inputs (a home stereo for
example) is very good.
The output coupling capacitor required in single-supply SE mode also places additional constraints on the
selection of other components in the amplifier circuit. With the rules described earlier still valid, add the following
relationship:
(8)
1
ǒ
CB
160 kΩ
Ǔ
v
1
ǒ
CIR
I
Ǔ
Ơ
1
RLC
C
output pull-down resistor, RC + R
O
Placing a 100-Ω resistor, RC, from the output side of the coupling capacitor to ground insures the coupling
capacitor, CC, is charged before a plug is inserted into the jack. Without this resistor, the coupling capacitor
would charge rapidly upon insertion of a plug, leading to an audible pop in the headphones.
Placing a 20-kΩ resistor, RO, from the output of the IC to ground insures that the coupling capacitor fully
discharges at power down. If the supply is rapidly cycled without this capacitor, a small pop may be audible in
10-kΩ loads.
using low-ESR capacitors
Low-ESR capacitors are recommended throughout this applications section. A real capacitor can be modeled
simply as a resistor in series with an ideal capacitor. The voltage drop across this resistor minimizes the
beneficial effects of the capacitor in the circuit. The lower the equivalent value of this resistance, the more the
real capacitor behaves like an ideal capacitor.
TPA152
75-mW STEREO AUDIO POWER AMPLIFIER
SLOS210A – JUNE 1998 – REVISED MARCH 2000
15
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
MECHANICAL DATA
D (R-PDSO-G**) PLASTIC SMALL-OUTLINE PACKAGE
14 PINS SHOWN
4040047/D 10/96
0.228 (5,80)
0.244 (6,20)
0.069 (1,75) MAX
0.010 (0,25)
0.004 (0,10)
1
14
0.014 (0,35)
0.020 (0,51)
A
0.157 (4,00)
0.150 (3,81)
7
8
0.044 (1,12)
0.016 (0,40)
Seating Plane
0.010 (0,25)
PINS **
0.008 (0,20) NOM
A MIN
A MAX
DIM
Gage Plane
0.189
(4,80)
(5,00)
0.197
8
(8,55)
(8,75)
0.337
14
0.344
(9,80)
16
0.394
(10,00)
0.386
0.004 (0,10)
M
0.010 (0,25)
0.050 (1,27)
0°–8°
NOTES: A. All linear dimensions are in inches (millimeters).
B. This drawing is subject to change without notice.
C. Body dimensions do not include mold flash or protrusion, not to exceed 0.006 (0,15).
D. Falls within JEDEC MS-012
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Copyright 2000, Texas Instruments Incorporated
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