Datasheet TPA0102PWPR, TPA0102PWPLE, TPA0102PWP, TPA0102EVM Datasheet (Texas Instruments)

Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.

TP A0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

High Power with PC Power Supply – 1.5 W/Ch at 5 V – 600 mW/Ch at 3 V

Ultra-Low Distortion

< 0.05% THD+N at 1.5 W and 4-Ω Load

Bridge-Tied Load (BTL) or Single Ended (SE) Modes

Stereo Input MUX

Surface-Mount Power Package

24-Pin TSSOP PowerP AD

Shutdown Control ...IDD < 10 µA

Right

MUX

RLINEIN RHPIN

Left

MUX

LHPIN

LLINEIN

Bias, Mute, Shutdown,

and SE/BTL

MUX Control

–

RBYPASS

MUTE IN MUTE OUT SHUTDOWN

LBYPASS

ROUT+

ROUT–

LOUT+

LOUT–

SE/BTL

HP/LINE

System Control

100 kΩ

OUTR

OUTL

1 kΩ

0.1 µF

1 2 3 4 5 6 7 8 9 10 11 12

24 23 22 21 20 19 18 17 16 15 14 13

GND/HS

LOUT+

LLINEIN

LHPIN

LBYPASS

SHUTDOWN

MUTE OUT

LOUT–

MUTE IN

GND/HS

GND/HS NC ROUT+ RLINEIN RHPIN RBYPASS RV

NC HP/LINE ROUT– SE/BTL GND/HS

PWP PACKAGE

(TOP VIEW)

PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters.

PowerPAD is a trademark of Texas Instruments Incorporated.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

description

The TPA0102 is a stereo audio power amplifier in a 24-pin TSSOP thermal package capable of delivering greater than 1.5 W of continuous RMS power per channel into 4-Ω loads. This device functionality provides a very efficient upgrade path from the TP A4860 and TP A4861 mono amplifiers where three separate devices are required for stereo applications: two for speaker drive, plus a third for headphone drive. The TP A0102 simplifies design and frees up board space for other features. Full power distortion levels of less than 0.1% THD+N from a 5-V supply are typical. This provides significant improvement in fidelity for speech and music over the popular TPA4860/61 series. Low-voltage applications are also well served by the TPA0102 providing 600-mW per channel into 4-Ω loads with a 3.3-V supply voltage.

Amplifier gain is externally configured by means of two resistors per input channel and does not require external compensation for settings of 2 to 20 in BTL mode (1 to 10 in SE mode). An internal input MUX allows two sets of stereo inputs to the amplifier. In notebook applications, where internal speakers are driven as BTL and the line (often headphone drive) outputs are required to be SE, the TP A0102 automatically switches into SE mode when the SE/BTL

input is activated. Using the TP A0102 to drive line outputs up to 500 mW/channel into external 4 Ω loads is ideal for small non-powered external speakers in portable multimedia systems. The TPA0102 also features a shutdown function for power sensitive applications, holding the supply current below 5 µA. In speakerphone or other monaural applications, the TP A0102 is configured through the power supply terminals to activate only half of the amplifier which reduces supply current by approximately one-half over stereo applications.

The PowerPAD package (PWP) delivers a level of thermal performance that was previously achievable only in TO-220-type packages. Thermal impedances of approximately 35°C/W are readily realized in multilayer PCB applications. This allows the TP A0102 to operate at full power into 4- Ω loads at ambient temperature of up to 55°C. Into 8-Ω loads, the operating ambient temperature increases to 100°C.

AVAILABLE OPTIONS

PACKAGE

TSSOP

(PWP)

40°C to 85°C TPA0102PWP

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

Terminal Functions

TERMINAL

NAME NO.

I/O

DESCRIPTION

GND/HS 1, 12,

13, 24

Ground connection for circuitry, directly connected to thermal pad

HP/LINE 16 I Input MUX control input, hold high to select L/RHPIN (5, 20), hold low to select L/RLINEIN (4, 21) LBYPASS 6 Tap to voltage divider for left channel internal mid-supply bias LHP IN 5 I Left channel headphone input, selected when HP/LINE terminal (16) is held high LLINE IN 4 I Left channel line input, selected when HP/LINE terminal (16) is held low LOUT+ 3 O Left channel + output in BTL mode, + output in SE mode LOUT– 10 O Left channel – output in BTL mode, high-impedance state in SE mode LV

7 I Supply voltage input for left channel and for primary bias circuits MUTE IN 11 I Mute all amplifiers, hold low for normal operation, hold high to mute MUTE OUT 9 O Follows MUTE IN terminal (11), provides buffered output NC 2, 17, 23 No internal connection RBYPASS 19 Tap to voltage divider for right channel internal mid–supply bias RHP IN 20 I Right channel headphone input, selected when HP/LINE terminal (16) is held high RLINE IN 21 I Right channel line input, selected when HP/LINE terminal (16) is held low

ROUT+ 22 O Right channel + output in BTL mode, + output in SE mode ROUT– 15 O Right channel – output in BTL mode, high impedance state in SE mode RV

18 I Supply voltage input for right channel SE/BTL 14 I Hold low for BTL mode, hold high for SE mode SHUTDOWN 8 I Places entire IC in shutdown mode when held high, I

< I µA

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

absolute maximum ratings over operating free-air temperature range (unless otherwise noted)

†

Supply voltage, VDD 6 V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Input voltage, VI –0.3 V to VDD +0.3 V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Continuous total power dissipation internally limited (see Dissipation Rating Table). . . . . . . . . . . . . . . . . . . . .

Operating free-air temperature range, T

–40°C to 85°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Operating junction temperature range, TJ –40°C to 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Storage temperature range, T

stg

–65°C to 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds 260°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

†

Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.

DISSIPATION RATING TABLE

PACKAGE

TA ≤ 25°C DERATING FACTOR TA = 70°C TA = 85°C

PWP 2.7 W

‡

21.8 mW/°C 1.7 W 1.4 W

‡

Please see the Texas Instruments document,

PowerPAD Thermally Enhanced Package Application Report

(literature number SLMA002), for more information on the PowerPAD package. The thermal data was measured on a PCB layout based on the information in the section entitled

T exas Instruments Recommended

Board for PowerPAD

on page 33 of the before mentioned document.

recommended operating conditions

MIN NOM MAX UNIT

Supply voltage, V

3 5 5.5 V

VDD = 5 V, 4-Ω stereo BTL drive, 250 mW/ch average power, With proper PCB design

–40 85

Operating free-air temperature, T

VDD = 5 V, 4-Ω stereo BTL drive,

1.5 W/ch average power, With proper PCB design

–40 55

°C

VDD = 5 V 1.25 4.5

Common mode input voltage, V

ICM

VDD = 3.3 V 1.25 2.7

dc electrical characteristics, TA = 25°C

PARAMETER TEST CONDITIONS TYP†MAX UNIT

Stereo BTL 19 25 mA Stereo SE 9 15 mA

= 5

Mono BTL 9 15 mA

Mono SE 3 10 mA

IDDSupply current

Stereo BTL 13 20 mA Stereo SE 3 10 mA

3.3 V

Mono BTL 3 10 mA Mono SE 3 10 mA

Output offset voltage (measured differentially)

VDD = 5 V Gain = 2, See Note 1 5 25 mV

DD(MUTE)

Supply current in mute mode VDD = 5 V 800 µA

DD(SD)

IDD in shutdown VDD = 5 V 5 15 µA

NOTE 1: At 3 V < VDD < 5 V the dc output voltage is approximately VDD/2.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

ac operating characteristics, V

= 5 V, T

= 25°C, R

= 4 Ω

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

THD = 0.2%, BTL 1.25

THD = 1%, BTL 1.5

POOutput power (each channel) see Note 2

THD = 0.2%, SE 500 THD = 1%, SE 600

THD+N Total harmonic distortion plus noise Po = 1 W, f = 20 to 20 kHz 200 m% B

Maximum output power bandwidth G = 10, THD < 5 % >20 kHz

BTL 72°

Phase margin

Open Load

71°

SE 52°

f = 1 kHz 75

Power supply ripple rejection

f = 20 – 20 kHz, 60

Mute attenuation 85 dB Channel-to-channel output separation f = 1 kHz 65 dB Line/HP input separation 100 dB BTL attenuation in SE mode 100 dB

Input impedance 2 MΩ Signal-to-noise ratio Po = 500 mW, BTL 95 dB

Output noise voltage 25 µV(rms)

NOTE 2: Output power is measured at the output terminals of the IC at 1 kHz.

ac operating characteristics, V

= 3.3 V, TA = 25°C, RL = 4 Ω

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

THD = 0.2% BTL 600

THD = 1% BTL 750

POOutput power (each channel) see Note 2

THD = 0.2%, SE 200

THD = 1%, SE 250 THD+N Total harmonic distortion plus noise Po = 600 mW, f = 20 to 20 kHz 250 m% B

Maximum output power bandwidth G = 10, THD < 5 % >20 kHz

BTL 92°

Phase margin

Open Load

70°

SE 57°

f = 1 kHz 70

Power supply ripple rejection

f = 20 – 20 kHz 55

Mute attenuation 85 dB Channel-to-channel output separation f = 1 kHz 65 dB Line/HP input separation 100 dB BTL attenuation in SE mode 100 dB

Input impedance 2 MΩ Signal-to-noise ratio Po = 500 mW, BTL 95 dB

Output noise voltage 25 µV(rms)

NOTE 2 Output power is measured at the output terminals of the IC at 1 kHz.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

PARAMETER MEASUREMENT INFORMATION

MUX

4.7 µF

SE/BTL

HP/LINE

RL = 4 Ω or 8 Ω

Figure 1. BTL Test Circuit

MUX

SE/BTL

HP/LINE

RL = 4 Ω, 8 Ω, or 32 Ω

4.7 µF

Figure 2. SE Test Circuit

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Table of Graphs

FIGURE

vs Frequency

4, 5, 7, 8, 11, 12, 14, 15, 17, 18, 20,

21, 23, 24, 26, 27, 29, 30, 32, 33

THD

Total harmonic distortion plus noise

vs Output power

3, 6, 9, 10, 13, 16, 19, 22, 25, 28,

31, 34

Output noise voltage vs Frequency 35, 36 Supply ripple rejection ratio vs Frequency 37, 38 Crosstalk vs Frequency 39–40 Open loop response vs Frequency 43, 44 Closed loop response vs Frequency 45 – 48

Supply current vs Supply voltage 49

Output power

vs Supply voltage vs Load resistance

50,51 52,53

Power dissipation vs Output power 54 – 57

Figure 3

0.1

0.01 0 0.25 0.5 0.75 1 1.25 1.5

1.75 2 2.25 2.5

PO – Output Power – W

VDD = 5 V f = 1 kHz BTL

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

RL = 4 Ω

RL = 8 Ω

Figure 4

0.01

20 100 1 k 10 k 20 k

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 5 V PO = 1.5 W RL = 4 Ω BTL

AV = –2 V/V

AV = –20 V/V

AV = –10 V/V

0.1

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 5

PO = 1.5 W

PO = 0.25 W

VDD = 5 V RL = 4 Ω AV = –2 V/V BTL

0.1

0.01 20 100 1 k

10 k 20 k

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

PO = 0.75 W

Figure 6

f = 20 kHz

f = 1 kHz

f = 20 Hz

0.1

0.01

0.01 0.1

110

PO – Output Power – W

VDD = 5 V RL = 4 Ω BTL

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

Figure 7

0.1

0.01 20 100 1 k

10 k 20 k

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

PO = 1 W

VDD = 5 V RL = 8 Ω AV = –2 V/V BTL

PO = 0.25 W

PO = 0.5 W

Figure 8

0.1

0.01 20 100 1 k

10 k 20 k

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 5 V PO = 1 W RL = 8 Ω BTL

AV = –2 V/V

AV = –20 V/V

AV = –10 V/V

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 9

0.1

0.01

0.01 0.1

110

f = 20 kHz

f = 1 kHz

f = 20 Hz

PO – Output Power – W

VDD = 5 V RL = 8 Ω AV = –2 V/V BTL

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

Figure 10

0.1

0.01 0 0.1 0.2 0.3 0.4 0.5 0.6

0.7 0.8 0.9 1

PO – Output Power – W

VDD = 3.3 V f = 1 kHz BTL

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

RL = 4 Ω

RL = 8 Ω

Figure 11

0.1

0.01 20 100 1 k

10 k 20 k

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 3.3 V PO = 0.75 W RL = 4 Ω BTL

AV = –10 V/V

AV = –20 V/V

AV = –2 V/V

Figure 12

PO = 0.35 W

PO = 0.1 W

PO = 0.75 W

0.1

0.01 20 100 1 k

10 k 20 k

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 3.3 V RL = 4 Ω AV = –2 V/V BTL

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 13

0.1

0.01

1100.1

f = 20 kHz

f = 1 kHz

f = 20 Hz

PO – Output Power – W

VDD = 3.3 V RL = 4 Ω AV = –2 V/V BTL

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

Figure 14

0.1

0.01 20 100 1 k

10 k 20 k

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

AV = –20 V/V

AV = –10 V/V

AV = –2 V/V

VDD = 3.3 V PO = 0.4 W RL = 8 Ω BTL

Figure 15

PO = 0.4 W

PO = 0.25 W

PO = 0.1 W

VDD = 3.3 V RL = 8 Ω AV = –2 V/V BTL

0.1

0.01 20 100 1 k

10 k 20 k

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

Figure 16

0.1

0.01

0.01 0.1

110

f = 20 kHz

f = 1 kHz

f = 20 Hz

PO – Output Power – W

VDD = 3.3 V RL = 8 Ω AV = –2 V/V BTL

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 17

0.1

0.01 20 100 1 k

10 k 20 k

AV = –10 V/V

AV = –5 V/V

AV = –1 V/V

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 5 V PO = 0.5 W RL = 4 Ω SE

Figure 18

0.1

0.01 20 100 1 k

10 k 20 k

PO = 0.25 W

PO = 0.1 W

PO = 0.5 W

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 5 V RL = 4 Ω AV = –2 V/V SE

Figure 19

f = 20 kHz

f =100 Hz

f = 1 kHz

VDD = 5 V RL = 4 Ω AV = –2 V/V SE

0.1

0.01

0.001 0.01

0.1 1

PO – Output Power – W

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

Figure 20

0.1

0.01 20 100 1 k

10 k 20 k

AV = –10 V/V

AV = –5 V/V

AV = –1 V/V

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 5 V PO = 0.25 W RL = 8 Ω SE

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 21

0.1

0.01 20 100 1 k

10 k 20 k

PO = 0.25 W

PO = 0.05 W

PO = 0.1 W

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 5 V RL = 8 Ω SE

Figure 22

0.1

0.01

0.001 0.1

PO – Output Power – W

VDD = 5 V RL = 8 Ω AV = –2 V/V SE

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

0.01

f = 20 kHz

f = 1 kHz

f = 100 Hz

Figure 23

0.1

0.01 20 100 1 k

10 k 20 k

AV = –10 V/V

AV = –5 V/V

AV = –1 V/V

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 5 V PO = 0.075 W RL = 32 Ω SE

Figure 24

0.1

0.01 20 100 1 k

10 k 20 k

PO = 75 mW

PO = 25 mW

PO = 50 mW

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 5 V RL = 32 Ω SE

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 25

0.1

0.01

0.001 0.01

0.1 1

f = 20 kHz

f = 1 kHz

f = 20 Hz

PO – Output Power – W

VDD = 5 V RL = 32 Ω SE

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

Figure 26

0.1

0.01 20 100 1 k

10 k 20 k

AV = –10 V/V

AV = –5 V/V

AV = –1 V/V

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 3.3 V PO = 0.2 W RL = 4 Ω SE

Figure 27

0.1

0.01 20 100 1 k

10 k 20 k

PO = 0.05 W

PO = 0.1 W

PO = 0.2 W

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 3.3 V RL = 4 Ω SE

Figure 28

f = 100 Hz

f = 1 kHz

f = 20 kHz

VDD = 3.3 V RL = 4 Ω AV = –2 V/V SE

0.1

0.01

0.001 0.01

10.1

PO – Output Power – W

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 29

AV = –10 V/V

AV = –5 V/V

AV = –1 V/V

VDD = 3.3 V PO = 100 mW RL = 8 Ω SE

0.1

0.01 20 100 1 k

10 k 20 k

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

Figure 30

0.1

0.01 20 100 1 k

10 k 20 k

PO = 25 mW

PO = 50 mW

PO = 100 mW

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 3.3 V RL = 8 Ω SE

Figure 31

VDD = 3.3 V RL = 8 Ω SE

0.1

0.01

0.001 0.1

PO – Output Power – W

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

f = 20 kHz

f = 1 kHz

f = 100 Hz

0.01

Figure 32

0.1

0.01 20 100 1 k

10 k 20 k

AV = –10 V/V

AV = –5 V/V

AV = –1 V/V

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 3.3 V PO = 30 mW RL = 32 Ω SE

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 33

0.1

0.01

0.001 20 100 1 k

10 k 20 k

PO = 10 mW

PO = 20 mW

PO = 30 mW

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

TOTAL HARMONIC DISTORTION PLUS NOISE

FREQUENCY

VDD = 3.3 V RL = 32 Ω SE

Figure 34

0.1

0.01

0.001

0.001 0.01

0.1 1

f = 20 Hz

f = 1 kHz

f = 20 kHz

PO – Output Power – W

VDD = 3.3 V RL = 32 Ω SE

THD+N –Total Harmonic Distortion + Noise – %

TOTAL HARMONIC DISTORTION PLUS NOISE

OUTPUT POWER

Figure 35

20 100 1 k

f – Frequency – Hz

OUTPUT NOISE VOLTAGE

FREQUENCY

100

10 k 20 k

VDD = 5 V BW = 22 Hz to 22 kHz RL = 4Ω

VO BTL V

O+

O–

– Output Noise Voltage –

Vµ

(rms)

Figure 36

20 100 1 k

f – Frequency – Hz

OUTPUT NOISE VOLTAGE

FREQUENCY

100

10 k 20 k

VDD = 3.3 V BW = 22 Hz to 22 kHz RL = 4Ω

VO BTL V

O+

O–

– Output Noise Voltage –

Vµ

(rms)

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 37

–50

–60

–80

–100

20 100 1 k

Supply Ripple Rejection Ratio – dB

–30

–20

f – Frequency – Hz

SUPPLY RIPPLE REJECTION RATIO

FREQUENCY

10 k 20 k

–10

–40

–70

–90

VDD = 5 V

VDD = 3.3 V

RL = 4 Ω CB = 4.7 µF BTL

Figure 38

–50

–60

–80

–100

20 100 1 k

–30

–20

f – Frequency – Hz

SUPPLY RIPPLE REJECTION RATIO

FREQUENCY

10 k 20 k

–10

–40

–70

–90

VDD = 5 V

VDD = 3.3 V

RL = 4 Ω CB = 4.7 µF SE

Supply Ripple Rejection Ratio – dB

Figure 39

Left to Right

Right to Left

–80

–90

–110

–120

–60

–50

–40

–70

–100

20 100 1 k

Crosstalk – dB

f – Frequency – Hz

CROSSTALK

FREQUENCY

10 k 20 k

VDD = 5 V PO = 1.5 W RL = 4 Ω BTL

Figure 40

–80

–90

–110

–120

–60

–50

–40

–70

–100

20 100 1 k

Crosstalk – dB

f – Frequency – Hz

CROSSTALK

FREQUENCY

10 k 20 k

VDD = 3.3 V PO = 0.75 W RL = 4 Ω BTL

Left to Right

Right to Left

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 41

–80

–90

–110

–120

–60

–50

–40

–70

–100

20 100 1 k

Crosstalk – dB

f – Frequency – Hz

CROSSTALK

FREQUENCY

10 k 20 k

VDD = 5 V PO = 75 mW RL = 32 Ω SE

Left to Right

Right to Left

Figure 42

–80

–90

–110

–120

–60

–50

–40

–70

–100

20 100 1 k

Crosstalk – dB

f – Frequency – Hz

CROSSTALK

FREQUENCY

10 k 20 k

VDD = 3.3 V PO = 35 mW RL = 32 Ω SE

Left to Right

Right to Left

–20

–40

0.01

Gain – dB

f – Frequency – kHz

OPEN LOOP RESPONSE

100

0.1 1 10 100 1000 10000

180°

90°

0°

–90°

–180°

VDD = 5 V BTL

Gain

Phase

Figure 43

Phase

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

–20

–40

180°

90°

0°

–90°

–180°

0.01

Gain – dB

f – Frequency – kHz

OPEN LOOP RESPONSE

0.1 1 10 100 1000 10000

VDD = 3.3 V BTL

Gain

Figure 44

Phase

20 100 1 k 10 k

Gain – dB

f – Frequency – Hz

CLOSED LOOP RESPONSE

100 k 200 k

–45°

0°

–90°

–135°

–180°

–225°

–270°

Phase

Gain

VDD = 5 V AV = –2 V/V PO = 1.5 W BTL

Figure 45

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

20 100 1 k 10 k

Gain – dB

f – Frequency – Hz

CLOSED LOOP RESPONSE

100 k 200 k

–45°

0°

–90°

–135°

–180°

–225°

–270°

Phase

Gain

VDD = 3.3 V AV = –2 V/V PO = 0.75 W BTL

Figure 46

Figure 47

–5

–7

–8

–10

20 100 1 k 10 k

Gain – dB

–3

–1

f – Frequency – Hz

CLOSED LOOP RESPONSE

100 k 200 k

–2

–4

–6

–9

–45°

0°

–90°

–135°

–180°

–225°

–270°

Phase

VDD = 5 V AV = –1 V/V PO = 0.5 W SE

Phase

Gain

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

–5

–7

–8

–10

20 100 1 k 10 k

Gain – dB

–3

–1

f – Frequency – Hz

CLOSED LOOP RESPONSE

100 k 200 k

–2

–4

–6

–9

–45°

0°

–90°

–135°

–180°

–225°

–270°

Phase

VDD = 3.3V AV = –1 V/V PO = 0.25 W SE

Phase

Gain

Figure 48

Figure 49

Stereo BTL

SUPPLY CURRENT

SUPPLY VOLTAGE

465

VDD – Supply Voltage – V

Stereo SE

– Supply Current – mA I

Figure 50

1.5

0.5

2.5 3 3.5 4 4.5 5

2.5

5.5 6

RL = 4 Ω

RL = 8 Ω

– Output Power – WP

OUTPUT POWER

SUPPLY VOLTAGE

VDD – Supply Voltage – V

THD+N = 1% BTL Each Channel

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 51

0.4

0.2

2.5 3 3.5 4 4.5 5

0.6

0.8

5.5 6

RL = 4 Ω

RL = 8 Ω

RL = 32 Ω

THD+N = 1% SE Each Channel

– Output Power – WP

OUTPUT POWER

SUPPLY VOLTAGE

VDD – Supply Voltage – V

Figure 52

RL – Load Resistance – Ω

1.5

0.5

04 8121620

2.5

24 28 32

THD+N = 1% BTL Each Channel

– Output Power – WP

OUTPUT POWER

LOAD RESISTANCE

VDD = 5 V

VDD = 3.3 V

Figure 53

0.4

0.2

04 8121620

0.6

0.8

24 28 32

RL – Load Resistance – Ω

THD+N = 1% SE Each Channel

– Output Power – WP

OUTPUT POWER

LOAD RESISTANCE

VDD = 5 V

VDD = 3.3 V

Figure 54

0.6

0.4

0.2

0 0.5 1

– Power Dissipation – W

1.2

POWER DISSIPATION

OUTPUT POWER

1.4

1.5 2

0.8

PO – Output Power – W

RL = 4 Ω

RL = 8 Ω

VDD = 5 V BTL Each Channel

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 55

0.3

0.2

0.1

0 0.25 0.5

– Power Dissipation – W

0.4

0.5

POWER DISSIPATION

OUTPUT POWER

0.6

0.75 1

PO – Output Power – W

RL = 4 Ω

RL = 8 Ω

VDD = 3.3 V BTL Each Channel

Figure 56

0.4

0.2

0 0.1 0.2 0.3

0.6

0.8

0.4 0.5 0.6

– Power Dissipation – W

POWER DISSIPATION

OUTPUT POWER

PO – Output Power – W

RL = 4 Ω

RL = 8 Ω

VDD = 5 V SE Each Channel

RL = 32Ω

Figure 57

0.2

0 0.05 0.1 0.15

0.4

0.6

0.2 0.25

– Power Dissipation – W

POWER DISSIPATION

OUTPUT POWER

PO – Output Power – W

RL = 4 Ω

RL = 8 Ω

VDD = 3.3V SE Each Channel

RL = 32Ω

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

THERMAL INFORMATION

The thermally enhanced PWP package is based on the 24-pin TSSOP, but includes a thermal pad (see Figure 58) to provide an effective thermal contact between the IC and the PWB.

Traditionally, surface mount and power have been mutually exclusive terms. A variety of scaled-down TO-220-type packages have leads formed as gull wings to make them applicable for surface-mount applications. These packages, however, have only two shortcomings: they do not address the very low profile requirements (<2 mm) of many of today’s advanced systems, and they do not offer a terminal-count high enough to accommodate increasing integration. On the other hand, traditional low-power surface-mount packages require power-dissipation derating that severely limits the usable range of many high-performance analog circuits.

The PowerP AD package (thermally enhanced TSSOP) combines fine-pitch surface-mount technology with thermal performance comparable to much larger power packages.

The PowerPAD package is designed to optimize the heat transfer to the PWB. Because of the very small size and limited mass of a TSSOP package, thermal enhancement is achieved by improving the thermal conduction paths that remove heat from the component. The thermal pad is formed using a patented lead-frame design and manufacturing technique to provide a direct connection to the heat-generating IC. When this pad is soldered or otherwise thermally coupled to an external heat dissipator, high power dissipation in the ultra-thin, fine-pitch, surface-mount package can be reliably achieved.

DIE

Side View (a)

End View (b)

Bottom View (c)

DIE

Thermal

Pad

Figure 58. Views of Thermally Enhanced PWP Package

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

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APPLICATION INFORMATION

bridged-tied load versus single-ended mode

Figure 59 shows a linear audio power amplifier (APA) in a BTL configuration. The TPA0102 BTL amplifier consists of two linear amplifiers driving both ends of the load. There are several potential benefits to this differential drive configuration but initially consider power to the load. The differential drive to the speaker means that as one side is slewing up, the other side is slewing down, and vice versa. This in effect doubles the voltage swing on the load as compared to a ground referenced load. Plugging 2 × V

O(PP)

into the power equation, where

voltage is squared, yields 4× the output power from the same supply rail and load impedance (see equation 1).

Power

(rms)

(1)

(rms)

O(PP)

2x V

O(PP)

–V

O(PP)

Figure 59. Bridge-Tied Load Configuration

In a typical computer sound channel operating at 5 V, bridging raises the power into an 8-Ω speaker from a singled-ended (SE, ground reference) limit of 250 mW to 1 W. In sound power that is a 6-dB improvement — which is loudness that can be heard. In addition to increased power there are frequency response concerns. Consider the single-supply SE configuration shown in Figure 60. A coupling capacitor is required to block the dc offset voltage from reaching the load. These capacitors can be quite large (approximately 33 µF to 1000 µF) so they tend to be expensive, heavy , occupy valuable PCB area, and have the additional drawback of limiting low-frequency performance of the system. This frequency limiting effect is due to the high pass filter network created with the speaker impedance and the coupling capacitance and is calculated with equation 2.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

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APPLICATION INFORMATION

fc+

2pR

(2)

For example, a 68-µF capacitor with an 8-Ω speaker would attenuate low frequencies below 293 Hz. The BTL configuration cancels the dc offsets, which eliminates the need for the blocking capacitors. Low-frequency performance is then limited only by the input network and speaker response. Cost and PCB space are also minimized by eliminating the bulky coupling capacitor.

O(PP)

–3 dB

Figure 60. Single-Ended Configuration and Frequency Response

Increasing power to the load does carry a penalty of increased internal power dissipation. The increased dissipation is understandable considering that the BTL configuration produces 4× the output power of the SE configuration. Internal dissipation versus output power is discussed further in the

thermal considerations

section.

BTL amplifier efficiency

Linear amplifiers are notoriously inefficient. The primary cause of these inefficiencies is voltage drop across the output stage transistors. There are two components of the internal voltage drop. One is the headroom or dc voltage drop that varies inversely to output power. The second component is due to the sinewave nature of the output. The total voltage drop can be calculated by subtracting the RMS value of the output voltage from VDD. The internal voltage drop multiplied by the RMS value of the supply current, I

rms, determines the internal

power dissipation of the amplifier. An easy-to-use equation to calculate efficiency starts out as being equal to the ratio of power from the power

supply to the power delivered to the load. To accurately calculate the RMS values of power in the load and in the amplifier, the current and voltage waveform shapes must first be understood (see Figure 61).

(LRMS)

DD(RMS)

Figure 61. Voltage and Current Waveforms for BTL Amplifiers

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

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APPLICATION INFORMATION

Although the voltages and currents for SE and BTL are sinusoidal in the load, currents from the supply are very different between SE and BTL configurations. In an SE application the current waveform is a half-wave rectified shape whereas in BTL it is a full-wave rectified waveform. This means RMS conversion factors are different. Keep in mind that for most of the waveform both the push and pull transistors are not on at the same time, which supports the fact that each amplifier in the BTL device only draws current from the supply for half the waveform. The following equations are the basis for calculating amplifier efficiency.

rms

SUP

VDDIDDrms

VDD2V

Efficiency

SUP

Efficiency of a BTL Configuration

PLR

1ń2

(3)

Where:

(4)

PL+

VLrms

T able 1 employs equation 4 to calculate efficiencies for four different output power levels. Note that the efficiency of the amplifier is quite low for lower power levels and rises sharply as power to the load is increased resulting in a nearly flat internal power dissipation over the normal operating range. Note that the internal dissipation at full output power is less than in the half power range. Calculating the efficiency for a specific system is the key to proper power supply design. For a stereo 1-W audio system with 8-Ω loads and a 5-V supply , the maximum draw on the power supply is almost 3.25 W.

Table 1. Efficiency Vs Output Power in 5-V 8-Ω BTL Systems

OUTPUT POWER

(W)

EFFICIENCY

(%)

PEAK-TO-PEAK

VOLTAGE

(V)

INTERNAL

DISSIPATION

(W)

0.25 31.4 2.00 0.55

0.50 44.4 2.83 0.62

1.00 62.8 4.00 0.59

1.25 70.2 4.47

†

0.53

†

High peak voltages cause the THD to increase.

A final point to remember about linear amplifiers (either SE or BTL) is how to manipulate the terms in the efficiency equation to utmost advantage when possible. Note that in equation 4, VDD is in the denominator. This indicates that as VDD goes down, efficiency goes up.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

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APPLICATION INFORMATION

For example, if the 5-V supply is replaced with a 3.3-V supply (TP A0102 has a maximum recommended V

of 5.5 V) in the calculations of T able 1, then ef ficiency at 0.5 W would rise from 44% to 67% and internal power dissipation would fall from 0.62 W to 0.25 W at 5 V. Then for a stereo 0.5-W system from a 3.3-V supply, the maximum draw would only be 1.5 W as compared to 2.24 W from 5 V . In other words, use the efficiency analysis to chose the correct supply voltage and speaker impedance for the application.

selection of components

Figure 62 and Figure 63 are a schematic diagrams of a typical notebook computer application circuits.

Right

MUX

RLINEIN RHPIN

Left

MUX

LHPIN

LLINEIN

Bias, Mute, Shutdown,

and SE/BTL

MUX Control

–

RBYPASS

MUTE IN MUTE OUT SHUTDOWN

LBYPASS

ROUT+

ROUT–

LOUT+

LOUT–

SE/BTL

HP/LINE

System Control

100 kΩ

OUTR

OUTL

1 kΩ

0.1 µF

Figure 62. TPA0102 Minimum Configuration Application Circuit

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

Right

MUX

RLINEIN

RHPIN

Left

MUX

LHPIN

LLINEIN

Bias, Mute, Shutdown,

and SE/BTL

MUX Control

–

RBYPASS

MUTE IN MUTE OUT SHUTDOWN

LBYPASS

ROUT+ ROUT–

LOUT+

LOUT–

SE/BTL

HP/LINE

IRLINE

FRLINE

System Control

ILLINE

FLLINE

100 kΩ

OUTR

OUTL

1 kΩ

IRHP

FRHP

See Note A

ILHP

FLHP

0.1 µF

NOTE A: This connection is for ultralow current in shutdown mode.

Figure 63. TPA0102 Full Configuration Application Circuit

gain setting resistors, RF and R

The gain for each audio input of the TP A0102 is set by resistors RF and RI according to equation 5 for BTL mode.

(5)

BTL Gain+*

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

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APPLICATION INFORMATION

gain setting resistors, RF and RI (continued)

BTL mode operation brings about the factor 2 in the gain equation due to the inverting amplifier mirroring the voltage swing across the load. Given that the TPA0102 is a MOS amplifier, the input impedance is very high, consequently input leakage currents are not generally a concern although noise in the circuit increases as the value of RF increases. In addition, a certain range of RF values are required for proper startup operation of the amplifier. Taken together it is recommended that the effective impedance seen by the inverting node of the amplifier be set between 5 kΩ and 20 kΩ. The effective impedance is calculated in equation 6.

(6)

Effective Impedance

FRI

RF)

As an example consider an input resistance of 10 kΩ and a feedback resistor of 50 kΩ. The BTL gain of the amplifier would be –10 and the effective impedance at the inverting terminal would be 8.3 kΩ, which is well within the recommended range.

For high performance applications metal film resistors are recommended because they tend to have lower noise levels than carbon resistors. For values of RF above 50 kΩ the amplifier tends to become unstable due to a pole formed from RF and the inherent input capacitance of the MOS input structure. For this reason, a small compensation capacitor of approximately 5 pF should be placed in parallel with R

when RF is greater than

50 kΩ. This, in effect, creates a low pass filter network with the cutoff frequency defined in equation 7.

(7)

c(lowpass)

2pRFC

–3 dB

For example, if RF is 100 kΩ and Cf is 5 pF then fc is 318 kHz, which is well outside of the audio range.

input capacitor, C

In the typical application an input capacitor, CI, is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. In this case, CI and RI form a high-pass filter with the corner frequency determined in equation 8.

(8)

c(highpass)

2pRIC

–3 dB

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

input capacitor, CI (continued)

The value of CI is important to consider as it directly affects the bass (low frequency) performance of the circuit. Consider the example where RI is 10 kΩ and the specification calls for a flat bass response down to 40 Hz. Equation 8 is reconfigured as equation 9.

(9)

2pRIf

In this example, CI is 0.40 µF so one would likely choose a value in the range of 0.47 µF to 1 µF. A further consideration for this capacitor is the leakage path from the input source through the input network (RI, CI) and the feedback resistor (RF) to the load. This leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most applications as the dc level there is held at V

/2, which is likely higher

than the source dc level. Please note that it is important to confirm the capacitor polarity in the application.

power supply decoupling, C

The TPA0102 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is achieved by using two capacitors of different types that target different types of noise on the power supply leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance (ESR) ceramic capacitor, typically 0.1 µF placed as close as possible to the device V

lead works best. For filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF or greater placed near the audio power amplifier is recommended.

midrail bypass capacitor, C

The midrail bypass capacitor, CB, serves several important functions. During startup or recovery from shutdown mode, CB determines the rate at which the amplifier starts up. The second function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This noise is from the midrail generation circuit internal to the amplifier. The capacitor is fed from a 25-kΩ source inside the amplifier . T o keep the start-up pop as low as possible, the relationship shown in equation 10 should be maintained.

(10)

25 kΩ

CIR

As an example, consider a circuit where CB is 0.1 µF, CI is 0.22 µF and RI is 10 kΩ. Inserting these values into the equation 10 we get 400 ≤ 454 which satisfies the rule. Bypass capacitor, CB, values of 0.1 µF to 1 µF ceramic or tantalum low-ESR capacitors are recommended for the best THD and noise performance.

In Figure 63, the full feature configuration, two bypass capacitors are used. This provides the maximum separation between right and left drive circuits. When absolute minimum cost and/or component space is required, one bypass capacitor can be used as shown in Figure 62. It is critical that terminals 6 and 19 be tied together in this configuration.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

single-ended operation

In SE mode (see Figure 59 and Figure 60), the load is driven from the primary amplifier output for each channel (OUT+, terminals 22 and 3).

In SE mode the gain is set by the RF and RI resistors and is shown in equation 1 1. Since the inverting amplifier is not used to mirror the voltage swing on the load, the factor of 2, from equation 5, is not included.

(11)

SE Gain

The output coupling capacitor required in single-supply SE mode also places additional constraints on the selection of other components in the amplifier circuit. The rules described earlier still hold with the addition of the following relationship:

(12)

25 kΩ

CIR

RLC

output coupling capacitor, C

In the typical single-supply SE configuration, an output coupling capacitor (C

) is required to block the dc bias at the output of the amplifier thus preventing dc currents in the load. As with the input coupling capacitor, the output coupling capacitor and impedance of the load form a high-pass filter governed by equation 13.

(13)

c(high)

2pRLC

–3 dB

The main disadvantage, from a performance standpoint, is the load impedances are typically small, which drives the low-frequency corner higher degrading the bass response. Large values of C

are required to pass low frequencies into the load. Consider the example where a CC of 330 µF is chosen and loads vary from 4 Ω, 8 Ω, 32 Ω, to 47 kΩ. Table 2 summarizes the frequency response characteristics of each configuration.

Table 2. Common Load Impedances Vs Low Frequency Output Characteristics in SE Mode

LOWEST FREQUENCY

4 Ω 330 µF 120 Hz 8 Ω 330 µF 60 Hz

32 Ω 330 µF

15 Hz

47,000 Ω 330 µF 0.01 Hz

As Table 2 indicates, most of the bass response is attenuated into a 4-Ω load, an 8-Ω load is adequate, headphone response is good, and drive into line level inputs (a home stereo for example) is exceptional.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

SE/BTL

operation

The ability of the TP A0102 to easily switch between BTL and SE modes is one of its most important cost saving features. This feature eliminates the requirement for an additional headphone amplifier in applications where internal stereo speakers are driven in BTL mode but external headphone or speakers must be accommodated. Internal to the TPA0102, two separate amplifiers drive OUT+ and OUT–. The SE/BTL input (terminal 14) controls the operation of the follower amplifier that drives LOUT– and ROUT– (terminals 10 and 15). When SE/BTL

is held low, the amplifier is on and the TP A0102 is in the BTL mode. When SE/BTL is held high, the OUT– amplifiers are in a high output impedance state, which configures the TPA0102 as an SE driver from LOUT+ and ROUT+ (terminals 3 and 22). IDD is reduced by approximately one-half in SE mode. Control of the SE/BTL input can be from a logic-level CMOS source or, more typically, from a resistor divider network as shown in Figure 64.

MUX

RLINE IN

RHP IN

–

Bypass

SE/BTL

HP/LINE

100 kΩ

OUTR

1 kΩ

–

ROUT–

ROUT+ 22

Left

Channel

0.1 µF

Figure 64. TPA0102 Resistor Divider Network Circuit

Using a readily available 1/8-in. (3.5 mm) stereo headphone jack, the control switch is closed when no plug is inserted. When closed the 100-kΩ/1-kΩ divider pulls the SE/BTL

input low. When a plug is inserted, the 1-kΩ resistor is disconnected and the SE/BTL input is pulled high. When the input goes high, the OUT– amplifier is shutdown causing the speaker to mute (virtually open-circuits the speaker). The OUT+ amplifier then drives through the output capacitor (CO) into the headphone jack.

As shown in the full feature application (Figure 63), the input MUX control can be tied to the SE/BTL input. The benefits of doing this are described in the following input MUX operation section.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

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APPLICATION INFORMATION

Input MUX operation

Working in concert with the SE/BTL feature, the HP/LINE MUX feature gives the audio designer the flexibility of a multichip design in a single IC (see Figure 65). The primary function of the MUX is to allow different gain settings for BTL versus SE mode. Speakers typically require approximately a factor of 10 more gain for similar volume listening levels as compared to headphones. To achieve headphone and speaker listening parity, the resistor values would need to be set as follows:

(14)

SE Gain

(HP)

F(HP)

I(HP)

If, for example R

I(HP)

= 20 kΩ and R

F(HP)

= 20 kΩ then SE Gain

(HP)

= –1

(15)

BTL Gain

(LINE)

F(LINE)

I(LINE)

If, for example R

I(LINE)

= 20 kΩ and R

F(LINE)

= 100 kΩ then BTL Gain

(LINE)

= –10

ROUT+

ROUT–

IRLINE

IRHP

FRHP

MUX

RLINE IN

RHP IN

SE/BTL

HP/LINE

–

Left Channel

Right Channel

MID

FRLINE

0.1 µF

Figure 65. TPA0102 Example Input MUX Circuit

Another advantage of using the MUX feature is setting the gain of the headphone channel to –1. This provides the optimum distortion performance into the headphones where clear sound is more important. Refer to the SE/BTL operation section for a description of the headphone jack control circuit.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

mute and shutdown modes

The TP A0102 employs both a mute and a shutdown mode of operation designed to reduce supply current, IDD, to the absolute minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN input terminal should be held low during normal operation when the amplifier is in use. Pulling SHUTDOWN high causes the outputs to mute and the amplifier to enter a low-current state, IDD < 1 µA. SHUTDOWN or MUTE IN should never be left unconnected because amplifier operation would be unpredictable. Mute mode alone reduces I

< 1 mA.

Table 3. Shutdown and Mute Mode Functions

INPUTS

†

OUTPUT

AMPLIFIER STATE

SE/BTL

HP/LINE

MUTE IN SHUTDOWN MUTE OUT

INPUT OUTPUT

Low Low Low Low Low L/R Line BTL

X X — High — X Mute X X High — High X Mute

Low High Low Low Low L/R HP BTL

High Low Low Low Low L/R Line SE High High Low Low Low L/R HP SE

†

Inputs should never be left unconnected.

X = do not care

using low-ESR capacitors

Low-ESR capacitors are recommended throughout this applications section. A real (as opposed to ideal) capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this resistance the more the real capacitor behaves like an ideal capacitor.

5-V versus 3.3-V operation

The TP A0102 operates over a supply range of 3 V to 5.5 V. This data sheet provides full specifications for 5-V and 3.3-V operation, as these are considered to be the two most common standard voltages. There are no special considerations for 3.3-V versus 5-V operation as far as supply bypassing, gain setting, or stability goes. For 3.3-V operation, supply current is reduced from 19 mA (typical) to 13 mA (typical). The most important consideration is that of output power. Each amplifier in TPA0102 can produce a maximum voltage swing of V

– 1 V. This means, for 3.3-V operation, clipping starts to occur when V

O(PP)

= 2.3 V as opposed to

O(PP)

= 4 V at 5 V . The reduced voltage swing subsequently reduces maximum output power into an 8-Ω load

before distortion becomes significant. Operation from 3.3-V supplies, as can be shown from the efficiency formula in equation 4, consumes

approximately two-thirds the supply power for a given output-power level than operation from 5-V supplies. When the application demands less than 500 mW, 3.3-V operation should be strongly considered, especially in battery-powered applications.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

headroom and thermal considerations

Linear power amplifiers dissipate a significant amount of heat in the package under normal operating conditions. A typical music CD requires 12 dB to 15 dB of dynamic headroom to pass the loudest portions without distortion as compared with the average power output. From the TPA0102 data sheet, one can see that when the TPA0102 is operating from a 5-V supply into a 4-Ω speaker that 1.5 W peaks are available. Converting watts to dB:

PdB+

10Log

ref

10Log

1.5 1

1.76 dB

Subtracting the headroom restriction to obtain the average listening level without distortion yields:

1.76 dB*15 dB

13.24 dB(15 dB headroom

)

1.76 dB*12 dB

10.24 dB(12 dB headroom

)

1.76 dB*9dB

7.24 dB(9 dB headroom

)

1.76 dB*6dB

4.24 dB(6 dB headroom

)

1.76 dB*3dB

1.24 dB(3 dB headroom

)

Converting dB back into watts:

PdBń10

ref

47 mW (15 dB headroom)

94 mW (12 dB headroom)

188 mW (9 dB headroom)

376 mW (6 dB headroom)

752 mW (3 dB headroom)

This is valuable information to consider when attempting to estimate the heat dissipation requirements for the amplifier system. Comparing the absolute worst case, which is 1.5 W of continuous power output with 0 dB of headroom, against 12 dB and 15 dB applications drastically affects maximum ambient temperature ratings for the system. Using the power dissipation curves for a 5-V, 4-Ω system, the internal dissipation in the TPA0102 and maximum ambient temperatures is shown in Table 4.

Table 4. TPA0102 Power Rating, 5-V, 4-Ω, Stereo

PEAK OUTPUT POWER

(W)

AVERAGE OUTPUT POWER

POWER DISSIPATION

(W/Channel)

MAXIMUM AMBIENT

TEMPERATURE

1.5 1.5 W 1.35 28°C

1.5 752 mW (3 dB) 1.3 33°C

1.5 376 mW (6 dB) 0.9 69°C

1.5 188 mW (9 dB) 0.7 87°C

1.5 94 mW (12 dB) 0.55 100°C

1.5 47 mW (15 dB) 0.4 114°C

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

APPLICATION INFORMATION

headroom and thermal considerations (continued)

DISSIPATION RATING TABLE

PACKAGE

TA ≤ 25°C

DERATING FACTOR TA = 70°C TA = 85°C

PWP

†

2.7 W

21.8 mW/°C

1.7 W

1.4 W

PWP

‡

2.8 W

22.1 mW/°C 1.8 W 1.4 W

†

This parameter is measured with the recommended copper heat sink pattern on a 1-layer PCB, 4 in2 5-in × 5-in PCB, 1 oz. copper, 2-in × 2-in coverage.

‡

This parameter is measured with the recommended copper heat sink pattern on an 8-layer PCB, 6.9 in2 1.5-in × 2-in PCB, 1 oz. copper with layers 1, 2, 4, 5, 7, and 8 at 5% coverage (0.9 in2) and layers 3 and 6 at 100% coverage (6 in2).

The maximum ambient temperature depends on the heatsinking ability of the PCB system. Using the 0 CFM and 300 CFM data from the dissipation rating table, the derating factor for the PWP package with 6.9 in

copper area on a multilayer PCB is 22 mW/°C and 54 mW/°C respectively. Converting this to ΘJA:

Derating

0.022

45°CńW

To calculate maximum ambient temperatures, first consider that the numbers from the dissipation graphs are per channel so the dissipated heat needs to be doubled for two channel operation. Given Θ

, the maximum allowable junction temperature, and the total internal dissipation, the maximum ambient temperature can be calculated with the following equation. The maximum recommended junction temperature for the TP A0102 is 150 °C. The internal dissipation figures are taken from the Power Dissipation vs Output Power graphs.

TAMax+TJMax

150*45(0.4 2)+

114°C(15 dB headroom, 0 CFM

)

NOTE:

Internal dissipation of 0.4 W is estimated for a 1.5-W system with 15 dB headroom per channel.

Table 4 shows that for most applications no airflow is required to keep junction temperatures in the specified range. The TP A0102 is designed with thermal protection that turns the device off when the junction temperature surpasses 150°C to prevent damage to the IC. Table 4 was calculated for maximum listening volume without distortion. When the output level is reduced the numbers in the table change significantly. Also, using 8-Ω speakers dramatically increases the thermal performance by increasing amplifier efficiency.

TPA0102

1.5-W STEREO AUDIO POWER AMPLIFIER

SLOS166E – MARCH 1997 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

PWP (R-PDSO-G**) PowerPAD PLASTIC SMALL-OUTLINE

2820

6,40

6,60

1614

5,10

4,904,90

5,10

4073225/F 10/98

0,50

0,75

0,25

0,15 NOM

Thermal Pad (See Note D)

Gage Plane

7,70

7,90

9,60

9,80

6,60 6,20

0,19

4,50 4,30

0,15

0,30

1,20 MAX

PINS **

DIM

A MIN

A MAX

0,05

Seating Plane

0,65

0,10

0°–8°

20 PINS SHOWN

NOTES: A. All linear dimensions are in millimeters.

B. This drawing is subject to change without notice. C. Body dimensions do not include mold flash or protrusions. D. The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane.

This pad is electrically and thermally connected to the backside of the die and possibly selected leads.

E. Falls within JEDEC MO-153

For the latest package information, go to http://www.ti.com/sc/docs/package/pkg_info.htm PowerPAD is a trademark of Texas Instruments Incorporated.

IMPORTANT NOTICE

T exas Instruments and its subsidiaries (TI) reserve the right to make changes to their products or to discontinue any product or service without notice, and advise customers to obtain the latest version of relevant information to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied at the time of order acknowledgement, including those pertaining to warranty, patent infringement, and limitation of liability.

TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in accordance with TI’s standard warranty. Testing and other quality control techniques are utilized to the extent TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed, except those mandated by government requirements.

CERT AIN APPLICATIONS USING SEMICONDUCTOR PRODUCTS MAY INVOLVE POTENTIAL RISKS OF DEATH, PERSONAL INJURY, OR SEVERE PROPERTY OR ENVIRONMENTAL DAMAGE (“CRITICAL APPLICATIONS”). TI SEMICONDUCTOR PRODUCTS ARE NOT DESIGNED, AUTHORIZED, OR WARRANTED TO BE SUITABLE FOR USE IN LIFE-SUPPORT DEVICES OR SYSTEMS OR OTHER CRITICAL APPLICATIONS. INCLUSION OF TI PRODUCTS IN SUCH APPLICA TIONS IS UNDERSTOOD T O BE FULLY AT THE CUSTOMER’S RISK.

In order to minimize risks associated with the customer’s applications, adequate design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards.

TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other intellectual property right of TI covering or relating to any combination, machine, or process in which such semiconductor products or services might be or are used. TI’s publication of information regarding any third party’s products or services does not constitute TI’s approval, warranty or endorsement thereof.

Datasheet TPA0102PWPR, TPA0102PWPLE, TPA0102PWP, TPA0102EVM Datasheet (Texas Instruments)

Specifications and Main Features

Frequently Asked Questions

User Manual