Texas Instruments TPA005D14DCAR, TPA005D14DCA, TPA005D14EVM Datasheet

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TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

Choose TPA2000D2 For Upgrade

Extremely Efficient Class-D Stereo Operation

Drives L and R Channels, Plus Stereo Headphones

2-W BTL Output Into 4 Ω

5-W Peak Music Power

Fully Specified for 5-V Operation

Low Quiescent Current

Shutdown Control . . . 0.2 µA

Class-AB Headphone Amplifier

Thermally-Enhanced PowerP AD Surface Mount Packaging

Thermal, Over-Current, and Under-V oltage Protection

description

The TPA005D14 is a monolithic power IC stereo audio amplifier that operates in extremely efficient Class-D operation, using the high switching speed of power DMOS transistors to replicate the analog input signal through high-frequency switching of the output stage. This allows the TPA005D14 to be configured as a bridge-tied load (BTL) amplifier capable of delivering up to 2 W of continuous average power into a 4-Ω load at 0.4% THD+N from a 5-V power supply in the high-fidelity audio frequency range (20 Hz to 20 kHz). A BTL configuration eliminates the need for external coupling capacitors on the output. Included is a Class-AB headphone amplifier with interface logic to select between the two modes of operation. Only one amplifier is active at any given time, and the other is in power-saving sleep mode. Also, a chip-level shutdown control is provided to limit total quiescent current to 0.2 µA, making the device ideal for battery-powered applications.

A full range of protection circuitry is included to increase device reliability: thermal, over-current, and under-voltage shutdown, with two status feedback terminals for use when any error condition is encountered.

The high switching frequency of the TP A005D14 allows the output filter to consist of three small capacitors and two small inductors per channel. The high switching frequency also allows for good THD+N performance.

The TPA005D14 is offered in the thermally enhanced 48-pin PowerPAD TSSOP surface-mount package (designator DCA).

PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters.

Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.

PowerPAD is a trademark of Texas Instruments Incorporated.

SHUTDOWN

MUTE

MODE

LINN LINP

LCOMP

AGND

LPV

LOUTP LOUTP

PGND

PGND LOUTN LOUTN

LPV

HPDL

HPLOUT

HPLIN

AGND

VCP

CP3 CP2

COSC AGND AGND RINN RINP RCOMP FAULT0 FAULT1 RPV

ROUTP ROUTP PGND PGND ROUTN ROUTN RPV

HPDR HPROUT HPRIN V2P5 PV

PGND CP4 CP1

1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24

48 47 46 45 44 43 42 41 40 39 38 37 36 35 34 33 32 31 30 29 28 27 26 25

DCA PACKAGE

(TOP VIEW)

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

Template Release Date: 7–11–94

POST OFFICE BOX 655303 DALLAS, TEXAS 75265

•

LINP

RAMP

GENERATOR

GATE

DRIVE

LPV

GATE

DRIVE

LPV

GATE

DRIVE

RPV

GATE

DRIVE

RPV

OVER-I

DETECT

THERMAL

DETECT

VCP-UVLO

DETECT

TRIPLER

CHARGE PUMP

CONTROL and

STARTUP

LOGIC

GENERATOR

LINN

LCOMP

COSC

RCOMP

RINP RINN

RPV

AGND

LPV

ROUTP

ROUTN

VCP

CP4

CP3

CP2

CP1

LOUTP

LOUTN

FAULT0

FAULT1

SHUTDOWN MODE MUTE

V2P5

HPLIN

HPLOUT

HPROUT

HPRIN

LPV

RPV

PGND

VCP PV

10 kΩ10 kΩ

1.5 V

10 kΩ10 kΩ

1.5 V

DEPOP

HPDL HPDR

LPV

RPV

NOTE A: LPVDD, RPVDD, VDD, and PVDD are externally connected. AGND and PGND are externally connected.

schematic

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

Terminal Functions

TERMINAL

NAME NO.

DESCRIPTION

AGND

7, 20,

46, 47

Analog ground for headphone and Class-D analog sections

COSC 48 Capacitor I/O for ramp generator. Adjust the capacitor size to change the switching frequency. CP1 25 First diode node for charge pump CP2 24 First inverter switching node for charge pump CP3 23 Second diode node for charge pump CP4 26 Second inverter switching node for charge pump FAULT0 42 Logic level fault0 output signal. Lower order bit of the two fault signals with open drain output. FAULT1 41 Logic level fault1 output signal. Higher order bit of the two fault signals with open drain output. HPDL 17 Depop control for left headphone HPDR 32 Depop control for right headphone HPLIN 19 Headphone amplifier left input HPLOUT 18 Headphone amplifier left output HPRIN 30 Headphone amplifier right input HPROUT 31 Headphone amplifier right output LCOMP 6 Compensation capacitor terminal for left-channel Class-D amplifier LINN 4 Class-D left-channel negative input LINP 5 Class-D left-channel positive input LOUTN 14, 15 Class-D amplifier left-channel negative output of H-bridge LOUTP 10, 11 Class-D amplifier left-channel positive output of H-bridge LPV

9, 16 Class-D amplifier left-channel power supply

MODE 3

Logic-level mode input signal. When MODE is held low, the main Class-D amplifier is active. When MODE is held high, the head phone amplifier is active.

MUTE

Active-low logic-level mute input signal. When MUTE is held low, the selected amplifier is muted. When MUTE is held high, the device operates normally. When the Class-D amplifier is muted, the low-side output transistors are

turned on, shorting the load to ground. PGND 12, 13 Power ground for left-channel H–bridge only PGND 27 Power ground for charge pump only PGND 36, 37 Power ground for right-channel H-bridge only PV

21, 28 VDD supply for charge-pump and gate-drive circuitry RCOMP 43 Compensation capacitor terminal for right-channel Class-D amplifier RINN 45 Class-D right-channel negative input RINP 44 Class-D right-channel positive input RPV

33, 40 Class-D amplifier right-channel power supply ROUTN 34, 35 Class-D amplifier right-channel negative output of H-bridge ROUTP 38, 39 Class-D amplifier right-channel positive output of H-bridge

SHUTDOWN

Active-low logic-level shutdown input signal. When SHUTDOWN is held low, the device goes into shutdown mode. When SHUTDOWN

is held at logic high, the device operates normally. V2P5 29 2.5-V internal reference bypass VCP 22 Storage capacitor terminal for charge pump

VDD bias supply for analog circuitry. This terminal needs to be well filtered to prevent degrading the device performance.

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

Class-D amplifier faults

Table 1. Class-D Amplifier Fault Table

FAULT 0†FAULT 1

†

DESCRIPTION

1 1 No fault. — The device is operating normally. 0 1 Charge pump under-voltage lock-out (VCP-UV) fault — All low-side transistors are turned on, shorting the load to

ground. Once the charge pump voltage is restored, normal operation resumes, but FAULT1 is still active. FAULT1 is cleared by cycling MUTE

, SHUTDOWN, or the power supply.

1 0 Over-current fault — The output transistors are all switched off. This causes the load to be in a high-impedance state.

This is a latched fault and is cleared by cycling MUTE

, SHUTDOWN, or the power supply.

0 0 Thermal fault — All the low-side transistors are turned on, shorting the load to ground. This is latched fault and is

cleared by cycling MUTE

, SHUTDOWN, or the power supply.

†

These logic levels assume a pullup to PVDD from the open-drain outputs.

headphone amplifier faults

The thermal fault remains active when the device is in head phone mode. This fault operates exactly the same as it does for the Class-D amplifier (see Table 1).

If LPVDD or RPV

drops below 4.5 V , the headphone is disabled by the under-voltage lockout circuitry . Once

LPVDD and RPVDD exceed 4.5 V, the headphone amplifier is re-enabled. No fault is reported to the user.

AVAILABLE OPTIONS

PACKAGED DEVICES

TSSOP

†

(DCA)

–40°C to 125°C TPA005D14DCA

†

The DCA package is available in left-ended tape and reel. T o order a taped and reeled part, add the suffix R to the part number (e.g., TPA005D14DCAR).

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

absolute maximum ratings over operating free-air temperature range, TC = 25°C (unless otherwise noted)

‡

Supply voltage, VDD (PVDD, LPVDD, RPVDD, VDD) 5.5 V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Input voltage, VI (SHUTDOWN, MUTE, MODE) –0.3 V to 5.8 V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Output current, IO (FAULT0, FAULT1), open drain terminated 1 mA. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Charge pump voltage, VCP PVDD + 15 V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Continuous H-bridge output current 2 A. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Pulsed H-Bridge output current, each output, I

max

(see Note 1) 5 A. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Continuous total power dissipation See Dissipation Ratings Table. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Operating virtual junction temperature range, TJ –40°C to 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Operating case temperature range, TC –40°C to 125°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Storage temperature range, T

stg

–40°C to 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds 260°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

†

Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.

NOTE 1: Pulse duration = 10 ms, duty cycle v 2%

DISSIPATION RATING TABLE

PACKAGE

TA ≤ 25°C

‡

POWER RATING

DERATING FACTOR

ABOVE TA = 25°C

TA = 70°C

POWER RATING

TA = 85°C

POWER RATING

TA = 125°C

POWER RATING

DCA 5.6 W 44.8 mW/°C 3.6 W 2.9 W 1.1 mW

‡

See the Texas Instruments document,

PowerPAD Thermally Enhanced Package Application Report

(literature number SLMA002), for more information on the PowerP AD package. The thermal data was measured on a PCB layout based on the information in the section entitled

T exas Instruments Recommended Board for PowerP AD

on page 33 of the before mentioned

document.

recommended operating conditions

MIN NOM MAX UNIT

Supply voltage, PVDD, LPVDD, RPVDD, V

4.5 5.5 V High-level input voltage, VIH (MUTE, MODE, SHUTDOWN) 4.25 V Low-level input voltage, VIL (MUTE, MODE, SHUTDOWN) 0.75 V Audio inputs, LINN, LINP, RINN, RINP, HPLIN, HPRIN, differential input voltage 1 V

RMS

PWM frequency 150 450 kHZ

electrical characteristics, Class-D amplifier, VDD = PVDD = LPVDD = RPVDD = 5 V, RL = 4 Ω, T

= 25°C, See Figure 1 (unless otherwise noted)

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

Power supply rejection ratio VDD = PVDD = LPVDD = RPVDD = 4.5 V to 5.5 V –40 dB

Supply current No output filter connected 25 35 mA IDD(MUTE) Supply current, mute mode MUTE = 0 V 3.9 10 mA IDD(SD) Supply current, shutdown mode SHUTDOWN = 0 V 0.2 10 µA I

High-level input current VIH = 5.3 V 1 µA I

Low-level input current VIL = –0.3 V –1 µA

DS(on)

Total static drain-to-source on-state

resistance (low-side plus high-side

FETs)

ID = 0.5 A 700 900 mΩ

DS(on)

Matching, high-side to high-side,

low-side to low-side, same channel

ID = 0.5 A 95% 98%

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

operating characteristics, Class-D amplifier, VDD = PVDD = LPVDD = RPVDD = 5 V, RL = 4 Ω, T

= 25°C, See Figure 1 (unless otherwise noted)

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

RMS output power

f = 1 kHz, THD = 0.5%, Per channel

2 W

THD+N Total harmonic distortion plus noise PO = 1 W, f = 1 kHz 0.2%

Efficiency PO = 1 W, RL = 8 Ω 80%

Gain 20 dB Left/right channel gain matching 95% 99% Noise floor –55 dBV Dynamic range 70 dB Crosstalk f = 1 kHz –55 dB Frequency response bandwidth, post output filter, –3 dB 20 20000 Hz

Maximum output power bandwidth 20 kHz

Input impedance 10 kΩ

electrical characteristics, headphone amplifier, PVDD = LPVDD= RPVDD = 5 V , RL = 32 Ω, TA = 25°C, See Figure 3 (unless otherwise noted)

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

Power supply rejection ratio PVDD = 4.5 V to 5.5 V,

AV = –1 V/V

–60 dB

Uncompensated gain range –1 –10 V/V

Supply current 8 10 mA IDD(MUTE) Supply current, mute mode 1.5 2 mA IDD(SD) Supply current, shutdown mode 0.2 10 µA I

Input bias current 30 µA

operating characteristics, headphone amplifier, PVDD = LPVDD = RPVDD = 5 V , RL = 32 Ω, TA = 25°C, See Figure 3 (unless otherwise noted)

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

Output power

THD = 0.5%, f = 1 kHz, AV = –10V/V

50 mW

Supply voltage rejection ratio f = 1 kHz –60 dB Noise floor –84 dBV Dynamic range 90 dB Crosstalk f = 1 kHz –38 dB Frequency response bandwidth, post output filter, –3 dB 20 20000 Hz

Maximum output power bandwidth 20 kHz

Input impedance >1 MΩ

thermal shutdown

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

Thermal shutdown temperature 165 °C

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

PARAMETER MEASUREMENT INFORMATION

LINP

LINN

LCOMP

COSC

RCOMP

RINP

RINN

RPV

AGND (see Note A)

LPV

SHUTDOWN

V2P5

HPLIN

HPLOUT

HPROUT

HPRIN

PGND (see Note A)

15 µH

0.22 µF

0.22 µF 1 µF

4 Ω

5 V

1 µF

Balanced

Differential

Input Signal

470 pF

1 µF

Balanced

Differential

Input Signal

5 V

CP1

CP2 CP3

CP4

VCP

FAULT0 FAULT1

MODE

MUTE

1 µF

LOUTP

LOUTN

15 µH

0.22 µF

0.22 µF 1 µF

4 Ω

ROUTP

ROUTN

47 nF

0.1 µF

1 2 3

9,16

33,40

7,20,46,47

12,13,27,36,37

21, 28

14,15

10,11

18 31

24 23

26 22

34,35

38,39

HPDL

HPDR

Figure 1. 5-V, 4-Ω Test Circuit, Class-D Amplifier

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

PARAMETER MEASUREMENT INFORMATION

LINP

LINN

LCOMP

COSC

RCOMP

RINP

RINN

RPV

AGND

LPV

SHUTDOWN

HPDR

V2P5

HPLIN

HPLOUT

HPROUT

HPRIN

PGND

5 V

470 pF

5 V

CP1

CP2

CP3

CP4

VCP

FAULT0 FAULT1

MODE

MUTE

1 µF

LOUTP

LOUTN

ROUTP

ROUTN

47 nF

0.1 µF

1 2 3

9,16

33,40

7,20,46,47

12,13,27,36,37

21, 28

14,15

10,11

18 31 32

26 22

34,35 38,39

5 V

5 V 5 V

Left SE

HP Input

HPLOUT

100 kΩ

0.1 µF

Right SE

HP Input

100 kΩ

0.1 µF

100

kΩ

32 Ω

220 µF

32 Ω

5 V

HPROUT

47 nF

HPDL

Figure 2. Headphone Test Circuit

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

PARAMETER MEASUREMENT INFORMATION

LINP

LINN

LCOMP

COSC

RCOMP

RINP

RINN

RPV

AGND

LPV

SHUTDOWN

V2P5

HPLOUT

HPROUT

PGND

15 µH

0.22 µF

0.22 µF 1 µF

4 Ω

5 V

1 µF

Left Class-D Balanced

Differential Input

Signal

470 pF

1 µF

HPDR

HPDL

CP1

CP2

VCP

FAULT0 FAULT1

MODE

MUTE

1 µF

LOUTP

LOUTN

15 µH

0.22 µF

0.22 µF 1 µF

4 Ω

ROUTP

ROUTN

47 nF

0.1 µF

1 2 3

9,16

33,40

7,20,46,47

12,13,27,36,37

21, 28

14,15

10,11

29 8

18 31

32 17

34,35

38,39

5 V

HPLIN

HPRIN

Left SE

HP Input

HPLOUT

100 kΩ

0.1 µF

Right SE HP Input

100 kΩ

0.1 µF

100

kΩ

To System

Control

100 kΩ

1 µF1 µF

10 µF

Right Class-D Balanced

Differential Input

Signal

5 V

1 µF1 µF

10 µF

1 µF

100 kΩ

To System Control

1 µF

100 kΩ

5 V

MODE

1 kΩ1 kΩ

NOTE A: = power ground and = analog ground

HPROUT

220 µF 220 µF

5 V

CP3

CP4

47 nF

Figure 3. TPA032D04 Typical Configuration Application Circuit

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Table of Graphs

FIGURE

vs Switching frequency 4

IDDSupply current

vs Free-air temperature 5, 6

THD+N Total harmonic distortion plus noise

vs Frequency

7, 9, 11

12, 14, 15

THD+N

Total harmonic distortion lus noise

vs Output power 8, 10, 13 Gain and phase vs Frequency 16, 17 Crosstalk vs Frequency 18 Power dissipation vs Output power 19 Efficiency vs Output power 20

Figure 4

f – Frequency – kHz

100 200 300 400 500

SUPPLY CURRENT

SWITCHING FREQUENCY

– Supply Current – mA

With Output Filter

Without Output Filter

Class-D Amplifier

Figure 5

–50 –25 0 25 50 75 100 125 150

– Supply Current – mA

With Output Filter

Without Output Filter

SUPPLY CURRENT

FREE–AIR TEMPERATURE

TA – Free–Air Temperature – °C

Class-D Amplifier

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 6

5.5

6.0

6.5

7.0

7.5

8.0

8.5

9.0

9.5

10.0

–50 –25 0 25 50 75 100 125 150

– Supply Current – mA

SUPPLY CURRENT

FREE–AIR TEMPERATURE

TA – Free–Air Temperature – °C

Headphone Amplifier

Figure 7

TOTAL HARMONIC DISTORTION + NOISE

FREQUENCY

Class-D Amplifier VDD = 5 V RL = 8 Ω

0.1

0.01

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

20 100 1k 10k 30k

100 mW

1 W

500 mW

Figure 8

TOTAL HARMONIC DISTORTION + NOISE

OUTPUT POWER

0.1

0.02

THD+N –Total Harmonic Distortion + Noise – %

PO – Output Power – W

0.01 0.1 1 10

f = 20 kHz

f = 20 Hz

f = 1 kHz

Class-D Amplifier VDD = 5 V RL = 8 Ω

Figure 9

TOTAL HARMONIC DISTORTION + NOISE

FREQUENCY

Class-D Amplifier VDD = 5 V RL = 4 Ω

0.1

0.01

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

20 100 1k 10k 30k

1 W

500 mW

2 W

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 10

TOTAL HARMONIC DISTORTION + NOISE

OUTPUT POWER

0.1

0.04

THD+N –Total Harmonic Distortion + Noise – %

PO – Output Power – W

0.01 0.1 1 10

Class-D Amplifier VDD = 5 V RL = 4 Ω

f = 20 kHz

f = 1 kHz

f = 20 Hz

Figure 11

TOTAL HARMONIC DISTORTION + NOISE

FREQUENCY

0.1

0.006

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

20 100 1k 10k 20k

0.01

Headphone Amplifier CI = 10 µF RL = 32 Ω CO = 470 µF

AV = 10

AV = 5

AV = 1

Figure 12

TOTAL HARMONIC DISTORTION + NOISE

FREQUENCY

0.1

0.005

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

20 100 1k 10k 20

0.01

Headphone Amplifier VO = 1 V PO = 40 mW AV = 1 CI = 10 µF RI = RF = 10 kΩ CO = 470 µF

Figure 13

TOTAL HARMONIC DISTORTION + NOISE

OUTPUT POWER

0.1

0.005

THD+N –Total Harmonic Distortion + Noise – %

PO – Output Power – W

0.001 0.01 0.1 0.2

0.01

Headphone Amplifier VDD = 5 V AV = 1 CI = 10 µF RI = RF = 10 kΩ CO = 470 µF

f = 20 kHz

f = 1 kHz

f = 20 Hz

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

Figure 14

0.1

0.004

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

20 100 1k 10k 20k

0.01

VO = 1 V AV = 1 CI = 10 µF RI = RF = 50 kΩ CO = 470 µF RL = 10 kΩ

HEADPHONE AMPLIFIER

TOTAL HARMONIC DISTORTION + NOISE

FREQUENCY

Figure 15

0.1

0.004

THD+N –Total Harmonic Distortion + Noise – %

f – Frequency – Hz

20 100 1k 10k 20k

0.01

VO = 1 V CI = 10 µF RI = RF = 10 kΩ CO = 470 µF

AV = 10

AV = 5

AV = 1

HEADPHONE AMPLIFIER

TOTAL HARMONIC DISTORTION + NOISE

FREQUENCY

100

f – Frequency – Hz

1k 10k 30k

Gain – dBV

–60°

–90°

Phase – Degrees

VDD = 5 V PO = 2 W RL = 4 Ω

–30°

0°

30°

60°

90°

Gain

Phase

CLASS-D AMPLIFIER

GAIN and PHASE

FREQUENCY

Figure 16

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS240A – AUGUST 1999 – REVISED MARCH 2000

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

–6

–8

–10

100

f – Frequency – Hz

–5

–7

–9

1k 10k 30k

Gain – dBV

–120°

–180°

Phase – Degrees

–60°

0°

60°

120°

180°

–4

–2 –3

2 1 0

–1

VDD = 5 V PO = 40 mW AV = 1 CI = 10 µF RI = RF = 10 kΩ CO = 470 µF

Gain

Phase

HEADPHONE AMPLIFIER

GAIN and PHASE

FREQUENCY

Figure 17

Figure 18

Crosstalk – dB

f – Frequency – Hz

20 100 1k 10k 20k

–48

–60

–52

–56

–36

–40

–44

VDD = 5 V PO = 2 W RL = 4 Ω

CLASS-D AMPLIFIER

CROSSTALK

FREQUENCY

Figure 19

0.5

1.0

1.5

2.0

2.5

3.0

0 0.5 1.0 1.5 2.0 2.5

POWER DISSIPATION

OUTPUT POWER

PO – Output Power – W

Class-D Amplifier

Power Dissipation – W

RL = 4 Ω

RL = 8 Ω

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

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POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

TYPICAL CHARACTERISTICS

0 0.5 1.0 1.5 2.0 2.5

EFFICIENCY

OUTPUT POWER

PO – Output Power – W

Class-D Amplifier

Efficiency – %

RL = 4 Ω

RL = 8 Ω

Figure 20

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

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APPLICATION INFORMATION

input capacitor, C

In the typical application an input capacitor, CI, is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. In this case, CI and RIN, the TPA005D14’s input resistance forms a high-pass filter with the corner frequency determined in equation 1.

(1)

c(highpass)

2pZIC

–3 dB

ZI is nominally 10 kΩ

The value of CI is important to consider as it directly affects the bass (low frequency) performance of the circuit. Consider the example where the specification calls for a flat bass response down to 40 Hz. Equation 1 is reconfigured as equation 2.

(2)

2pZIf

In this example, CI is 0.40 µF so one would likely choose a value in the range of 0.47 µF to 1 µF . A low-leakage tantalum or ceramic capacitor is the best choice for the input capacitors. When polarized capacitors are used, the positive side of the capacitor should face the amplifier input as the dc level there is held at 1.5 V, which is likely higher than the source dc level. Please note that it is important to confirm the capacitor polarity in the application.

differential input

The TP A005D14 has differential inputs to minimize distortion at the input to the IC. Since these inputs nominally sit at 1.5 V, dc-blocking capacitors are required on each of the four input terminals. If the signal source is single-ended, optimal performance is achieved by treating the signal ground as a signal. In other words, reference the signal ground at the signal source, and run a trace to the dc-blocking capacitor which should be located physically close to the TP A005D14. If this is not feasible, it is still necessary to locally ground the unused input terminal through a dc-blocking capacitor.

power supply decoupling, C

The TPA005D14 is a high-performance Class-D CMOS audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is achieved by using two capacitors of different types that target different types of noise on the power supply leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-seriesresistance (ESR) ceramic capacitor, typically 0.1 µF placed as close as possible to the device’s various V

leads works best. For filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF or greater placed near the audio power amplifier is recommended.

The TP A005D14 has several different power supply terminals. This was done to isolate the noise resulting from high-current switching from the sensitive analog circuitry inside the IC.

TPA005D14

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APPLICATION INFORMATION

mute and shutdown modes

The TP A005D14 employs both a mute and a shutdown mode of operation designed to reduce supply current, IDD, to the absolute minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN input terminal should be held high during normal operation when the amplifier is in use. Pulling SHUTDOWN low causes the outputs to mute and the amplifier to enter a low-current state, IDD = 0.2 µA. Mute mode alone reduces I

to 10 mA.

using low-ESR capacitors

Low-ESR capacitors are recommended throughout this applications section. A real (as opposed to ideal) capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this resistance the more the real capacitor behaves like an ideal capacitor.

output filter components

The output inductors are key elements in the performance of the class-D audio amplifier system. It is important that these inductors have a high enough current rating and a relatively constant inductance over frequency and temperature. The current rating should be higher than the expected maximum current to avoid magnetically saturating the inductor. When saturation occurs, the inductor loses its functionality and looks like a short circuit to the PWM signal, which increases the harmonic distortion considerably.

A shielded inductor may be required if the class-D amplifier is placed in an EMI sensitive system; however, the switching frequency is low for EMI considerations and should not be an issue in most systems. The dc series resistance of the inductor should be low to minimize losses due to power dissipation in the inductor, which reduces the efficiency of the circuit.

Capacitors are important in attenuating the switching frequency and high frequency noise, and in supplying some of the current to the load. It is best to use capacitors with low equivalent-series-resistance (ESR). A low ESR means that less power is dissipated in the capacitor as it shunts the high-frequency signals. Placing these capacitors in parallel also parallels their ESR, effectively reducing the overall ESR value. The voltage rating is also important, and, as a rule of thumb, should be 2 to 3 times the maximum rms voltage expected to allow for high peak voltages and transient spikes. These output filter capacitors should be stable over temperature since large currents flow through them.

For 8-Ω loads, double the inductor value and halve the common-mode capacitors (i.e., 15 µH to 30 µH). For more information, see application report SLOA023,

Reducing and Eliminating the Class-D Output Filter

and

application report SLOA031,

Design Considerations for Class-D Audio Power Amplifiers

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

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APPLICATION INFORMATION

efficiency of class-D vs linear operation

Amplifier efficiency is defined as the ratio of output power delivered to the load to power drawn from the supply . In the efficiency equation below, PL is power across the load and P

SUP

is the supply power.

Efficiency+h

SUP

A high-efficiency amplifier has a number of advantages over one with lower efficiency . One of these advantages is a lower power requirement for a given output, which translates into less waste heat that must be removed from the device, smaller power supply required, and increased battery life.

Audio power amplifier systems have traditionally used linear amplifiers, which are well known for being inefficient. Class-D amplifiers were developed as a means to increase the efficiency of audio power amplifier systems.

A linear amplifier is designed to act as a variable resistor network between the power supply and the load. The transistors operate in their linear region and voltage that is dropped across the transistors (in their role as variable resistors) is lost as heat, particularly in the output transistors.

The output transistors of a class-D amplifier switch from full OFF to full ON (saturated) and then back again, spending very little time in the linear region in between. As a result, very little power is lost to heat because the transistors are not operated in their linear region. If the transistors have a low ON resistance, little voltage is dropped across them, further reducing losses. The ideal class-D amplifier is 100% efficient, which assumes that both the ON resistance (r

DS(ON)

) and the switching times of the output transistors are zero.

the ideal class-D amplifier

T o illustrate how the output transistors of a class-D amplifier operate, a half-bridge application is examined first (Figure 21).

OUT

–

Figure 21. Half-Bridge Class-D Output Stage

Figures 22 and 23 show the currents and voltages of the half-bridge circuit. When transistor M1 is on and M2 is off, the inductor current is approximately equal to the supply current. When M2 switches on and M1 switches off, the supply current drops to zero, but the inductor keeps the inductor current from dropping. The additional inductor current is flowing through M2 from ground. This means that V

(the voltage at the drain of M2, as shown in Figure 21) transitions between the supply voltage and slightly below ground. The inductor and capacitor form a low-pass filter, which makes the output current equal to the average of the inductor current. The low pass filter averages V

, which makes V

OUT

equal to the supply voltage multiplied by the duty cycle.

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APPLICATION INFORMATION

the ideal class-D amplifier (continued)

Control logic is used to adjust the output power, and both transistors are never on at the same time. If the output voltage is rising, M1 is on for a longer period of time than M2.

Supply Current

Time

M1 on M2 off

M1 off M2 on

M1 on M2 off

Output Current

Inductor Current

Current

Figure 22. Class-D Currents

OUT

Voltage

Time

M1 on M2 off

M1 off M2 on

M1 on M2 off

Figure 23. Class-D Voltages

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

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APPLICATION INFORMATION

the ideal class-D amplifier (continued)

Given these plots, the efficiency of the class-D device can be calculated and compared to an ideal linear amplifier device. In the derivation below, a sine wave of peak voltage (VP) is the output from an ideal class-D and linear amplifier and the efficiency is calculated.

L(rms)

CLASS-D LINEAR

L(rms)

PL+

AverageǒI

L(rms)

PL+

L(rms)

AverageǒI

SUP

VDD

AverageǒI

SUP

VDD

AverageǒI

VDDV

SUP

L(rms)

Efficiency+h

SUP

Efficiency+h

SUP

Efficiency+h+VDD

Efficiency+h+1 Efficiency+h

In the ideal efficiency equations, assume that VP = VDD, which is the maximum sine wave magnitude without clipping. Then, the highest efficiency that a linear amplifier can have without clipping is 78.5%. A class-D amplifier, however, can ideally have an efficiency of 100% at all power levels.

The derivation above applies to an H-bridge as well as a half-bridge. An H-bridge requires approximately twice the supply current but only requires half the supply voltage to achieve the same output power—factors that cancel in the efficiency calculation. The H-bridge circuit is shown in Figure 24.

OUT

–

Figure 24. H-Bridge Class-D Output Stage

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APPLICATION INFORMATION

losses in a real-world class-D amplifier

Losses make class-D amplifiers nonideal, and reduce the efficiency below 100%. These losses are due to the output transistors having a nonzero r

DS(on)

, and rise and fall times that are greater than zero.

The loss due to a nonzero r

DS(on)

is called conduction loss, and is the power lost in the output transistors at

nonswitching times, when the transistor is ON (saturated). Any R

DS(on)

above 0 Ω causes conduction loss. Figure 25 shows an H-bridge output circuit simplified for conduction loss analysis and can be used to determine new efficiencies with conduction losses included.

VDD = 5 V

4 Ω

0.35 Ω

DS(on)

DS(off)

DS(on)

5 MΩ

Figure 25. Output Transistor Simplification for Conduction Loss Calculation

The power supplied, P

SUP

, is determined to be the power output to the load plus the power lost in the transistors,

assuming that there are always two transistors on.

Efficiency+h

I2R

I22r

DS(on)

)

I2R

Efficiency+h

SUP

Efficiency+h

DS(on)

)

Efficiency+h+95%ǒat all output levels r

DS(on)

0.1, RL+

Efficiency+h+85%ǒat all output levels r

DS(on)

0.35, RL+

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

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APPLICATION INFORMATION

losses in a real-world class-D amplifier (continued)

Losses due to rise and fall times are called switching losses. A plot of the output, showing switching losses, is shown in Figure 26.

SWon

SWoff

Figure 26. Output Switching Losses

Rise and fall times are greater than zero for several reasons. One is that the output transistors cannot switch instantaneously because (assuming a MOSFET) the channel from drain to source requires a specific period of time to form. Another is that transistor gate-source capacitance and parasitic resistance in traces form RC time constants that also increase rise and fall times.

Switching losses are constant at all output power levels, which means that switching losses can be ignored at high power levels in most cases. At low power levels, however, switching losses must be taken into account when calculating efficiency. Switching losses are dominated by conduction losses at the high output powers, but should be considered at low powers. The switching losses are automatically taken into account if you consider the quiescent current with the output filter and load.

class-D effect on power supply

Efficiency calculations are an important factor for proper power supply design in amplifier systems. Table 2 shows class-D efficiency at a range of output power levels (per channel) with a 1-kHz sine wave input. The maximum power supply draw from a stereo 1-W per channel audio system with 8-Ω loads and a 5-V supply is almost 2.7 W. A similar linear amplifier such as the TP A005D14 has a maximum draw of 3.25 W under the same circumstances.

Table 2. Efficiency vs Output Power in 5-V 8-Ω H-Bridge Systems

Output Power (W) Efficiency (%) Peak Voltage (V) Internal Dissipation (W)

0.25 63.4 2 0.145

0.5 73 2.83 0.183

0.75 77.1 3.46 0.222 1 79.3 4 0.314

1.25 80.6 4.47

†

0.3

†

High peak voltages cause the THD to increase

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

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APPLICATION INFORMATION

class-D effect on power supply (continued)

There is a minor power supply savings with a class-D amplifier versus a linear amplifier when amplifying sine waves. The difference is much larger when the amplifier is used strictly for music. This is because music has much lower RMS output power levels, given the same peak output power (Figure 27); and although linear devices are relatively efficient at high RMS output levels, they are very inefficient at mid-to-low RMS power levels. The standard method of comparing the peak power to RMS power for a given signal is crest factor, whose equation is shown below. The lower RMS power for a set peak power results in a higher crest factor

Crest Factor

10 log

rms

Time

Power

RMS

Figure 27. Audio Signal Showing Peak and RMS Power

Figure 28 is a comparison of a 5-V class-D amplifier to a similar linear amplifier playing music that has a 13.76-dB crest factor. From the plot, the power supply draw from a stereo amplifier that is playing music with a 13.76 dB crest factor is 1.02 W, while a class-D amplifier draws 420 mW under the same conditions. This means that just under 2.5 times the power supply is required for a linear amplifier over a class-D amplifier.

600

500

300

200

100

400

1 1.5 2 2.5

Power Supplied (mW)

POWER SUPPLIED

PEAK OUTPUT VOLTAGE AND PEAK OUTPUT POWER

4 4.53

3.5

0.25 0.56 1 1.56 4 5.062.25

3.06

Peak Output Voltage (V)

Peak Output Power (W)

TPA0202

TPA005D14

Figure 28. Audio Signal Showing Peak and RMS Power (With Music Applied)

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

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APPLICATION INFORMATION

class-D effect on battery life

Battery operations for class-D amplifiers versus linear amplifiers have similar power supply savings results. The essential contributing factor to longer battery life is lower RMS supply current. Figure 29 compares the TPA005D14 supply current to the supply current of the TPA0202, a 2-W linear device, while playing music at different peak voltage levels.

400

350

250

200

150

300

1 1.5 2 2.5

Supply Current (mA rms)

SUPPLY CURRENTS

PEAK OUTPUT VOLTAGE AND PEAK OUTPUT POWER

3.5

100

0.25 0.56 1 1.56 42.25

3.06

Peak Output Voltage (V)

Peak Output Power (W)

TPA0202

TPA005D14

Figure 29. Supply Current vs Peak Output Voltage of TPA005D14 vs TPA0202 With Music Input

This plot shows that a linear amplifier has approximately three times more current draw at normal listening levels than a class-D amplifier. Thus, a class-D amplifier has approximately three times longer battery life at normal listening levels. If there is other circuitry in the system drawing supply current, that must also be taken into account when estimating battery life savings.

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

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APPLICATION INFORMATION

crest factor and thermal considerations

A typical music CD requires 12 dB to 15 dB of dynamic headroom to pass the loudest portions without distortion as compared with the average power output. From the TPA005D14 data sheet, one can see that when the TP A005D14 is operating from a 5-V supply into a 4-Ω speaker that 4 W peaks are available. Converting W atts to dB:

PdB+

10Log

ref

10Log

4 1

6dB

(3)

Subtracting the crest factor restriction to obtain the average listening level without distortion yields:

6.0 dB*15 dB

9dB(15 dB crest factor

)

6.0 dB*12 dB

6dB(12 dB crest factor

)

6.0 dB*9dB

3dB(9 dB crest factor

)

6.0 dB*6dB

0dB(6 dB crest factor

)

6.0 dB*3dB+3dB(3 dB crest factor

)

6.0 dB*18 dB

12 dB(15 dB crest factor

)

Converting dB back into watts:

PW+

PdBń10

ref

125 mW (15 dB crest factor)

250 mW (12 dB crest factor)

500 mW (9 dB crest factor)

1000 mW (6 dB crest factor)

2000 mW (3 dB crest factor)

(4)

63 mW (18 dB crest factor)

This is valuable information to consider when attempting to estimate the heat dissipation requirements for the amplifier system. Comparing the absolute worst case, which is 2 W of continuous power output with a 3 dB crest factor, against 12 dB and 15 dB applications drastically af fects maximum ambient temperature ratings for the system. Using the power dissipation curves for a 5-V, 4-Ω system, the internal dissipation in the TPA005D14 and maximum ambient temperatures is shown in Table 3.

TPA005D14 2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

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APPLICATION INFORMATION

crest factor and thermal considerations (continued)

Table 3. TPA005D14 Power Rating, 5-V, 4-Ω, Stereo

PEAK OUTPUT POWER AVERAGE OUTPUT POWER DISSIPA TION MAXIMUM AMBIENT

(W) POWER (W/Channel) TEMPERATURE

4 2 W (3 dB) 0.56 125°C 4 1000 mW (6 dB) 0.30 136°C

†

4 500 mW (9 dB) 0.23 139°C

†

4 250 mW (12 dB) 0.20 141°C

†

4 120 mW (15 dB) 0.14 143°C

†

4 63 mW (18 dB) 0.09 146°C

†

Case temperature (TC) is rated to 125°C maximum.

DISSIPATION RATING TABLE

PACKAGE

TA ≤ 25°C

DERATING FACTOR TA = 70°C TA = 85°C

DCA

5.6 W

44.8 mW/°C

3.5 W

2.9 W

The maximum ambient temperature depends on the heatsinking ability of the PCB system. Using the 0 CFM data from the dissipation rating table, the derating factor for the DCA package with 6.9 in2 of copper area on a multilayer PCB is 44.8 mW/°C. Converting this to ΘJA:

Derating

0.0448

22.3°CńW

(5)

To calculate maximum ambient temperatures, first consider that the numbers from the dissipation graphs are per channel so the dissipated heat needs to be doubled for two channel operation. Given ΘJA, the maximum allowable junction temperature, and the total internal dissipation, the maximum ambient temperature can be calculated with the following equation. The maximum recommended junction temperature for the TP A005D14 is 150 °C. The internal dissipation figures are taken from the Efficiency vs Output Power graphs.

Max+TJMax

JAPD

150*22.3(0.14 2)+

143°C(15 dB crest factor

)

150*22.3(0.56 2)+

125°C(3dB crest factor

)

(6)

NOTE:

Internal dissipation of 0.6 W is estimated for a 2-W system with a 15 dB crest factor per channel.

Table 3 shows that for some applications no airflow is required to keep junction temperatures in the specified range. The TPA005D14 is designed with thermal protection that turns the device off when the junction temperature surpasses 150°C to prevent damage to the IC. Table 3 was calculated for maximum listening volume without distortion. When the output level is reduced the numbers in the table change significantly . Also, using 8-Ω speakers dramatically increases the thermal performance by increasing amplifier efficiency.

TPA005D14

2-W STEREO CLASS-D AUDIO POWER AMPLIFIER

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THERMAL INFORMATION

The thermally enhanced DCA package is based on the 56-pin TSSOP, but includes a thermal pad (see Figure 30) to provide an effective thermal contact between the IC and the PWB.

Traditionally, surface mount and power have been mutually exclusive terms. A variety of scaled-down TO-220-type packages have leads formed as gull wings to make them applicable for surface-mount applications. These packages, however, have only two shortcomings: they do not address the very low profile requirements (<2 mm) of many of today’s advanced systems, and they do not offer a terminal-count high enough to accommodate increasing integration. On the other hand, traditional low-power surface-mount packages require power-dissipation derating that severely limits the usable range of many high-performance analog circuits.

The PowerP AD package (thermally enhanced TSSOP) combines fine-pitch surface-mount technology with thermal performance comparable to much larger power packages.

The PowerPAD package is designed to optimize the heat transfer to the PWB. Because of the very small size and limited mass of a TSSOP package, thermal enhancement is achieved by improving the thermal conduction paths that remove heat from the component. The thermal pad is formed using a patented lead-frame design and manufacturing technique to provide a direct connection to the heat-generating IC. When this pad is soldered or otherwise thermally coupled to an external heat dissipator, high power dissipation in the ultra-thin, fine-pitch, surface-mount package can be reliably achieved.

DIE

Side View (a)

End View (b)

Bottom View (c)

DIE

Thermal

Pad

Figure 30. Views of Thermally Enhanced DCA Package

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MECHANICAL DATA

DCA (R-PDSO-G**) PowerPAD PLASTIC SMALL-OUTLINE P ACKAGE

0,25

0,50

0,75

0,15 NOM

Gage Plane

6,00

6,20

8,30 7,90

Thermal Pad (See Note D)

17,10

14,10

Seating Plane

16,9013,90

4073259/A 01/98

0,27

0,17

48 PINS SHOWN

DIM

PINS **

A MAX

A MIN

1,20 MAX

12,40

12,60

0,50

0,10

0,08

0°–8°

0,05

0,15

NOTES: A. All linear dimensions are in millimeters.

B. This drawing is subject to change without notice. C. Body dimensions do not include mold flash or protrusion not to exceed 0,15. D. The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane.

This pad is electrically and thermally connected to the backside of the die and possibly selected leads.

E. Falls within JEDEC MO-153

PowerPAD is a trademark of Texas Instruments.

IMPORTANT NOTICE

T exas Instruments and its subsidiaries (TI) reserve the right to make changes to their products or to discontinue any product or service without notice, and advise customers to obtain the latest version of relevant information to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied at the time of order acknowledgment, including those pertaining to warranty, patent infringement, and limitation of liability.

TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in accordance with TI’s standard warranty. Testing and other quality control techniques are utilized to the extent TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed, except those mandated by government requirements.

Customers are responsible for their applications using TI components. In order to minimize risks associated with the customer’s applications, adequate design and operating

safeguards must be provided by the customer to minimize inherent or procedural hazards. TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent

that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other intellectual property right of TI covering or relating to any combination, machine, or process in which such semiconductor products or services might be or are used. TI’s publication of information regarding any third party’s products or services does not constitute TI’s approval, warranty or endorsement thereof.

Texas Instruments TPA005D14DCAR, TPA005D14DCA, TPA005D14EVM Datasheet

Specifications and Main Features

Frequently Asked Questions

User Manual