condition able to meet “blue angel” norm (<1w
total power consumption)
■ Internally trimmed zener reference
■ Undervoltage lock-out with hysteresis
■ Integrated start-up supply
■ Over-temperature protection
■ Low stand-by current
■ Adjustable current limitation
Block diagram
10
1
PENTAWATT HV (022Y)
POWERSO-10
TM
Description
All the devices are made using VIPower M0
Technology, combines on the same silicon chip a
state-of-the-art PWM circuit together with an
optimized, high voltage, Vertical Power MOSFET
(700V/ 0.5A).
Typical applications cover offline power supplies
with a secondary power capability of 10W in wide
range condition and 20W in single range or with
doubler configuration. It is compatible from both
primary or secondary regulation loop despite
using around 50% less components when
compared with a discrete solution. Burst mode
operation is an additional feature of this device,
offering the ability to operate in stand-by mode
without extra components.
Continuous Drain-Source Voltage (TJ = 25 to 125°C)
–0.3 to 700V
Maximum CurrentInternally limitedA
Supply Voltage 0 to 15V
Voltage Range Input
0 to V
DD
V
Voltage Range Input0 to 5V
Maximum Continuous Current±2mA
Electrostatic Discharge (R = 1.5kΩ; C = 100pF)4000V
Avalanche Drain-Source Current, Repetitive or Not Repetitive
= 100°C; Pulse width limited by TJ max; δ < 1%)
(T
C
Power Dissipation at TC= 25ºC
Junction Operating TemperatureInternally limited° C
J
0.4 A
57W
Storage Temperature-65 to 150°C
4/34
VIPer20A-EElectrical data
1.2 Electrical characteristics
TJ = 25°C; VDD = 13V, unless otherwise specified
Table 2.Power section
SymbolParameterTest conditionsMinTypMaxUnit
BV
I
DSS
R
DS(on)
t
t
C
oss
(1) On Inductive Load, Clamped.
Drain-Source Voltage
DS
Off-State Drain
Current
Static Drain-Source
On Resistance
Fall Time
f
Rise Time
r
Output Capacitance
I
= 1mA; V
D
V
V
= 0V; Tj = 125°C
COMP
= 700V
DS
ID = 0.4A
= 0.4A; TJ= 100°C
I
D
= 0.2A; V
I
D
ID = 0.4A; V
= 25V90pF
V
DS
= 0V700V
COMP
15.518
=300V
IN
= 300V
IN
(1)
Figure 7
(1)
Figure 7
100ns
50ns
1.0mA
32
Table 3.Supply section
SymbolParameterTest conditionsMinTypMaxUnit
I
DDch
I
DD0
I
DD1
I
DD2
V
DDoff
V
DDon
V
DDhyst
Start-Up Charging CurrentV
Operating Supply CurrentV
Operating Supply CurrentV
Operating Supply CurrentV
Undervoltage Shutdown
Undervoltage Reset
Hysteresis Start-up
= 5V; VDS = 35V
DD
Figure 6, Figure 11
= 12V; F
DD
SW
= 0kHz
Figure 6
= 12V; F
DD
= 12V; F
DD
= 100kHz
sw
= 200kHz
sw
-2mA
1216mA
13mA
14mA
Figure 67.589V
Figure 61112V
Figure 62.43V
Ω
Ω
Table 4.Oscillator section
SymbolParameterTest conditionsMinTypMaxUnit
=8.2KΩ; CT=2.4nF
R
T
=9 to 15V;
F
V
OSCIH
V
OSCIL
SW
Oscillator Frequency Total
Variat ion
Oscillator Peak Voltage7.1V
Oscillator Valley Voltage3.7V
V
DD
± 1%; CT± 5%
with R
T
(see Figure )(see Figure 14)
90100110KHz
5/34
Electrical dataVIPer20A-E
Table 5.Error amplifier section
SymbolParameterTest conditionsMinTypMaxUnit
V
DDREGVDD
∆V
DDreg
G
BW
Regulation PointI
Total Variation
Unity Gain Bandwidth
=0mA (see Figure 5)
COMP
= 0 to 100°C
T
J
From Input =V
Output = V
DD
COMP
to
COMP pin is open
12.61313.4V
2%
150KHz
Figure 15
A
VOL
G
V
COMPLO
V
COMPHI
I
COMPLO
I
COMPHI
Open Loop Voltage Gain
DC Transconductance
m
Output Low Level
Output High Level
Output Low Current Capability
Output High Current
Capability
COMP pin is open
Figure 15
=2.5V(see Figure 5)
V
COMP
=-400µA; VDD=14V
I
COMP
=400µA; VDD=12V
I
COMP
V
=2.5V; VDD=14V
COMP
V
=2.5V; VDD=12V
COMP
4552dB
1.11.51.9mA/V
0.2V
4.5V
-600µA
600µA
Table 6.PWM comparator section
SymbolParameterTest conditionsMinTypMaxUnit
H
V
COMPoffVCOMP
I
Dpeak
t
∆V
ID
COMP
/ ∆I
DPEAK
OffsetI
Peak Current Limitation
Current Sense Delay to Turn-
d
Off
V
= 1 to 3 V
COMP
= 10mA
DPEAK
= 12V; COMP pin open
V
DD
ID = 1A
4.267.8V/A
0.5V
0.50.670.9 A
250ns
t
t
on(min)
Blanking Time250360ns
b
Minimum On Time3501200ns
Table 7.Shutdown and overtemperature section
SymbolParameterTest conditionsMinTypMaxUnit
V
COMPth
t
DISsu
T
tsd
T
hyst
6/34
Restart Threshold(see Figure 8)0.5V
Disable Set Up Time(see Figure 8)1.75µs
Thermal Shutdown
Temperature
(see Figure 8)140170190°C
Thermal Shutdown Hysteresis (see Figure 8)40°C
VIPer20A-EThermal data
2 Thermal data
Table 8.Thermal data
Symbol Parameter PENTAWATT
PowerSO-10™
(1)
DIP-8 Unit
R
R
R
1. When mounted using the minimum recommended pad size on FR-4 board.
2. On multylayer PCB.
Thermal Resistance Junction-pinMax 20 °C/W
thJA
Thermal Resistance Junction-caseMax 2.0 2.0 °C/W
thJC
Thermal Resistance Ambient-caseMax 70 60
thJC
35
(2)
°C/W
7/34
Pin descriptionVIPer20A-E
3 Pin description
3.1 Drain pin (Integrated Power MOSFET drain):
Integrated Power MOSFET drain pin. It provides internal bias current during start-up via an
integrated high voltage current source which is switched off during normal operation. The
device is able to handle an unclamped current during its normal operation, assuring self
protection against voltage surges, PCB stray inductance, and allowing a snubberless operation
for low output power.
3.2 Source pin:
Power MOSFET source pin. Primary side circuit common ground connection.
3.3 VDD pin (power supply):
This pin provides two functions :
●It corresponds to the low voltage supply of the control part of the circuit. If V
8V, the start-up current source is activated and the output power MOSFET is switched off
until the V
reduced, the V
ground. After that, the current source is shut down, and the device tries to start up by
switching again.
●This pin is also connected to the error amplifier, in order to allow primary as well as
secondary regulation configurations. In case of primary regulation, an internal 13V
trimmed reference voltage is used to maintain V
voltage between 8.5V and 12.5V will be put on V
stuck the output of the transconductance amplifier to the high state. The COMP pin
behaves as a constant current source, and can easily be connected to the output of an
optocoupler. Note that any overvoltage due to regulation loop failure is still detected by the
error amplifier through the V
will be somewhat higher than the nominal one, but still under control.
voltage reaches 11V. During this phase, the internal current consumption is
DD
pin is sourcing a current of about 2mA and the COMP pin is shorted to
DD
at 13V. For secondary regulation, a
DD
pin by transformer design, in order to
DD
voltage, which cannot overpass 13V. The output voltage
DD
goes below
DD
3.4 Compensation pin
This pin provides two functions :
●It is the output of the error transconductance amplifier, and allows for the connection of a
compensation network to provide the desired transfer function of the regulation loop. Its
bandwidth can be easily adjusted to the needed value with usual components value. As
stated above, secondary regulation configurations are also implemented through the
COMP pin.
●When the COMP voltage is going below 0.5V, the shut-down of the circuit occurs, with a
zero duty cycle for the power MOSFET. This feature can be used to switch off the
converter, and is automatically activated by the regulation loop (no matter what the
configuration is) to provide a burst mode operation in case of negligible output power or
open load condition.
8/34
VIPer20A-EPin description
3.5 OSC pin (oscillator frequency):
An Rt-Ct network must be connected on that to define the switching frequency. Note that
despite the connection of R
from 8V to 15V. It provides also a synchronisation capability, when connected to an external
frequency source.
Figure 1.Connection diagrams (top view)
to VDD, no significant frequency change occurs for VDD varying
t
PENTAWATT HV
PENTAWATT HV (022Y)
Figure 2.Current and voltage convention
IDDID
IOSC
OSC
13V
VDD
VOSC
-
+
VCOMP
COMP SOURCE
ICOMP
DIP-8
DRAINVDD
VDS
FC00020
PowerSO-10
TM
9/34
Typical circuitVIPer20A-E
4 Typical circuit
Figure 3.Offline power supply with auxiliary supply feedback
F1
BR1
TR1
D2
D1
C2
R1
C7
L2
+Vcc
C9
AC IN
TR2
C1
R9
D3
C4
C3
R7
R2
DRAINVDD
13V
-
+
C11
COMP SOURCE
C6
OSC
C5
R3
Figure 4.Offline power supply with optocoupler feedback
AC IN
F1
TR2
C1
R9
BR1
D1
C2
C4
R1
D3
C3
R7
VIPer20
TR1
GND
C10
FC00401
D2
C7
C10
L2
C9
+Vcc
GND
R2
13V
-
+
COMP SOURCE
C11
OSC
C5
10/34
DRAINVDD
VIPer20
C6
R3
R6
ISO1
R4
U2
C8
R5
FC00411
VIPer20A-EOperation description
5 Operation description
5.1 Current mode topology:
The current mode control method, like the one integrated in the devices, uses two control loops
- an inner current control loop and an outer loop for voltage control. When the Power MOSFET
output transistor is on, the inductor current (primary side of the transformer) is monitored with a
SenseFET technique and converted into a voltage V
reaches V
(the amplified output voltage error) the power switch is switched off. Thus, the
COMP
outer voltage control loop defines the level at which the inner loop regulates peak current
through the power switch and the primary winding of the transformer.
Excellent open loop D.C. and dynamic line regulation is ensured due to the inherent input
voltage feedforward characteristic of the current mode control. This results in improved line
regulation, instantaneous correction to line changes, and better stability for the voltage
regulation loop.
Current mode topology also ensures good limitation in case there is a short circuit. During the
first phase the output current increases slowly following the dynamic of the regulation loop.
Then it reaches the maximum limitation current internally set and finally stops because the
power supply on V
is no longer correct. For specific applications the maximum peak current
DD
internally set can be overridden by externally limiting the voltage excursion on the COMP pin.
An integrated blanking filter inhibits the PWM comparator output for a short time after the
integrated Power MOSFET is switched on. This function prevents anomalous or premature
termination of the switching pulse in case there are current spikes caused by primary side
capacitance or secondary side rectifier reverse recovery time.
proportional to this current. When VS
S
5.2 Stand-by mode
Stand-by operation in nearly open load conditions automatically leads to a burst mode
operation allowing voltage regulation on the secondary side. The transition from normal
operation to burst mode operation happens for a power P
1
Where:
is the primary inductance of the transformer. FSW is the normal switching frequency.
L
P
I
STBY
P
STBY
is the minimum controllable current, corresponding to the minimum on time that the
device is able to provide in normal operation. This current can be computed as :
I
STBY
t
+ td is the sum of the blanking time and of the propagation time of the internal current sense
b
and comparator, and represents roughly the minimum on time of the device. Note: that P
may be affected by the efficiency of the converter at low load, and must include the power
drawn on the primary auxiliary voltage.
-- -
L
2
tbtd+()V
-----------------------------=
given by :
STBY
I2STBYFSW=
P
IN
L
p
STBY
11/34
Operation descriptionVIPer20A-E
As soon as the power goes below this limit, the auxiliary secondary voltage starts to increase
above the 13V regulation level, forcing the output voltage of the transconductance amplifier to
low state (V
COMP
< V
COMPth
). This situation leads to the shutdown mode where the power
switch is maintained in the Off state, resulting in missing cycles and zero duty cycle. As soon as
V
gets back to the regulation level and the V
DD
COMPth
threshold is reached, the device operates
again. The above cycle repeats indefinitely, providing a burst mode of which the effective duty
cycle is much lower than the minimum one when in normal operation. The equivalent switching
frequency is also lower than the normal one, leading to a reduced consumption on the input
main supply lines. This mode of operation allows the VIPer20A-E to meet the new German
"Blue Angel" Norm with less than 1W total power consumption for the system when working in
stand-by mode. The output voltage remains regulated around the normal level, with a low
frequency ripple corresponding to the burst mode. The amplitude of this ripple is low, because
of the output capacitors and low output current drawn in such conditions.The normal operation
resumes automatically when the power gets back to higher levels than P
STBY
.
5.3 High voltage start-up current suorce
An integrated high voltage current source provides a bias current from the DRAIN pin during
the start-up phase. This current is partially absorbed by internal control circuits which are
placed into a standby mode with reduced consumption and also provided to the external
capacitor connected to the V
threshold V
of the UVLO logic, the device becomes active mode and starts switching. The
DDon
start-up current generator is switched off, and the converter should normally provide the
needed current on the V
(see Figure 11).
pin. As soon as the voltage on this pin reaches the high voltage
DD
pin through the auxiliary winding of the transformer, as shown on
DD
In case there are abnormal conditions where the auxiliary winding is unable to provide the low
voltage supply current to the V
external capacitor discharges to the low threshold voltage V
pin (i.e. short circuit on the output of the converter), the
DD
of the UVLO logic, and the
DDoff
device goes back to the inactive state where the internal circuits are in standby mode and the
start-up current source is activated. The converter enters a endless start-up cycle, with a startup duty cycle defined by the ratio of charging current towards discharging when the VIPer20-E
tries to start. This ratio is fixed by design to 2A to 15A, which gives a 12% start-up duty cycle
while the power dissipation at start-up is approximately 0.6W, for a 230Vrms input voltage.
This low value start-up duty cycle prevents the application of stress to the output rectifiers as
well as the transformer when a short circuit occurs.
The external capacitor C
converter to start up, when the device starts switching. This time t
on the VDD pin must be sized according to the time needed by the
VDD
depends on many
SS
parameters, among which transformer design, output capacitors, soft start feature, and
compensation network implemented on the COMP pin. The following formula can be used for
defining the minimum capacitor needed:
I
DDtSS
--------------------
>
where:
I
DD
C
VDD
V
DDhyst
is the consumption current on the VDD pin when switching. Refer to specified I
and IDD2
DD1
values.
t
is the start up time of the converter when the device begins to switch. Worst case is
SS
generally at full load.
V
12/34
is the voltage hysteresis of the UVLO logic (refer to the minimum specified value).
DDhyst
VIPer20A-EOperation description
The soft start feature can be implemented on the COMP pin through a simple capacitor which
will be also used as the compensation network. In this case, the regulation loop bandwidth is
rather low, because of the large value of this capacitor. In case a large regulation loop
bandwidth is mandatory, the schematics of (see Figure 17) can be used. It mixes a high
performance compensation network together with a separate high value soft start capacitor.
Both soft start time and regulation loop bandwidth can be adjusted separately.
If the device is intentionally shut down by tying the COMP pin to ground, the device is also
performing start-up cycles, and the V
voltage is oscillating between V
DD
DDon
and V
DDoff
.
This voltage can be used for supplying external functions, provided that their consumption does
not exceed 0.5mA. (see Figure 18) shows a typical application of this function, with a latched
shutdown. Once the "Shutdown" signal has been activated, the device remains in the Off state
until the input voltage is removed.
5.4 Transconductance error amplifier
The VIPer20A-E includes a transconductance error amplifier. Transconductance Gm is the
change in output current (I
∂l
G
COMP
------------------ -=
m
∂V
DD
) versus change in input voltage (VDD). Thus:
COMP
The output impedance Z
V
∂
COMP
Z
COMP
--------------------
I
∂
COMP
This last equation shows that the open loop gain A
A
= Gm x Z
VOL
COMP
at the output of this amplifier (COMP pin) can be defined as:
COMP
1
∂VCOMP
------- -
------------------------
×==
G
∂V
m
DD
can be related to Gm and Z
VOL
COMP
:
where Gm value for VIPer20A-E is 1.5 mA/V typically.
G
is defined by specification, but Z
m
and therefore A
COMP
are subject to large tolerances.
VOL
An impedance Z can be connected between the COMP pin and ground in order to define the
transfer function F of the error amplifier more accurately, according to the following equation
(very similar to the one above):
F
= Gm x Z(S)
(S)
The error amplifier frequency response is reported in for different values of a simple resistance
connected on the COMP pin. The unloaded transconductance error amplifier shows an internal
Z
of about 330KΩ. More complex impedance can be connected on the COMP pin to
COMP
achieve different compensation level. A capacitor will provide an integrator function, thus
eliminating the DC static error, and a resistance in series leads to a flat gain at higher
frequency, insuring a correct phase margin. This configuration is illustrated in Figure 20
As shown in Figure 19 an additional noise filtering capacitor of 2.2nF is generally needed to
avoid any high frequency interference.
Is also possible to implement a slope compensation when working in continuous mode with
duty cycle higher than 50%. Figure 21 shows such a configuration. Note: R1 and C2 build the
classical compensation network, and Q1 is injecting the slope compensation with the correct
polarity from the oscillator sawtooth.
13/34
Operation descriptionVIPer20A-E
5.5 External clock synchronization:
The OSC pin provides a synchronisation capability when connected to an external frequency
source. Figure 21 shows one possible schematic to be adapted, depending the specific needs.
If the proposed schematic is used, the pulse duration must be kept at a low value (500ns is
sufficient) for minimizing consumption. The optocoupler must be able to provide 20mA through
the optotransistor.
5.6 Primary peak current limitation
The primary I
current and, consequently, the output power can be limited using the
DPEAK
simple circuit shown in Figure 22 . The circuit based on Q1, R
the COMP pin in order to limit the primary peak current of the device to a value:
I
DPEAK
V
COMP
------------------------------- -=
0.5–
H
ID
where:
R
+
1R2
V
COMP
The suggested value for R
0.6
-------------------
×=
R
2
is in the range of 220KΩ.
1+R2
5.7 Over-temperature protection
Over-temperature protection is based on chip temperature sensing. The minimum junction
temperature at which over-temperature cut-out occurs is 140ºC, while the typical value is
170ºC. The device is automatically restarted when the junction temperature decreases to the
restart temperature threshold that is typically 40ºC below the shutdown value (see Figure 13)
Figure 21. External clock sinchronisationFigure 22. Current limitation circuit example
VIPer20
DRAINVDD
COMP SOURCE
Q1
FC00480
VIPer20
DRAINVDD
COMP SOURCE
10 k
13V
-
+
OSC
Ω
FC00470
20/34
OSC
13V
-
+
R1
R2
VIPer20A-EElectrical over stress
6 Electrical over stress
6.1 Electrical over stress ruggedness
The VIPer may be submitted to electrical over-stress, caused by violent input voltage surges or
lightning. Following the Layout Considerations is sufficient to prevent catastrophic damages
most of the time. However in some cases, the voltage surges coupled through the transformer
auxiliary winding can exceed the V
may trigger the V
discharge current of the V
internal protection circuitry which could be damaged by the strong
DD
bulk capacitor. The simple RC filter shown in Figure 23 can be
DD
implemented to improve the application immunity to such surges.
Figure 23. Input voltage surges protection
pin absolute maximum rating voltage value. Such events
DD
C1
Bulk capacitor
C2
22nF
OSC
VIPerXX0
13V
R2
39R
VDD
R1
(Optional)
D1
Auxilliary winding
DRAIN
-
+
COMP
SOURCE
21/34
LayoutVIPer20A-E
7 Layout
7.1 Layout considerations
Some simple rules insure a correct running of switching power supplies. They may be
classified into two categories:
–Minimizing power loops: The switched power current must be carefully analysed and
the corresponding paths must be as small an inner loop area as possible. This avoids
radiated EMC noises, conducted EMC noises by magnetic coupling, and provides a
better efficiency by eliminating parasitic inductances, especially on secondary side.
–Using different tracks for low level and power signals: Interference due to mixing of
signal and power may result in instabilities and/or anomalous behaviour of the device
in case of violent power surge (Input overvoltages, output short circuits...).
In case of VIPer, these rules apply as shown on (see Figure 24).
–Loops C1-T1-U1, C5-D2-T1, and C7-D1-T1 must be minimized.
–C6 must be as close as possible to T1.
–Signal components C2, ISO1, C3, and C4 are using a dedicated track connected
directly to the power source of the device.
Figure 24. Recommended layout
R1
C1
From input
dio des bri dge
C2
OSC
U1
VIPerXX0
13V
ISO1
-
+
COMP SOURCE
C3
T1
D2
DRAINVDD
C5
R2
C4
D1
To secondary
C7
f i l t er i n g an d l o ad
C6
FC00500
22/34
VIPer20A-EPackage mechanical data
8 Package mechanical data
In order to meet environmental requirements, ST offers these devices in ECOPACK® packages.
These packages have a Lead-free second level interconnect . The category of second Level
Interconnect is marked on the package and on the inner box label, in compliance with JEDEC
Standard JESD97. The maximum ratings related to soldering conditions are also marked on
the inner box label. ECOPACK is an ST trademark. ECOPACK specifications are available at:
www.st.com.
23/34
Package mechanical dataVIPer20A-E
Table 9.Pentawatt HV Mechanical data
Dim
MinTypMaxMinTypMax
A4.304.800.1690.189
C1.171.370.0460.054
D2.402.800.0940.11
E0.350.550.0140.022
F0.600.800.0240.031
G14.915.210.1930.205
G27.497.800.2950.307
H19.309.700.3660.382
H210.400.409
H310.0510.400.3960.409
L15.6017.306.140.681
L114.6015.220.5750.599
L221.2021.850.8350.860
L322.2022.820.8740.898
L52.6030.1020.118
L615.1015.800.5940.622
L766.600.2360.260
M2.503.100.0980.122
M14.505.600.1770.220
R0.500.02
V490°
Diam3.653.850.1440.152
mm.inch
Figure 25. Package dimension
24/34
P023H3
VIPer20A-EPackage mechanical data
Table 10.Pentawatt HV 022Y ( Vertical High Pitch ) Mechanical data
Dim
MinTypMaxMinTypMax
A4.304.800.1690.189
C1.171.370.0460.054
D2.402.800.0940.110
E0.350.550.0140.022
F0.600.800.0240.031
G14.915.210.1930.205
G27.497.800.2950.307
H19.309.700.3660.382
H210.400.409
H310.0510.400.3960.409
L16.4217.420.6460.686
L114.6015.220.5750.599
L320.5221.520.8080.847
L52.603.000.1020.118
L615.1015.800.5940.622
L76.006.600.2360.260
M2.503.100.0980.122
M15.005.700.1970.224
R0.500.020.020
V490°90°
Diam3.653.850.1440.154
mm.inch
Figure 26. Package dimension
M1
G2
G1
L
L1
E
M
R
Resin betw een
leads
V4
F
D
L6
L7
L3
L5
A
C
H2
H3
H1
DIA
25/34
Package mechanical dataVIPer20A-E
Table 11. DIP-8 Mechanical data
Dim.
MinTypMaxMinTypMax
A 3.32 0.131
a1 0.51 0.020
B 1.15 1.65 0.045 0.065
b 0.356 0.55 0.014 0.022
b1 0.204 0.304 0.008 0.012
D 10.92 0.430
E 7.95 9.75 0.313 0.384
e 2.54 0.100
e3 7.62 0.300
e4 7.62 0.300
F 6.6 0.260
I 5.08 0.200
L 3.18 3.81 0.125 0.150
Z 1.52 0.060
mm Inch
Figure 27. Package dimensions
26/34
VIPer20A-EPackage mechanical data
Table 12.PowerSO-10 mechanical data
Dim.
A 3.35 3.65 0.132 0.144
A1 0.00 0.10 0.000 0.004
B 0.40 0.60 0.016 0.024
C 0.35 0.55 0.013 0.022
D 9.40 9.60 0.370 0.378
D1 7.40 7.60 0.291 0.300
e 1.27 0.050
E 9.30 9.50 0.366 0.374
E1 7.20 7.40 0.283 0.291
E2 7.20 7.60 0.283 0.300
E3 6.10 6.35 0.240 0.250
E4 5.90 6.10 0.232 0.240
F 1.25 1.35 0.049 0.053
h 0.50 0.002
H 13.80 14.40 0.543 0.567
L 1.20 1.80 0.047 0.071
q 1.70 0.067
α
MinTypMaxMinTypMax
o
8
0
mm Inch
o
Figure 28. Package dimension
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Package mechanical dataVIPer20A-E
Figure 29. Power Pad layout
Figure 30. Tube shipment
Table 13.Tube shipment
Base Q.ty Bulk Q.ty Tube length (± 0.5) A B C (± 0.1)
Casablanca 50 1000 532 10.4 16.4 0.8
Muar 50 1000 532 4.9 17.2 0.8
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VIPer20A-EPackage mechanical data
Figure 31. Reel shipment
Table 14.Reel dimension
Base Q.ty 600
Bulk Q.ty 600
A (max) 330
B (min) 1.5
C (± 0.2) 13
F 20.2
G (± 0.2) 24.4
N (min) 60
T (max) 30.4
Note:All dimensoin are in mm.
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Package mechanical dataVIPer20A-E
Figure 32. Tape shipment
Table 15.Tape dimension
Tape width W 24
Tape Hole Spacing P0 (± 0.1) 4
Component Spacing P 24
Hole Diameter D (± 0.1/-0) 1.5
Hole Diameter D1 (min) 1.5
Hole Position F (± 0.05) 11.5
Compartment Depth K (max) 6.5
Hole Spacing P1 (± 0.1) 2
Note:All dimensions are in mm.
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VIPer20A-EPackage mechanical data
Figure 33. Pentawatt HV tube shipment ( no suffix )
Table 16.Tube dimension
Base Q.ty 50
Bulk Q.ty 1000
Tube le n g th (± 0.5 ) 532
A 18
B 33.1
C (± 0.1) 1
Note:All dimensions are in mm.
Figure 34. Dip-8 Tube shipment (no suffix)
Table 17.Tube dimension
Base Q.ty 20
Bulk Q.ty 1000
Tube le n g th (± 0.5 ) 532
A 8.4
B 11.2
C (± 0.1) 0.8
Note:All dimensions are in mm.
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Order codeVIPer20A-E
9 Order code
Table 18.Order code
Part numberPackage
VIPer20A-EPENTAWATT HV
VIPer20A-22-E PENTAWATT HV (022Y)
VIPer20ADIP-EDIP-8
VIPer20ASP-EPowerSO-10
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VIPer20A-ERevision history
10 Revision history
Table 19.Revision history
DateRevisionChanges
28-Sep-20051Initial release.
21-Jun-20062New template, few updates
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VIPer20A-E
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