L4972A
2A SWITCHING REGULATOR
■2A OUTPUT CURRENT
■5.1V TO 40V OUTPUT VOLTAGE RANGE
■0 TO 90% DUTY CYCLE RANGE
■INTERNAL FEED-FORWARD LINE REG.
■INTERNAL CURRENT LIMITING
■PRECISE 5.1V ± 2% ON CHIP REFERENCE
■RESET AND POWER FAIL FUNCTIONS
■INPUT/OUTPUT SYNC PIN
■UNDER VOLTAGE LOCK OUT WITH HYSTERETIC TURN-ON
■PWM LATCH FOR SINGLE PULSE PER PERIOD
■VERY HIGH EFFICIENCY
■SWITCHING FREQUENCY UP TO 200KHz
■THERMAL SHUTDOWN
■CONTINUOUS MODE OPERATION
The L4972A is a stepdown monolithic power switching regulator delivering 2A at a voltage variable from 5.1 to 40V.
Realized with BCD mixed technology, the device
PowerDIP20 (16+2+2) |
SO20 |
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Part Number |
Package |
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L4972A |
DIP20 (16+2+20) |
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L4972AD |
SO20 |
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L4972AD013TR |
SO20 in Tape & Reel |
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uses a DMOS output transistor to obtain very high efficiency and very fast switching times. Features of the L4972 include reset and power fail for microprocessors, feed forward line regulation, soft start, limiting current and thermal protection. The device is mounted in a Powerdip 16 + 2 + 2 and SO20 large plastic packages and requires few external components. Efficient operation at switching frequencies up to 200KHz allows reduction in the size and cost of external filter component.
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Rev. 3 |
May 2005 |
1/22 |
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L4972A
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Pin |
Function |
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1 |
BOOTSTRAP |
A Cboot capacitor connected between this terminal and the output allows to drive |
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properly the internal D-MOS transistor. |
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2 |
RESET DELAY |
A Cd capacitor connected between this terminal and ground determines the reset |
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signal delay time. |
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3 |
RESET OUT |
Open Collector Reset/power Failand the output voltages are safe. Signal Output. |
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This output is high when the supply |
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4 |
RESET INPUT |
Input of Power Fail Circuit. The threshold is 5.1V. It may be connected via a divider |
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to the input for power fail function. It must be connected to the pin 14 an external |
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30KΩ resistor when power fail signal not required. |
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5, 6 15, |
GROUND |
Common Ground Terminal |
16 |
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7 |
FREQUENCY |
A series RC network connected between this terminal and ground determines the |
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COMPENSATION |
regulation loop gain characteristics. |
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8 |
SOFT START |
Soft Start Time Constant. A capacitor is connected between the sterminal and |
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ground to define the soft start time constant. |
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9 |
FEEDBACK INPUT |
The Feedback Terminal of the Regulation Loop. The output is connected directly to |
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this terminal for 5.1V operation; It is connected via a divider for higher voltages. |
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10 |
SYNC INPUT |
Multiple L4972A’s are synchronized by connecting pin 10 inputs together or via an |
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external syncr. pulse. |
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11 |
SUPPLY VOLTAGE |
Unregulated Input Voltage. |
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12, 19 |
N.C. |
Not Connected. |
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13 |
Vref |
5.1V Vref Device Reference Voltage. |
14 |
Vstart |
Internal Start-up Circuit to Drive the Power Stage. |
17 |
OSCILLATOR |
Rosc. External resistor connected to ground determines the constant charging |
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current of Cosc. |
18 |
OSCILLATOR |
Cosc. External capacitor connected to ground determines (with Rosc) the switching |
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frequency. |
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20 |
OUTPUT |
Regulator Output. |
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BOOTSTRAP |
1 |
20 |
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OUTPUT |
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RESET DELAY |
2 |
19 |
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N.C. |
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RESET OUT |
3 |
18 |
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C OSC |
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P. FAIL INPUT |
4 |
17 |
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R OSC |
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GND |
5 |
16 |
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GND |
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GND |
6 |
15 |
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GND |
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FREQ. COMP. |
7 |
14 |
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Vstart |
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SOFT START |
8 |
13 |
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Vref |
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FEEDBACK IN. |
9 |
12 |
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N.C. |
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SYNC INPUT |
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10 |
11 |
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Vi |
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DIP20
2/22
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L4972A |
Table 3. Absolute Maximum Ratings |
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Symbol |
Parameter |
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Value |
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Unit |
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V11 |
Input Voltage |
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55 |
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V |
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V11 |
Input Operating Voltage |
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50 |
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V |
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V20 |
Output DC Voltage |
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-1 |
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V |
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Output Peak Voltage at t = 0.1µs f = 200kHz |
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-5 |
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V |
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I20 |
Maximum Output Current |
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Internally Limited |
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VI |
Boostrap Voltage |
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65 |
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V |
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Boostrap Operating Voltage |
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V11 + 15 |
V |
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V4, V8 |
Input Voltage at Pins 4, 12 |
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12 |
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V |
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V3 |
Reset Output Voltage |
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50 |
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V |
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I3 |
Reset Output Sink Current |
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50 |
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mA |
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V2, V7, V9, |
Input Voltage at Pin 2, 7, 9, 10 |
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7 |
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V |
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V10 |
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I2 |
Reset Delay Sink Current |
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30 |
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mA |
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I7 |
Error Amplifier Output Sink Current |
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1 |
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A |
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I8 |
Soft Start Sink Current |
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30 |
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mA |
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Ptot |
Total Power Dissipation at TPINS ≤ 90°C |
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5 / 3.75(*) |
W |
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at Tamb = 70°C (No copper area on PCB) |
1.3/1 (*) |
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TJ, Tstg |
Junction and Storage Temperature |
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-40 to 150 |
°C |
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(*) SO-20 |
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Table 4. Thermal Data |
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Symbol |
Parameter |
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PowerDIP |
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SO20 |
Unit |
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Rth j-pins |
Thermal Resistance Junction-Pins |
max, |
12 |
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16 |
°C/W |
Rth j-amb |
Thermal Resistance Junction-ambient |
max, |
60 |
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80 |
°C/W |
The L4972A is a 2A monolithic stepdown switching regulator working in continuous mode realized in the new BCD Technology. This technology allows the integration of isolated vertical DMOS power transistors plus mixed CMOS/Bipolar transistors.
The device can deliver 2A at an output voltage adjustable from 5.1V to 40V and contains diagnostic and control functions that make it particularly suitable for microprocessor based systems.
The block diagram shows the DMOS power transistors and the PWM control loop. Integrated functions include a reference voltage trimmed to 5.1V ± 2%, soft start, undervoltage lockout, oscillator with feedforward control, pulse by pulse current limit, thermal shutdown and finally the reset and power fail circuit. The reset and power fail circuit provides an output signal for a microprocessor indicating the status of the system.
Device turn on is around 11V with a typical 1V hysterysis, this threshold porvides a correct voltage for the driving stage of the DMOS gate and the hysterysis prevents instabilities.
An external bootstrap capacitor charge to 12V by an internal voltage reference is needed to provide correct gate drive to the power DMOS. The driving circuit is able to source and sink peak currents of around 0.5A to the gate of the DMOS transistor. A typical switching time of the current in the DMOS transistor is 50ns. Due to the fast commutation switching frequencies up to 200kHz are possible.
The PWM control loop consists of a sawtooth oscillator, error amplifier, comparator, latch and the output
3/22
L4972A
stage. An error signal is produced by comparing the output voltage with the precise 5.1V ± 2% on chip reference. This error signal is then compared with the sawtooth oscillator in order to generate frixed frequency pulse width modulated drive for the output stage. A PWM latch is included to eliminate multiple pulsing within a period even in noisy environments.
The gain and stability of the loop can be adjusted by an external RC network connected to the output of the error amplifier. A voltage feedforward control has been added to the oscillator, this maintains superior line regulation over a wide input voltage range. Closing the loop directly gives an output vol-tage of 5.1V, higher voltages are obtained by inserting a voltage divider.
At turn on, output overcurrents are prevented by the soft start function (fig. 5). The error amplifier is initially clamped by an external capacitor, Css, and allowed to rise linearly under the charge of an internal constant current source.
Output overload protection is provided by a current limit circuit. The load current is sensed by a internal metal resistor connected to a comparator. When the load current exceeds a preset threshold, the output of the comparator sets a flip flop which turns off the power DMOS. The next clock pulse, from an internal 40kHz oscillator, will reset the flip flop and the power DMOS will again conduct. This current protection method, ensures a constant current output when the system is overloaded or short circuited and limits the switching frequency, in this condition, to 40kHz. The Reset and Power fail diagram (fig. 7), generates an output signal when the supply voltage exceeds a threshold programmed by an external voltage divider. The reset signal, is generated with a delay time programmed by a external capacitor on the delay pin. When the supply voltage falls below the threshold or the output voltage goes below 5V, the reset output goes low immediately. The reset output is an open drain.
Fig. 7A shows the case when the supply voltage is higher than the threshold, but the output voltage is not yet 5V.
Fig. 7B shows the case when the output is 5.1V, but the supply voltage is not yet higher than the fixed threshold. The thermal protection disables circuit operation when the junction temperature reaches about 150°C and has a hysterysis to prevent unstable conditions.
4/22
L4972A
A
B
5/22
L4972A
Table 5. Electrical Characteristcs
Refer to the test circuit, TJ = 25°C, Vi = 35V, R4 = 30KΩ, C9 = 2.7nF, fSW = 100KHz typ, unless otherwise specified.
Symbol |
Parameter |
Test Condition |
Min. |
Typ. |
Max. |
Unit |
Fig. |
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DYNAMIC CHARACTERISTICS |
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Vi |
Input Volt. Range (pin 11) |
Vo = Vref to 40V Io = 2A (**) |
15 |
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50 |
V |
8 |
Vo |
Output Voltage |
Vi =15V to 50V Io= 1A; |
5 |
5.1 |
5.2 |
V |
8 |
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Vo = Vref |
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∆Vo |
Line Regulation |
Vi =15V to 50V |
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12 |
30 |
mV |
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Io = 0.5A; Vo= Vref |
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∆Vo |
Load Regulation |
Vo = Vref Io= 0.5A to 2A |
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7 |
20 |
mV |
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Vd |
Dropout Voltage between Pin |
Io = 2A |
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0.25 |
0.4 |
V |
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11 and 20 |
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I20L |
Max Limiting Current |
Vi = 15V to 50V |
2.5 |
2.8 |
3.5 |
A |
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Vo= Vref to 40V |
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η |
Efficiency (*) |
Io = 2A, f = 100KHz |
75 |
85 |
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% |
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Vo = Vref |
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Vo = 12V |
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90 |
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% |
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SVR |
Supply Voltage Ripple Rejection |
Vi = 2VRMS; Io= 1A |
56 |
60 |
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dB |
8 |
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f = 100Hz; Vo= Vref |
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f |
Switching Frequency |
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90 |
100 |
110 |
KHz |
8 |
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∆f/∆Vi |
Voltage Stability of Switching |
Vi = 15V to 45V |
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2 |
6 |
% |
8 |
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Frequency |
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∆f/Tj |
Temperature Stability of |
Tj = 0 to 125°C |
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1 |
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% |
8 |
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Switching Frequency |
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fmax |
Maximum Operating Switching |
Vo= Vref R4 = 15KΩ |
200 |
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KHz |
8 |
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Frequency |
Io = 2A C9= 2.2nF |
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(*) Only for DIP version (**) Pulse testing with a low duty cycle |
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Vref SECTION (pin 13) |
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V13 |
Reference Voltage |
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5 |
5.1 |
5.2 |
V |
10 |
∆V13 |
Line Regulation |
Vi = 15V to 50V |
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10 |
25 |
mV |
10 |
∆V13 |
Load Regulation |
I13 = 0 to 1mA |
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20 |
40 |
mV |
10 |
∆V13 /∆T |
Average Temperature |
Tj = 0°C to 125°C |
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0.4 |
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mV/°C |
10 |
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Coefficient Reference Voltage |
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I13 short |
Short Circuit Current Limit |
V13 = 0 |
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70 |
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mA |
10 |
VSTART SECTION (pin 15) |
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V14 |
Reference Voltage |
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11.4 |
12 |
12.6 |
V |
10 |
∆V14 |
Line Regulation |
Vi = 15 to 50V |
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0.6 |
1.4 |
V |
10 |
∆V14 |
Load Regulation |
I14 = 0 to 1mA |
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50 |
200 |
mV |
10 |
I14 short |
Short Circuit Current Limit |
V15 = 0V |
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80 |
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mA |
10 |
DC CHARACTERISTICS |
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V11on |
Turn-on Threshold |
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10 |
11 |
12 |
V |
12 |
V11 Hyst |
Turn-off Hysteresys |
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1 |
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V |
12 |
I11Q |
Quiescent Current |
V8 = 0; S1 = D |
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13 |
19 |
mA |
12 |
I11OQ |
Operating Supply Current |
V8 = 0; S1 = B; S2 = B |
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16 |
23 |
mA |
12 |
6/22 |
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L4972A
Table 5. Electrical Characteristcs (continued)
Refer to the test circuit, TJ = 25°C, Vi = 35V, R4 = 30KΩ, C9 = 2.7nF, fSW = 100KHz typ, unless otherwise specified.
Symbol |
Parameter |
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Test Condition |
Min. |
Typ. |
Max. |
Unit |
Fig. |
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I20L |
Out Leak Current |
Vi = 55V; S3 = A; V8= 0 |
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2 |
mA |
12 |
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SOFT START (pin 8) |
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I8 |
Soft Start Source Current |
V8 = 3V; V9= 0V |
80 |
115 |
150 |
µA |
13 |
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V8 |
Output Saturation Voltage |
I8 = 20mA; V11= 10V |
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1 |
V |
13 |
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I8= 200µA; V11= 10V |
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0.7 |
V |
13 |
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ERROR AMPLIFIER |
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V7H |
High Level Out Voltage |
I7 = 100µA; S1 = C; V9 = 4.7V |
6 |
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V |
14 |
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V7L |
Low Level Out Voltage |
I7 = 100µA; S1 = C; V9= 5.3V |
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1.2 |
V |
14 |
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I7H |
Source Output Current |
V7 = 1V; V7 = 4.7V |
100 |
150 |
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µA |
14 |
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-I7L |
Sink Output Current |
V7 = 6V; V9 = 5.3V |
100 |
150 |
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µA |
14 |
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I9 |
Input Bias Current |
S1 = B; RS = 10KΩ |
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0.4 |
3 |
µA |
14 |
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GV |
DC Open Loop Gain |
S1 = A; RS= 10Ω |
60 |
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dB |
14 |
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SVR |
Supply Voltage Rejection |
15 < Vi < 50V |
60 |
80 |
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dB |
14 |
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VOS |
Input Offset Voltage |
RS= 50Ω S1 = A |
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2 |
10 |
mV |
14 |
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RAMP GENERATOR (pin 18) |
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V18 |
Ramp Valley |
S1 = B; S2 = B |
1.2 |
1.5 |
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V |
12 |
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V18 |
Ramp Peak |
S1 = B; S2 = B |
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Vi |
= 15V |
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2.5 |
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V |
12 |
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Vi |
= 45V |
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5.5 |
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V |
12 |
I18 |
Min. Ramp Current |
S1 = A; I17= 100µA |
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270 |
300 |
µA |
12 |
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I18 |
Max. Ramp Current |
S1 = A; I17= 1mA |
2.4 |
2.7 |
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mA |
12 |
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SYNC FUNCTION (pin 10) |
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V10 |
Low Input Voltage |
Vi = 15V to 50V; V8 = 0; |
–0.3 |
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0.9 |
V |
12 |
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S1 = B; S2 = B; S4 = B |
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V10 |
High Input voltage |
V8 = 0; S1 = B; S2 = B; S4 = B |
2.5 |
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5.5 |
V |
12 |
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I10L |
Sync Input Current with Low |
V10= V18= 0.9V; S4 = B; |
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0.4 |
mA |
12 |
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Input Voltage |
S1 = B; S2 = B |
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I10H |
Input Current with High |
V10= 2.5V |
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1.5 |
mA |
12 |
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Input Voltage |
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V10 |
Output Amplitude |
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4 |
5 |
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V |
– |
tW |
Output Pulse Width |
Vthr = 2.5V |
0.3 |
0.5 |
0.8 |
µs |
– |
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RESET AND POWER FAIL FUNCTIONS |
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V9R |
Rising Thereshold Voltage (pin 9) |
Vi = 15 to 50V |
Vref |
Vref |
Vref |
V |
15 |
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V4 = 5.3V |
-130 |
-100 |
-80 |
mV |
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V9F |
Falling Thereshold Voltage (pin 9) |
Vi = 15 to 50V |
4.77 |
Vref |
Vref |
V |
15 |
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V4 = 5.3V |
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-200 |
-160 |
mV |
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V2H |
Delay High Threshold Volt. |
Vi = 15 to 50V |
4.95 |
5.1 |
5.25 |
V |
15 |
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V4 = 5.3V; V9 = V13 |
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V2L |
Delay Low Threshold Volt. |
Vi = 15 to 50V;V4 = 4.7V; V9 = V13 |
1 |
1.1 |
1.2 |
V |
15 |
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I2SO |
Delay Source Current |
V4 = 5.3V; V2 = 3V |
30 |
60 |
80 |
µA |
15 |
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I2SI |
Delay Source Sink Current |
V4 = 4.7V; V2 = 3V |
10 |
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mA |
15 |
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V3S |
Output Saturation Voltage |
I3 = 15mA; S1 = B V4 = 4.7V |
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0.4 |
V |
15 |
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I3 |
Output Leak Current |
V3 = 50V; S1 = A |
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100 |
µA |
15 |
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7/22 |