ST AN2492 Application note

AN2492

Application note

Wide range 400W L6599-based

HB LLC resonant converter for PDP application

Introduction

This note describes the performances of a 400 W reference board, with wide-range mains operation and power-factor-correction (PFC) and presents the results of its bench evaluation. The electrical specification refers to a power supply for a typical high-end PDP application.

The main features of this design are the very low no-load input consumption (<0.5 W) and the very high global efficiency, better than 90% at full load and nominal mains voltage (115 - 230 VAC).

The circuit consists of three main blocks. The first is a front-end PFC pre-regulator based on the L6563 PFC controller. The second stage is a multi-resonant half-bridge converter with an output voltage of +200 V/400 W, whose control is implemented through the L6599 resonant controller. A further auxiliary flyback converter based on the VIPer12A off-line primary switcher completes the architecture. This third block, delivering a total power of 7 W on two output voltages (+3.3 V and +5 V), is mainly intended for microprocessor supply and display power management operations.

L6599 & L6563 400W demo board (EVAL6599-400W-S)

June 2007

Rev 3

1/35

www.st.com

Contents	AN2492

Contents

1	Main characteristics and circuit description . . . . . . . . . . . . . . . . . . . .		. 4
2	Electrical test results . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		9
	2.1	Harmonic content measurement . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .	9
	2.2	Efficiency measurements . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .	10
	2.3	Resonant stage operating waveforms . . . . . . . . . . . . . . . . . . . . . . . . . . .	12
	2.4	Stand-by and no-load power consumption . . . . . . . . . . . . . . . . . . . . . . . .	15
	2.5	Short-circuit protection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .	16
	2.6	Overvoltage protection . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .	17
3	Thermal tests . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		18
4	Conducted emission pre-compliance test . . . . . . . . . . . . . . . . . . . . . .		20
5	Bill of materials . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		22
6	PFC coil specification . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		28
	6.1	Electrical characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .	28
	6.2	Mechanical aspect and pin numbering . . . . . . . . . . . . . . . . . . . . . . . . . . .	28
7	Resonant power transformer specification . . . . . . . . . . . . . . . . . . . . .		29
	7.1	Electrical characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .	29
8	Auxiliary flyback power transformer . . . . . . . . . . . . . . . . . . . . . . . . . . .		31
	8.1	Electrical characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .	31
9	Board layout . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		32
10	References . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		34
11	Revision history . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		34

2/35

AN2492	List of figures

List of figures

Figure 1. PFC pre-regulator electrical diagram . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 Figure 2. Resonant converter electrical diagram . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 7 Figure 3. Auxiliary converter electrical diagram . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 8 Figure 4. Compliance to EN61000-3-2 for harmonic reduction: full load . . . . . . . . . . . . . . . . . . . . . . . 9 Figure 5. Compliance to EN EN61000-3-2 for harmonic reduction: 70 W load . . . . . . . . . . . . . . . . . . 9 Figure 6. Compliance to JEIDA-MITI standard for harmonic reduction: full load . . . . . . . . . . . . . . . . . 9 Figure 7. Compliance to JEIDA-MITI standard for harmonic reduction: 70 W load . . . . . . . . . . . . . . . 9 Figure 8. Power factor vs. Vin & load. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 Figure 9. Total harmonic distortion vs. Vin & load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 10 Figure 10. Overall efficiency versus output power at nominal mains voltages. . . . . . . . . . . . . . . . . . . 10 Figure 11. Overall efficiency versus input mains voltage at various output power levels . . . . . . . . . . 12 Figure 12. Resonant circuit primary side waveforms at full load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 13 Figure 13. Resonant circuit primary side waveforms at light load (about 30 W output power) . . . . . . 13 Figure 14. Resonant circuit primary side waveforms at no load condition. . . . . . . . . . . . . . . . . . . . . . 14 Figure 15. Resonant circuit secondary side waveforms: +200 V output . . . . . . . . . . . . . . . . . . . . . . . 14 Figure 16. Low frequency (100 Hz) ripple voltage on the +200 V output. . . . . . . . . . . . . . . . . . . . . . . 15 Figure 17. Load transition (0.4 A - 2 A) on +200 V output voltage. . . . . . . . . . . . . . . . . . . . . . . . . . . . 15 Figure 18. +200 V output short-circuit waveforms . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 17

Figure 19. Thermal map @115 VAC - full load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19 Figure 20. Thermal map at 230 VAC - full load . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 19 Figure 21. Peak measurement on LINE at 115 VAC and full load . . . . . . . . . . . . . . . . . . . . . . . . . . . . 20 Figure 22. Peak measurement on NEUTRAL at 115 VAC and full load . . . . . . . . . . . . . . . . . . . . . . . . 20

Figure 23. Peak measurement on LINE at 230 VAC and full load . . . . . . . . . . . . . . . . . . . . . . . . . . . . 21 Figure 24. Peak measurement on NEUTRAL at 230 VAC and full load . . . . . . . . . . . . . . . . . . . . . . . . 21

Figure 25. Electrical diagram . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 28 Figure 26. Pin side view. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 29 Figure 27. Electrical diagram . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 29 Figure 28. Mechanical aspect and pin numbering . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 30 Figure 29. Winding position on coil former. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 30 Figure 30. Electrical diagram . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 31 Figure 31. Auxiliary transformer winding position on coil former . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 32 Figure 32. Copper tracks . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 32 Figure 33. Thru-hole component placing and top silk screen . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 33 Figure 34. SMT component placing and bottom silk screen . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 33

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Main characteristics and circuit description	AN2492

1 Main characteristics and circuit description

The main characteristics of the SMPS are listed below:

●Universal input mains range: 90 to 264 VAC - 45 to 65 Hz

●Output voltages: 200 V @ 2 A - 3.3 V @ 0.7 A - 5 V @ 1 A

●Mains harmonics: Compliance with EN61000-3-2 specifications

●Stand-by mains consumption: Typical 0.5 W @230 VAC

●Overall efficiency: better than 88% at full load, 90-264 VAC

●EMI: Compliance with EN55022-class B specifications

●Safety: Compliance with EN60950 specifications

●PCB single layer: 132x265 mm, mixed PTH/SMT technologies

The circuit consists of three stages. A front-end PFC pre-regulator implemented by the controller L6563 (Figure 1), a half-bridge resonant DC/DC converter based on the resonant controller L6599 (Figure 2) and a 7 W flyback converter intended for stand-by management (Figure 3) utilizing the VIPer12A off-line primary switcher.

The PFC stage delivers a stable 400 VDC supply to the downstream converters (resonant + flyback) and provides for the reduction of the current harmonics drawn from the mains, in order to meet the requirements of the European norm EN61000-3-2 and the JEIDA-MITI norm for Japan.

The PFC controller is the L6563 (U1), integrating all functions needed to operate the PFC and interface the downstream resonant converter. Though this controller chip is designed for Transition-Mode (TM) operation, where the boost inductor works next to the boundary between Continuous (CCM) and Discontinuous Conduction Mode (DCM), by adding a simple external circuit, it can be operated in LM-FOT (line-modulated fixed off-time) mode, allowing Continuous Conduction Mode operation, normally achievable with more expensive control chips and more complex architectures. This operative mode allows the use of this device at a high power level, usually covered by CCM topologies. For a detailed and complete description of the LM-FOT operating mode, see the application note AN1792. The external components to configure the circuit in LM-FOT mode are: C15, C17, D5, Q3, R14, R17 and R29.

The power stage of the PFC is a conventional boost converter, connected to the output of the rectifier bridge through a differential mode filtering cell (C5, C6 and L3) for EMI reduction. It includes a coil (L4), a diode (D3), and two capacitors (C7 and C8). The boost switch consists of two Power MOSFETs (Q1 and Q2), connected in parallel, which are directly driven by the L6563 output drive thanks to the high current capability of the IC. The divider (R30, R31 and R32) connected to MULT pin 3 brings the information of the instantaneous voltage that is used to modulate the boost current and to derive further information like the average value of the AC line used by the VFF (voltage feed-forward) function. This function is used to keep the output voltage almost independent of the mains.

The divider (R3, R6, R8, R10 and R11) is dedicated to detecting the output voltage while a further divider (R5, R7, R9, R16 and R25) is used to protect the circuit in case of voltage loop failure.

The second stage is an LLC resonant converter, with half-bridge topology implementation, working in ZVS (zero voltage switching) mode. The controller is the L6599 integrated circuit that incorporates the necessary functions to properly drive the two half-bridge MOSFETs by a 50% fixed duty cycle with fixed dead-time, changing the frequency according to the

4/35

AN2492	Main characteristics and circuit description

feedback signal in order to regulate the output voltages against load and input voltage variations.

The main features of the L6599 are a non-linear soft-start, a current protection mode used to program the hiccup mode timing, a dedicated pin for sequencing or brown-out (LINE) and a stand-by pin (STBY) for burst mode operation at light loads (not used in this design).

The transformer (T1) uses the magnetic integration approach, incorporating the resonant series and shunt inductances of the LLC resonant tank. Thus, no additional external coils are needed for the resonance. For a detailed analysis of the LLC resonant converter, please refer to the application note AN2450.

The secondary side power circuit is configured with a single-ended transformer winding and full-bridge rectification (diodes D8A, D8B, D10A, D10B), which is more suitable for the current design. In fact, with this configuration, the total junction capacitance of the output diodes reflected at primary side is one half the capacitance in case of center-tap transformer. This capacitance at transformer primary side may affect the behavior of the resonant tank, changing the circuit from LLC to LLCC type, with the risk that the converter, in light-load/no-load condition (when the feedback loop increases the operating frequency) can no longer control the output voltage. If the converter has to operate down to zero load, this capacitance needs to be minimized. An inherent advantage of the full-bridge rectification is that the voltage rating of the output diodes in this configuration is one half the rating necessary for center-tap and two diodes circuit, which translates into a lower junction capacitance device, with consequent lower reflected capacitance at primary side.

The feedback loop is implemented by means of a classical configuration using a TL431 (U4) to adjust the current in the optocoupler diode (U3). The optocoupler transistor modulates the current from controller Pin 4, so the frequency will change accordingly, thus achieving the output voltage regulation. Resistors R46 and R54 set the maximum operating frequency. In case of a short circuit, the current entering the primary winding is detected by the lossless circuit (C34, C39, D11, D12, R43, and R45) and the resulting signal is fed into L6599 Pin 6.

In case of overload, the voltage on Pin 6 will exceed an internal threshold that triggers a protection sequence via Pin 2, keeping the current flowing in the circuit at a safe level.

The third stage is a small flyback converter based on the VIPer12A, a current mode controller with integrated Power MOSFET, capable of delivering about 7 W total output power on the output voltages (5 V and 3.3 V). The regulated output voltage is the 3.3 V output and, also in this case, the feedback loop uses the TL431 (U7) and optocoupler (U6) to control the output voltage. This converter is able to operate in the whole mains voltage range, even when the PFC stage is not working. From the auxiliary winding on the primary side of the flyback transformer (T2), a voltage Vs is available, intended to supply the other controllers (L6563 and L6599) in addition to the VIPer12A itself.

The PFC stage and the resonant converter can be switched on and off through the circuit based mainly on components Q7, Q8, D22 and U8, which, depending on the level of the signal ST-BY, supplies or removes the auxiliary voltage (VAUX) necessary to start up the controllers of the PFC and resonant stages. When the AC input voltage is applied to the power supply, the small flyback converter switches on first. Then, when the ST-BY signal is low, the PFC pre-regulator becomes operative, and the resonant converter can deliver the output power to the load. Note that if Pin 9 of Connector J3 is left floating (no signal ST-BY present), the PFC and resonant converter will not operate, and only +5 V and +3.3 V supplies are available on the output. In order to enable the +200 V output, Pin 9 of Connector J3 must be pulled down to ground.

5/35

6/35

Main

Vrect

.1 Figure

characteristics

1N5406

description circuit and

D15XB60

CM-1.5mH-5A

CM-10mH-5A

5-6

Vdc

8A/250V

DM-51uH-6A

PQ40-500uH

STTH8R06

NTC 2R5-S237

+400V

1M5

470nF-X2

330nF-X2

680nF-X2

470nF/630V

330uF/450V

CON2-IN

C10

C11

2nF2-Y1

2nF2-Y2

electrical regulatorPFCpre-

Vdc

Vaux

680k

C12

C13

2M2

680k

100nF

10uF/50V

2M2

680k

diagram

R10

R11

2M2

C14

C15

100k

15k

100nF

100pF

LL4148

R14

R15

STP12NM50FP

C16

R13

3k3

6R8

L6563

R17

1uF

56k

C17

15k

LL4148

INV

VCC

220pF

LL4148

R18

COMP

STP12NM50FP

MULT

GND

6R8

ZCD

R19

R16

VFF

RUN

5k1

TBO

PWM-STOP

1k0

R20

LINE

PFC-OK

PWM-LATCH

PWM-Latch

C18

R21

R22

R23

R24

1k0

330pF

C19

0R39

R25

R26

10nF

30k

150k

C20

R28

C21

R29

470nF

240k

2nF2

1k5

R30

R31

Vrect

BC857C

620k

R32

C22

10k

10nF

AN2492

Vdc

2 Figure

C23

R33

Resonant

+200V

4uF7

LL4148

R35

R34

3k9

STP14NK50Z

R36

T-RES-ER49

D8A

C24

R39

STTH803

10uH

C25

470nF

D8B

22uF/250V

R37

L6599

LL4148

R40

converter

C28

C27

100nF

STTH803

1M0

CSS

VBOOT

STP14NK50Z

47nF/630V

CON8

C26

DELAY

HVG

D10A

C30

C29

270pF

OUT

100uF/250V

R41

STTH803

RFMIN

R38

D10B

16k

STBY

VCC

Vaux

ISEN

LVG

STTH803

electrical

LINE

R42

LINE

GND

C37

C38

C33

DIS

PFC-STOP

C34

100uF/250V

4nF7

C31

C32

220pF/630V

10uF/50V

100nF

R43

150

characteristics Main

diagram

D12

LL4148

C39

R45

D11

PWM-Latch

1uF0

75R

LL4148

R46

R47

C40

R48

R49

R50

R85

1k5

10k

10nF

330k

120k

R51

330k

R52

D13

C41

R53

C59

3k3

C-12V

10uF/50V

75k

47nF

R54

1k5

C60

U3B

U3A

R56

R58

R86

470nF

SFH617A-2

1k0

75k

470R

and

SFH617A-2

R87

220R

circuit

R60

R61

C44

R59

12k

2k2

47nF

1k0

description

TL431

7/35

8/35

+5Vst-by

Vdc

T-FLY-AUX-E20

D15

+5Vst-by

VIPER-12A

+400V

1N5822

C45

33uH

C46

D14

1000uF/10V

100uF/10V

+3V3

PKC-136

St-By

D16

Vdd D

CON10

1N5821

C47

33uH

C49

C48

LL4148 U6B

1000uF/10V

100uF/10V

10uF/50V

D17

SFH617A-2

D20

BAV103

D18

D19

C50

B-10V

C-30V

10uF/50V

R62

R64

C51

1k6

100nF

C52

47nF

R83

Vdc

U6A

Q11

SFH617A-2

R67

BC557C

+400V

C58

1M0

1k0

R84

R66

10nF

+5Vst-by

150k

U8A

1k0

SFH617A-2

C53

R68

Vaux

R69

22k

2nF2

R71

R73

C54

R70

BC547C

St-By

BC847C

8k2

100nF

10k

22R

C55

R72

TL431

10uF/50V

10k

R77

R74

D21

R75

R76

+200V

4k7

BC857C

10k

B-15V

150k

Q10

BC847C

C56

C57

D22

R79

R80

U8B

100nF

1nF0

C-15V

SFH617A-2

2k2

30k

.3 Figure	characteristics Main
converter Auxiliary	description circuit and
diagram electrical

AN2492

AN2492	Electrical test results

2 Electrical test results

2.1Harmonic content measurement

The current harmonics drawn from the mains have been measured according to the European rule EN61000-3-2 Class-D and Japanese rule JEIDA-MITI Class-D, at full load and 70 W output power, at both nominal input voltages (230 VAC and 100 VAC). The pictures in Figure 4., Figure 5., Figure 6. and Figure 7. show that the measured current harmonics are well below the limits imposed by the regulations, both at full load and at 70 W load.

Figure 4. Compliance to EN61000-3-2 for	Figure 5. Compliance to EN EN61000-3-2 for
harmonic reduction: full load	harmonic reduction: 70 W load

					Measurements@230Vac Full load						EN61000-3-2 classDlimit s
10
1
0.1
0.01
0.001
0.0001
1	2	3	4	5	6	7	8	9	10	11	12	13	14	15	16	17	18	19	20

Ha r monic Or de r ( n)

						Measurement s@230Vac 70W				EN61000-3-2 classDlimit s
1
0.1
0.01
0.001
0.0001
1	2	3	4	5	6	7	8	9	10	11	12	13	14	15	16	17	18	19	20

Ha r moni c Or de r ( n)

Figure 6. Compliance to JEIDA-MITI standard Figure 7.	Compliance to JEIDA-MITI standard
for harmonic reduction: full load	for harmonic reduction: 70 W load

Measurement s@100Vac Full load JEIDA-MITI classD limit s

10
1
0.1
0.01
0.001
0.0001
1	2	3	4	5	6	7	8	9	10	11	12	13	14	15	16	17	18	19	20

Ha r moni c Or de r ( n)

						Measurement s@100Vac 70W					JEIDA-MITI classD limit s
1
0.1
0.01
0.001
0.0001
1	2	3	4	5	6	7	8	9	10	11	12	13	14	15	16	17	18	19	20

Ha r moni c Or de r ( n)

The Power Factor (PF) and the Total Harmonic Distortion (THD) are reported in Figure 8. and Figure 9. It is evident from the picture that the PF stays close to unity in the whole mains voltage range at full load and at half load, while it decreases at high mains at low load (70W). The THD has similar behavior, remaining within 25% overall the mains voltage range and increasing at low load (70 W) at high mains voltage.

9/35

Electrical test results	AN2492

Figure 8. Power factor vs. Vin & load	Figure 9. Total harmonic distortion vs. Vin &
	load

PF						THD [%]
1.00						35.00
0.98						30.00		400W
0.98								400W
						25.00		200W
						25.00
0.95								70W
		400W				20.00
0.93		200W
		70W				15.00
		70W
0.90
						10.00
0.88						5.00
						5.00
0.85						0.00
80	120	160	200	240	280	80	120	160	200	240	280
			Vin [Vrms]						Vin [Vrms]

2.2Efficiency measurements

Table 1. and Table 2. show the output voltage measurements at the nominal mains voltages of 115 VAC and 230 VAC, with different load conditions. For all measurements, both at full load and at light load operations, the input power is measured using a Yokogawa WT-210 digital power meter. Particular attention has to be paid when measuring input power at full load in order to avoid measurement errors due to the voltage drop on cables and connections.

Figure 10. shows the overall circuit efficiency, measured at each load condition, at both nominal input mains voltages of 115 VAC and 230 VAC. The values were measured after 30 minutes of warm-up at maximum load. The high efficiency of the PFC pre-regulator working in FOT mode and the very high efficiency of the resonant stage working in ZVS (i.e. with negligible switching losses), provides for an overall efficiency better than 88% at full load in the complete mains voltage range. This is a significant high value for a two-stage converter, especially at low input mains voltage where PFC conduction losses increase. Even at lower loads, the efficiency still remains high.

Figure 10. Overall efficiency versus output power at nominal mains voltages

					@230Vac	@115Vac
	100%
	95%
	90%
	85%
(%)	80%
Eff.	80%
Eff.
	75%
	70%
	65%
	60%
	0	50	100	150	200	250	300	350	400	450

Output Power (W)

10/35

AN2492	Electrical test results

The global efficiency at full load has been measured even at the limits of the input voltage range, with good results:

At VIN = 90 VAC - full load, the efficiency is 88.48%

At VIN = 264 VAC - full load, the efficiency is 93.70%

Also at light load, at an output power of about 10% of the maximum level, the overall efficiency is very good, reaching a value better than 79% over the entire input mains voltage range. Figure 11. shows the efficiency measured at various output power levels versus input mains voltage.

Table 1.	Efficiency measurements @VIN = 115 VAC
+200 V@load(A)		+5 V @load(A)		+3.3 V @load(A)		POUT(W)	PIN(W)	Efficiency

202.50	1.989	4.84	0.968	3.33	0.695	409.77	451.38	90.78%

202.50	1.751	4.84	0.968	3.33	0.695	361.58	397.70	90.92%

202.50	1.501	4.84	0.968	3.33	0.695	310.95	341.39	91.08%

202.50	1.251	4.84	0.968	3.33	0.695	260.33	285.86	91.07%

202.50	1.000	4.84	0.968	3.33	0.695	209.50	230.96	90.71%

202.53	0.751	4.84	0.968	3.33	0.695	159.10	176.63	90.08%

202.53	0.500	4.84	0.968	3.33	0.695	108.26	122.62	88.29%

202.53	0.250	4.84	0.968	3.33	0.695	57.63	69.04	83.48%

202.56	0.150	4.84	0.293	3.33	0.309	32.83	41.14	79.80%

202.67	0.051	4.84	0.293	3.33	0.309	12.78	20.34	62.85%

Table 2.	Efficiency measurements @VIN = 230 VAC
+200 V@load(A)		+5 V @load(A)		+3.3 V @load(A)		POUT(W)	PIN(W)	Efficiency

202.50	1.987	4.84	0.968	3.33	0.695	409.37	437.79	93.51%

202.50	1.750	4.84	0.968	3.33	0.695	361.37	386.90	93.40%

202.50	1.500	4.84	0.968	3.33	0.695	310.75	333.33	93.23%

202.50	1.250	4.84	0.968	3.33	0.695	260.12	279.65	93.02%

202.50	1.000	4.84	0.968	3.33	0.695	209.50	226.68	92.42%

202.50	0.750	4.84	0.968	3.33	0.695	158.87	174.10	91.25%

202.53	0.500	4.84	0.968	3.33	0.695	108.26	121.54	89.08%

202.53	0.250	4.84	0.968	3.33	0.695	57.63	68.96	83.57%

202.54	0.150	4.84	0.293	3.33	0.309	32.83	41.80	78.54%

202.67	0.050	4.84	0.293	3.33	0.309	12.58	19.86	63.35%

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