Philips TEA1065T, TEA1065 Datasheet

INTEGRATED CIRCUITS

DATA SH EET

TEA1065

Versatile telephone transmission
circuit with dialler interface

Product specification
File under Integrated Circuits, IC03A

March 1994

Philips Semiconductors Product specification

Versatile telephone transmission circuit with
dialler interface

FEATURES

• Current and voltage regulator mode with adjustable
static resistances

• Provides supply for external circuitry

• Symmetrical high-impedance inputs for piezoelectric

microphone

• Asymmetrical high-impedance input for electret
microphone

• DTMF signal input with confidence tone

• Mute input for pulse or DTMF dialling

• Power-down input for pulse dial or register recall

• Digital pulse input to drive an external switch transistor

• Receiving amplifier for magnetic, dynamic or

piezoelectric earpieces

ORDERING INFORMATION

EXTENDED TYPE

NUMBER

PINS PIN POSITION MATERIAL CODE

TEA1065 24 DIL plastic SOT101L
TEA1065T 24 SO24 plastic SOT137A

• Large gain setting range on microphone and earpiece
amplifiers

• Line loss compensation facility, line current dependent
(on microphone and earpiece amplifiers)

• Adjustable gain control

• DC line voltage adjustment facility

GENERAL DESCRIPTION

The TEA1065 is a bipolar integrated circuit which performs
all speech and line interface functions that are required in
fully electronic telephone sets with adjustable DC mask.
The circuit performs electronic switching between dialling
and speech internally.

PACKAGE

TEA1065

Notes

1. SOT101-1; 1998 Jun 18.

2. SOT137-1; 1998 Jun 18.

QUICK REFERENCE DATA

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

V
I
I

LN
line
CC

line voltage I

= 15 mA 4.25 4.45 4.65 V

line

normal operation line current range 10 − 150 mA
internal supply consumption

power-down input LOW − 1.14 1.5 mA
power-down input HIGH − 73 105 µA

V

CC

supply voltage for peripherals I

= 15 mA;

line

MUTE input
HIGH

IP= 1.2 mA 2.7 −−V

= 1.55 mA 2.5 −−V

I

P

G

V

voltage gain range

microphone amplifier 30 − 46 dB
earpiece amplifier 20 − 45 dB

∆G

V

line loss compensation

gain control range −5.5 −5.9 −6.3 dB

T

amb

operating ambient temperature range −25 −+75 °C

March 1994 2

Philips Semiconductors Product specification

Versatile telephone transmission circuit with
dialler interface

handbook, full pagewidth

DTMF

MUTE

MIC+
MIC−

V

CC
PD

17

IR

+

−

TEA1065

8
7

19

dB

+

−

−
+

20
21

SUPPLY AND

18

REFERENCE

CONTROL
CURRENT

CURRENT

REFERENCE

TEA1065

6

GAR

−

+

−

+

−
+

BANDGAP

REFERENCE

+

−

LINE
CURRENT
CONTROL

5

QR+

4

QR−

2

GAS1

1

LN

24

SLPE

3

GAS2

11

VBG

13

REFI

12

DOC

2216

23 9 15

V

EE

REG AGC STAB

Fig.1 Block diagram.

March 1994 3

DPI

14

10

VSI

CURL

MBA557

Philips Semiconductors Product specification

V ersatile telephone transmission circuit with
dialler interface

PINNING

SYMBOL PIN DESCRIPTION

LN 1 positive line terminal
GAS1 2 gain adjustment; sending amplifier
GAS2 3 gain adjustment; sending amplifier
QR− 4 inverting output; receiving amplifier
QR+ 5 non-inverting output; receiving

amplifier
GAR 6 gain adjustment; receiving amplifier
MIC− 7 inverting microphone input
MIC+ 8 non-inverting microphone input
STAB 9 current stabilizer
DPI 10 digital pulse input
VBG 11 bandgap output reference
DOC 12 drive current output
REFI 13 reference voltage input
VSI 14 voltage sense input
CURL 15 current limitation input
V

EE

IR 17 receiving amplifier input
PD 18 power-down input
DTMF 19 dual-tone multifrequency input
MUTE 20 MUTE input
V

CC

REG 22 voltage regulator decoupling
AGC 23 automatic gain control input
SLPE 24 slope (DC resistance) adjustment

16 negative line terminal

21 positive supply decoupling

handbook, halfpage

1

LN

GAS1

2
3

GAS2

4

QR−
QR+

5
6

GAR
MIC−
MIC+

STAB

DPI

VBG

DOC

7
8

9
10
11
12

TEA1065

MBA551

Fig.2 Pinning diagram.

TEA1065

SLPE

24
23

AGC

22

REG
V

21

CC

20

MUTE

19

DTMF

18

PD

17

IR
V

16

EE

CURL

15

VSI

14

REFI

13

March 1994 4

Philips Semiconductors Product specification

V ersatile telephone transmission circuit with
dialler interface

FUNCTIONAL DESCRIPTION
Supply: V

The circuit and its peripherals are usually supplied from the
telephone line. The circuit develops its own supply voltage
at V

CC

and SLPE (pins 1 and 24). The internal supply requires a
decoupling capacitor between VCCand VEE(pin 16); the
internal voltage regulator has to be decoupled by a
capacitor from REG (pin 22) to VEE. The internal current
stabilizer is set by a 3.6 kΩ resistor connected between
STAB (pin 9) and VEE.
The TEA1065 can be set either in a DC voltage regulator
mode or in a DC current regulator mode. The DC mask can
be selected by connecting the appropriate external
components to the dedicated pins (VSI, REFI, DOC,
VBG).
When the DC current regulator mode is not required it can
be cancelled by connecting pin VSI to VEE; pins REFI,
VBG and DOC are left open-circuit.

Voltage regulator mode

The voltage regulator mode is achieved when the line
current is less than the current I
With R13 = R14 = 30 kΩ, the current I
(Ip= 0 mA).

, LN, SLPE, REG and STAB

CC

(pin 21) and regulates its voltage drop between LN

as illustrated in Fig.3.

knee

= 30 mA

knee

TEA1065

This line current value will be reached when the voltage on
pin VSI (almost equal to the voltage on pin SLPE) exceeds
the voltage on pin REFI (equal to the voltage on pin VBG
divided by the resistor tap R13, R14). For other values of
R13 and R14, the I
formula:

I

knee=ICC

+ IP+ (VBG/R9) × {R14/(R14 + R13)}

− (R15/R9) × IO(VSI)

ICCis the current required by the circuit itself
(typ. 1.14 mA). IPis the current required by the peripheral
circuits connected between VCCand VEE. I
output current from pin VSI (typ. 2.5 µA).

The DC slope of the V
determined by R9 (R9 = R9a + R9b) in series with the
rdsof the external line current control transistor (see Fig.4;
rds= ∂VGS/∂IDat VGS=VDS).

Current regulator mode

The current regulator mode is achieved when the line
current is greater than I
V

curve is approximately 1300 Ω with R9 = 20 Ω,

line/Iline

R16 = 1 MΩ, R13 = R14 = 30 kΩ. For other values of
these resistances, the slope value can be approximated by
the following formula:

R9 × {1 + R16 × (1/R13 + 1/R14)}

current is given by the following

knee

O(VSI)

curve is, in this mode,

line/Iline

. In this mode, the slope of the

knee

is the

handbook, full pagewidth

line

current

I

knee

0

0

voltage

regulator

mode

current

regulator

mode

Fig.3 Voltage and current regulator mode.

March 1994 5

MBA567

set

voltage

Philips Semiconductors Product specification

V ersatile telephone transmission circuit with
dialler interface

The DC current flowing into the set is determined by the
exchange supply voltage (V
subscriber line (R

) and the DC voltage on the subscriber

line

set (see Fig.4).
If the line current exceeds ICC+ 0.3 mA, required by the
circuit itself (ICC≈ 1.14 mA), plus the current Iprequired by
the peripheral circuits connected to VCCthen the voltage
regulator will divert the excess current via LN.

VLN=V

where: V

ref

+ I

V

ref

× R9 =

SLPE

+ (I

ref

− ICC− 0.3 × 10−3− Ip) × R9

line

is an internally generated temperature
compensated reference voltage of 4.18 V and R9 is an
external resistor connected between SLPE and VEE.

The preferred value of R9 is 20 Ω. Changing R9 will
influence the microphone gain, gain control
characteristics, sidetone and the maximum output swing
on LN. In this instance, the voltage on the line (excluding
the diode rectifier bridge; see Fig.4) is:

V

line=VLN

+ VGS+ R16 × I

where: VGSis the voltage drop between the gate and
source terminal of the external line current control
transistor and I
(I

= 0 in the voltage regulator mode and increases with

DOC

is the current sunk by pin DOC

DOC

), the DC resistance of the

exch

DOC

TEA1065

I

in the current regulator mode).

line

Under normal conditions I
for the voltage regulator mode (I
behaviour of the circuit is equal to a 4.18 V voltage
regulator diode with an internal resistance of R9 in series
with the V

of the external line current control

GSon

transistor. For the current regulator mode (I
static behaviour of the circuit is equal to a 4.18 V voltage
regulator diode with an internal resistance of R9 in series
with the V

of the external line current control transistor

GSon

and also in series with a DC voltage source R16
× I

(the preferred value of R16 is 1 MΩ at this value the

DOC

current I

is negligible compared to I

DOC

In the audio frequency range the dynamic impedance
between LN and VEEis equal to R1 (see Fig.8). The
internal reference voltage V
of an external resistor RVA. This resistor, connected
between LN and REG, will decrease the internal reference
voltage. When RVAis connected between REG and SLPE
the internal reference voltage will increase.
The maximum allowed line current is given in Figs 5 and 6,
where the current is shown as a function of the required
reference voltage, ambient temperature and applied
package.

>> ICC+ 0.3 mA + Ipand

SLPE

< I

line

can be adjusted by means

ref

), the static

knee

line

).

line

> I

knee

), the

handbook, full pagewidth

V

R

exch

exch

R

line

I

DOC

V

line

I

R16

TEA1065

line

I

SLPE

+ 0.5 mA

DC
AC

22 9
REG V

C3 R5 R9

STAB

Fig.4 Supply arrangement.

March 1994 6

LNDOC

12112

24

SLPE

R1

I

CC

V

CC

0.3 mA

16

EE

C1

peripheral

circuits

MBA550

I

p

Philips Semiconductors Product specification

V ersatile telephone transmission circuit with
dialler interface

The current Ip, available from VCCfor supplying peripheral
circuits, depends on the external components and on the
line current. Fig.7 shows this current for VCC> 2.2 V and
for VCC> 3 V, where 3 V is the minimum supply voltage for
most CMOS circuits including a diode voltage drop for a
back-up diode. If MUTE is LOW the available current is
further reduced when the receiving amplifier is driven
(earpiece amplifier supplied from VCC).

handbook, halfpage

170

I

LN

(mA)

150

130

MBA570

(1)

handbook, halfpage

170

I

LN

(mA)

150

130

TEA1065

MBA571

(1)

110

(2)

90

70

50

30

212

46810

VLN-V

SLPE

(V)

110

90

70

50

30

212

T

amb

(1) 35 °C
(2) 45 °C

T

amb

(1) 65 °C
(2) 75 °C

Fig.5 TEA1065 safe operating area.

P

tot

1.2 W

1.0 W

(3) 55 °C
(4) 65 °C
(5) 75 °C

Fig.6 TEA1065T safe operating area.

(2)

(3)

(4)

(5)

46810

V

LN-VSLPE

P

tot

(V)

1.2 W

1.07 W

0.93 W

0.8 W

0.67 W

March 1994 7

Philips Semiconductors Product specification

V ersatile telephone transmission circuit with
dialler interface

handbook, halfpage

3

I

P

(mA)

2

1

0

(1)

(2)

(3)

(4)

012 4

3

VCC (V)

TEA1065

MBA569

I

= 15 mA at VLN= 4.45 V

line

R1 = 620 Ω
R9 = 20 Ω

Curve (1) and (3) are valid when the receiving amplifier is not driven or when MUTE =HIGH, curves (2) and (4)
are valid when MUTE = LOW and the receiving amplifier is driven, V
(1) = 2.2 mA; (2) = 1.77 mA; (3) = 0.78 mA and (4) = 0.36 mA.

= 150 mV, RL= 150 Ω (asymmetrical).

o(rms)

Fig.7 Maximum current Ipavailable from VCCfor external (peripheral) circuitry with VCC> 2.2 V and VCC> 3 V.

R1

V

C1

MBA552

CC

LN

V

EE

andbook, halfpage

SLPE

Leq=C3×R9 × R
Rp= 17.5 kΩ

L

eq

V

R9
20 Ω

p

ref

R

p

REG

C3

4.7 µF

Fig.8 Equivalent circuit impedance between LN

and VEE.

March 1994 8

Philips Semiconductors Product specification

V ersatile telephone transmission circuit with
dialler interface

Microphone inputs MIC+ and MIC− and gain
adjustment connections GAS1 and GAS2

The TEA1065 has symmetrical microphone inputs, its
input impedance is 40.8 kΩ (2 × 20.4 kΩ) and its voltage
gain is typ. 38 dB with R7 = 68 kΩ. Either dynamic,
magnetic or piezoelectric microphones can be used, or an
electret microphone with a built-in FET buffer.
Arrangements for the microphones types are illustrated in
Fig.9.

handbook, full pagewidth

MIC+

(1)

MIC−

8

7

MIC−

MIC+

TEA1065

The gain of the microphone amplifier is proportional to
external resistor R7, connected between GAS1 and
GAS2, which can be adjusted between 30 dB and 46 dB to
suit the sensitivity of the transducer.

An external 100 pF capacitor (C6) is required between
GAS1 and SLPE to ensure stability. A larger value of C6
may be chosen to obtain a first-order low-pass filter. The
“cut-off” frequency corresponds with the time constant
R7 × C6.

V

CC

21

7

8

16

V

EE

MIC+

MIC−

8

7

MBA553

(a) (b)

(a) magnetic or dynamic microphone,
the resistor (1) may be connected to
reduce the terminating impedance, or
for sensitive types a resistive
attenuator can be used to prevent
overloading the microphone inputs;

(c)

(b) electret microphone; (c) piezoelectric microphone.

Fig.9 Microphone arrangements.

March 1994 9