ON Semiconductor NCP3065, NCV3065 Technical data

NCP3065, NCV3065

Up to 1.5 A Constant Current Switching Regulator for LEDs

The NCP3065 is a monolithic switching regulator designed to deliver constant current for powering high brightness LEDs. The device has a very low feedback voltage of 235 mV (nominal) which is used to regulate the average current of the LED string. In addition, the NCP3065 has a wide input voltage up to 40 V to allow it to operate from 12 Vac or 12 Vdc supplies commonly used for lighting applications as well as unregulated supplies such as Lead Acid batteries. The device can be configured in a controller topology with the addition of an external transistor to support higher LED currents beyond the 1.5 A rated switch current of the internal transistor. The NCP3065 switching regulator can be configured in Step−Down (Buck) and Step−Up (boost) topologies with a minimum number of external components.

Features

• Integrated 1.5 A Switch

• Input Voltage Range from 3.0 V to 40 V

• Low Feedback Voltage of 235 mV

• Cycle−by−Cycle Current Limit

• No Control Loop Compensation Required

• Frequency of Operation Adjustable up to 250 kHz

• Operation with All Ceramic Output Capacitors or No Output Capacitance

• Analog and Digital PWM Dimming Capability

• Internal Thermal Shutdown with Hysteresis

• Automotive Version Available

Applications

• Automotive and Marine Lighting

• High Power LED Driver

• Constant Current Source

• Low Voltage LED Lighting

(Landscape, Path, Solar, MR16 Replacement)

+LED

0.15 W

220 mF

NCP3065

NC I

= 0.235 V

SWC SWE

GND

2.2 nF

out

22 mF

Cluster

−LED

sense

0.68 W

LED

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MARKING

DIAGRAMS

SOIC−8

D SUFFIX

CASE 751

PDIP−8

P, P1 SUFFIX

CASE 626

DFN−8

MN SUFFIX

CASE 488

NCP3065 = Specific Device Code A = Assembly Location L, WL = Wafer Lot Y, YY = Year W, WW = Work Week G or G = Pb−Free Package

(Note: Microdot may be in either location)

3065

ALYWG

NCP3065

AWL

YYWWG

3065

ALYW G

ORDERING INFORMATION

See detailed ordering and shipping information in the package dimensions section on page 15 of this data sheet.

Figure 1. Typical Buck Application Circuit

October, 2008 − Rev. 1

1 Publication Order Number:

NCP3065/D

NCP3065, NCV3065

Switch Collector

Switch Emitter

Timing Capacitor

GND

Figure 2. Pin Connections

N.C.

Ipk Sense

Comparator Inverting Input

(Top View)

COMPARATOR

N.C.

Sense

Comparator Inverting Input

SET dominant

−

0.2 V

COMPARATOR

−

NCP3065

Switch Collector

Switch Emitter

Timing Capacitor

NOTE: EP Flag must be tied to GND Pin 4 on PCB

TSD

SET dominant

OSCILLATOR

0.235 V REFERENCE REGULATOR

EP Flag

GND

(Top View)

Figure 3. Pin Connections

Switch Collector

Switch Emitter

Timing Capacitor

GND

N.C.

Sense

Comparator Inverting Input

Figure 4. Block Diagram

PIN DESCRIPTION

Pin No. Pin Name Description

1 Switch Collector Internal Darlington switch collector

2 Switch Emitter Internal Darlington switch emitter

3 Timing Capacitor Timing Capacitor Oscillator Input, Timing Capacitor

4 GND Ground pin for all internal circuits

5 Comparator

6 V

7 Ipk Sense Peak Current Sense Input to monitor the voltage drop across an external resistor to limit the peak

8 N.C. Pin not connected

Inverting Input

Inverting input pin of internal comparator

Voltage supply

current through the circuit

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NCP3065, NCV3065

MAXIMUM RATINGS (measured vs. pin 4, unless otherwise noted)

Rating

VCC (Pin 6) V

Comparator Inverting Input (Pin 5) V

Darlington Switch Collector (Pin 1) V

Darlington Switch Emitter (Pin 2) (Transistor OFF) V

Darlington Switch Collector to Emitter (Pins 1−2) V

Darlington Switch Current I

Ipk Sense (Pin 7) V

Timing Capacitor (Pin 3) V

Power Dissipation and Thermal Characteristics

PDIP−8 (Note 5)

Thermal Resistance Junction−to−Air

SOIC−8 (Note 5)

Thermal Resistance Junction−to−Air

DFN−8 (Note 5)

Thermal Resistance Junction−to−Air Thermal Resistance Junction−to−Case

Storage Temperature Range T

Maximum Junction Temperature T

Operating Junction Temperature Range (Note 3)

NCP3065, NCV3065

Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect device reliability.

1. This device series contains ESD protection and exceeds the following tests: Pin 1−8: Human Body Model 2000 V per AEC Q100−002; 003 or JESD22/A114; A115 Machine Model Method 200 V

2. This device contains latch−up protection and exceeds 100 mA per JEDEC Standard JESD78.

3. The relation between junction temperature, ambient temperature and Total Power dissipated in IC is T

4. The pins which are not defined may not be loaded by external signals

5. 1 oz copper, 1 in

copper area

Symbol Value Unit

CII

SWC

SWE

SWCE

IPK

TCAP

0 to +40 V

−0.2 to +V

0 to +40 V

−0.6 to +V

0 to +40 V

1.5 A

−0.2 to VCC + 0.2 V

−0.2 to +1.4 V

°C/W

100

°C/W

180

°C/W

STG

J(MAX)

78 14

−65 to +150 °C

+150 °C

°C

−40 to +125

= TA + R

•

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NCP3065, NCV3065

ELECTRICAL CHARACTERISTICS (V

Characteristic

= 5.0 V, T

= −40°C to +125°C, unless otherwise specified)

Conditions Symbol Min Typ Max Unit

OSCILLATOR

Frequency

(VPin 5 = 0 V, CT = 2.2 nF,

= 25°C)

Discharge to Charge Current Ratio (Pin 7 to VCC, TJ = 25°C) I

Capacitor Discharging Current (Pin 7 to VCC, TJ = 25°C) I

Capacitor Charging Current (Pin 7 to VCC, TJ = 25°C) I

Current Limit Sense Voltage (TJ = 25°C) (Note 7) V

OSC

DISCHG

CHG

DISCHG

CHG

IPK(Sense)

110 150 190 kHz

5.5 6.0 6.5 −

1650

275

165 185 235 mV

OUTPUT SWITCH (Note 6)

Darlington Switch Collector to

Emitter Voltage Drop

(ISW = 1.0 A,

= 25°C) (Note 6)

Collector Off−State Current (VCE = 40 V) I

SWCE(DROP)

C(OFF)

1.0 1.3 V

0.01 100

COMPARATOR

Threshold Voltage

TJ = 25°C V

235 mV

TJ = 0 to +85°C ±5 %

= −40°C to +125°C V

Threshold Voltage Line Regulation (VCC = 3.0 V to 40 V) REG

Input Bias Current (Vin = Vth) I

CII in

LiNE

−10 +10 %

−6.0 6.0 mV

−1000 −100 1000 nA

TOTAL DEVICE

Supply Current

(VCC = 5.0 V to 40 V,

CT = 2.2 nF, Pin 7 = V

VPin 5 > Vth, Pin 2 = GND,

7.0 mA

remaining pins open)

Thermal Shutdown Threshold 160 °C

Hysteresis 10 °C

6. Low duty cycle pulse techniques are used during test to maintain junction temperature as close to ambient temperature as possible.

7. The

IPK(Sense)

on comparator response time and di/dt current slope. See the Operating Description section for details.

Current Limit Sense Voltage is specified at static conditions. In dynamic operation the sensed current turn−off value depends

8. NCV prefix is for automotive and other applications requiring site and change control.

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NCP3065, NCV3065

450

400

350

300

250

200

150

FREQUENCY (kHz)

100

0 1 2 3 4 5 6 7 8 9 1011 12 131415161718 1920

Ct, CAPACITANCE (nF) VCC, SUPPLY VOLTAGE (V)

Figure 5. Oscillator Frequency vs. Oscillator

Timing Capacitor

2.4

2.2

2.0

1.8

VCC = 5.0 V I

= 1 A

190

180

170

160

150

140

FREQUENCY (kHz)

130

120

110

Figure 6. Oscillator Frequency vs. Supply

1.25

1.20

1.15

CT = 2.2 nF T

= 25°C

21 34 38

Voltage

VCC = 5.0 V I

= 1 A

402925161273

1.6

1.4

VOLTAGE DROP (V)

1.2

1.0

TJ, JUNCTION TEMPERATURE (°C) TJ, JUNCTION TEMPERATURE (°C)

Figure 7. Emitter Follower Configuration Output

Darlington Switch Voltage Drop vs. Temperature

2.0

1.9

VCC = 5.0 V T

= 25°C

1.8

1.7

1.6

1.5

1.4

1.3

VOLTAGE DROP (V)

1.2

1.1

1.0

IE, EMITTER CURRENT (A) IC, COLLECTOR CURRENT (A)

Figure 9. Emitter Follower Configuration Output

Darlington Switch Voltage Drop vs. Emitter Current

1.10

VOLTAGE DROP (V)

1.05

150100500−50

1.0 150100500−50

Figure 8. Common Emitter Configuration Output Darlington Switch Voltage Drop vs. Temperature

1.5

1.4

1.3

1.2

1.1

1.0

0.9

0.8

VOLTAGE DROP (V)

0.7

0.6

1.51.00.50

0.5

VCC = 5.0 V T

= 25°C

1.51.00.50

Figure 10. Common Emitter Configuration

Output Darlington Switch Voltage Drop vs.

Collector Current

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NCP3065, NCV3065

0.25

0.245

0.24

0.235

0.23

0.225

0.22

, COMPARATOR THRESHOLD VOLTAGE (V)

0.30

0.28

0.26

0.24

0.22

0.20

0.18

VOLTAGE (V)

, CURRENT LIMIT SENSE

0.16

0.14

ipk(sense)

0.12

−10 907050 130

TJ, JUNCTION TEMPERATURE (°C) TJ, JUNCTION TEMPERATURE (°C)

1103010 150−30−50

Figure 11. Comparator Threshold Voltage vs.

Temperature

6.0

5.5

5.0

4.5

0.10 20 95 110

Figure 12. Current Limit Sense Voltage vs.

Temperature

65 80

12550355−10−25−40

4.0

3.5

3.0

, SUPPLY CURRENT (mA)

2.5

2.0 13 18 23 43

VCC, SUPPLY VOLTAGE (V)

CT = 2.2 nF Pin 5, 7 = V Pin 2 = GND

3833288.03.0

Figure 13. Standby Supply Current vs. Supply Voltage

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NCP3065, NCV3065

INTRODUCTION

The NCP3065 is a monolithic power switching regulator optimized for LED Driver applications. Its flexible architecture enables the system designer to directly implement a step−up or step−down topology with a minimum number of external components for driving LEDs. A representative block diagram is shown in Figure 4.

OPERATING DESCRIPTION

The NCP3065 operates as a fixed oscillator frequency output voltage ripple gated regulator. In general, this mode of operation is somewhat analogous to a capacitor charge pump and does not require dominant pole loop compensation for converter stability. The typical operating waveforms are shown in Figure 14. The output voltage waveform shown is for a step−down converter with the ripple and phasing exaggerated for clarity. During initial converter startup, the feedback comparator senses that the output voltage level is below nominal. This causes the output switch to turn on and off at a frequency and duty cycle controlled by the oscillator, thus pumping up the output filter capacitor. When the feedback voltage level reaches nominal

comparator value, the output switch cycle is inhibited. When the load current causes the output voltage to fall below the nominal value feedback comparator enables switching immediately. Under these conditions, the output switch conduction can be enabled for a partial oscillator cycle, a partial cycle plus a complete cycle, multiple cycles, or a partial cycle plus multiple cycles.

Oscillator

The oscillator frequency and off−time of the output switch are programmed by the value of the timing capacitor C Capacitor C

is charged and discharged by a 1 to 6 ratio

internal current source and sink, generating a positive going sawtooth waveform at Pin 3. This ratio sets the maximum t

/(tON+t

) of the switching converter as 6/(6+1) or

OFF

85.7% (typical). The oscillator peak and valley voltage difference is 500 mV typically. To calculate the C

capacitor

value for required oscillator frequency, use the equations found in Figure 22. An online NCP3065 design tool can be found at www.onsemi.com, which adds in selecting component values.

Feedback Comparator Output

IPK Comparator Output

Timing Capacitor, C

Output Switch

Nominal Output Voltage Level

Output Voltage

Off

Startup Operation

Figure 14. Typical Operating Waveforms

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NCP3065, NCV3065

Peak Current Sense Comparator

Under normal conditions, the output switch conduction is initiated by the Voltage Feedback comparator and terminated by the oscillator. Abnormal operating conditions occur when the converter output is overloaded or when feedback voltage sensing is lost. Under these conditions, the I

Current Sense comparator will protect the Darlington

output Switch. The switch current is converted to a voltage by inserting a fractional ohm resistor, R V

and the Darlington output switch. The voltage drop

across R

is monitored by the Current Sense comparator.

, in series with

If the voltage drop exceeds 200 mV (nom) with respect to V

, the comparator will set the latch and terminate the

output switch conduction on a cycle−by−cycle basis. This Comparator/Latch configuration ensures that the Output Switch has only a single on−time during a given oscillator cycle.

turn−off

Resistor

ipk(sense)

The V

Real

IPK(Sense)

di/dt slope

t_delay

Current Limit Sense Voltage threshold is

I through the

Darlington

Switch

specified at static conditions. In dynamic operation the sensed current turn−off value depends on comparator response time and di/dt current slope.

Real V

turn_off

turn−off

+ V

on Rsc resistor

ipk(sense)

) Rsc @ (t_delay @ dińdt)

Typical Ipk comparator response time t_delay is 350 ns. The di/dt current slope is dependent on the voltage difference across the inductor and the value of the inductor. Increasing the value of the inductor will reduce the di/dt slope.

It is recommended to verify the actual peak current in the application at worst conditions to be sure that the max peak current will never get over the 1.5 A Darlington Switch Current max rating.

Thermal Shutdown

Internal thermal shutdown circuitry is provided to protect the IC in the event that the maximum junction temperature is exceeded. When activated, typically at 165°C, the Darlington Output Switch is disabled. The temperature sensing circuit is designed with some hysteresis. The Darlington Switch is enabled again when the chip temperature decreases under the low threshold. This feature is provided to prevent catastrophic failures from accidental device overheating. It is not intended to be used as a replacement for proper heatsinking.

LED Dimming

The COMP pin of the NCP3065 is used to provide dimming capability. In digital input mode the PWM input signal inhibits switching of the regulator and reduces the average current through the LEDs. In analog input mode a PWM input signal is RC filtered and the resulting voltage is summed with the feedback voltage thus reduces the average current through the LEDs. Figure 15 illustrated the linearity of the digital dimming function with a 200 Hz digital PWM. For further information on dimming control refer to application note AND8298.

800

700

600

500

(mA)

400

LED

300

200

100

No Output Capacitor Operation

30 9080

DUTY CYCLE (%)

Figure 15.

24 Vin, Vf = 7.2 V

24 Vin, Vf = 3.6 V

12 Vin, Vf = 3.6 V

1007060504020100

A constant current buck regulator such as the NCP3065 focuses on the control of the current through the load, not the voltage across it. The switching frequency of the NCP3065 is in the range of 100−300 kHz which is much higher than the human eye can detect. This allows us to relax the ripple current specification to allow higher peak to peak values. This is achieved by configuring the NCP3065 in a continuous conduction buck configuration with low peak to peak ripple thus eliminating the need for an output filter capacitor. The important design parameter is to keep the peak current below the maximum current rating of the LED. Using 15% peak to peak ripple results in a good compromise between achieving max average output current without exceeding the maximum limit. This saves space and reduces part count for applications that require a compact footprint. (Example: See Figure 17) See application note AND8298 for more information.

Output Switch

The output switch is designed in a Darlington configuration. This allows the application designer to operate at all conditions at high switching speed and low voltage drop. The Darlington Output Switch is designed to switch a maximum of 40 V collector to emitter voltage and current up to 1.5 A.

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NCP3065, NCV3065

APPLICATIONS

Figures 16 through 24 show the simplicity and flexibility of the NCP3065. Two main converter topologies are demonstrated with actual test data shown below each of the circuit diagrams.

(See Notes 9, 10, 11) Step−Down Step−Up

off

L(avg)

pk (Switch)

ripple(pp)

Vin* V

L(avg)

pk (Switch)

out

SWCE

off

out

0.20

SWCE

8 f C

) V

) 1

)

* V

) (ESR)

out

CT+

Figure 16 gives the relevant design equations for the key parameters. Additionally, a complete application design aid for the NCP3065 can be found at www.onsemi.com.

) VF* V

out

Vin* V

off

) 1

off

osc

* 343 @ 10

*12

Vin* V

tonI

[

out

off

L(avg)

0.20

pk (Switch)

SWCE

out

) DIL@ ESR

381.6 @ 10

SWCE

) 1

)

out

9. V

10.V

11.The calculated t

The Following Converter Characteristics Must Be Chosen:

− Darlington Switch Collector to Emitter Voltage Drop, refer to Figures 7, 8, 9 and 10.

SWCE

− Output rectifier forward voltage drop. Typical value for 1N5819 Schottky barrier rectifier is 0.4 V.

must not exceed the minimum guaranteed oscillator charge to discharge ratio.

on/toff

ńR

ref

) 1

sense

ńR

ref

sense

) 1

Vin − Nominal operating input voltage. V

− Desired output voltage.

out

− Desired output current.

out

− Desired peak−to−peak inductor ripple current. For maximum output current it is suggested that DIL be chosen to be

less than 10% of the average inductor current I set by R

. If the design goal is to use a minimum inductance value, let DIL = 2(I

. This will help prevent I

L(avg)

pk (Switch)

from reaching the current limit threshold

). This will proportionally reduce

L(avg)

converter output current capability.

f − Maximum output switch frequency. V

ripple(pp)

value since it will directly affect line and load regulation. Capacitor C

− Desired peak−to−peak output ripple voltage. For best performance the ripple voltage should be kept to a low should be a low equivalent series resistance (ESR)

electrolytic designed for switching regulator applications.

Figure 16. Design Equations

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6x 1R0 ±1%R

0R10

R1 R2 R3 R4 R5 R6 R7

+VIN

GND

+VAUX

ON/OFF

1206 1206 1206 1206 1206 1206 1206

0.1 mF

BC807−LT1G

Q1 Q2

R11

Figure 17. Buck Demo Board with External Switch Application Schematic

220 mF / 50 V

BC817−LT1G

NCP3065, NCV3065

MMBT3904LT1G

R15

1 k

N.C. SWC

10 k

COMP

NCP3065

SOIC8

R14 NU

R13 NU

SWE

TCAP

GND

NTF2955

MMSD4148

15 k

1.8 nF

MBRS140LT3G

C5 100 pF

R10

1 k0805

470 mH

1208

R12

SENSE

0.1 mF

±1%

+LED

−LED

GND

This design illustrates the NCP3065 being used as a PFET controller, the design has been optimized for continuous current operation with low ripple which allows the output

efficiency with 1 and 2 LEDs and output currents of 350 mA and 700 mA. Additional data and design information can be found of this design in Application Note AND8298.

filter capacitor to be eliminated. Figure 20 illustrates the

Value of Components

Name Value

C1, C4 100 nF, Ceramic Capacitor, 1206

C3 1.8 nF, Ceramic Capacitor, 0805

C5 100 pF, Ceramic Capacitor, 0805

D1 1 A, 40 V Schottky Rectifier

D2 MMSD4148

Q4 NTF2955, P−MOSFET, SOT223

NOTE: R

SENSE

220 mF, 50 V, Electrolytic Capacitor

470 mH, DO5022P−474ML Coilcraft Inductor

is used to select LED output current, for 350 mA use 680 mW, for 700 mA use 330 mW and for 1000 mA use 220 mW

Test Results (without output capacitor)

Test Condition Results

Line Regulation Vin = 9 V to 35 V, Io = 350 mA 12 mA

Load Regulation Vin = 12 V, Io = 350 mA, Vo = 3 V to 8 V 13 mA

Output Ripple Vin = 9 V to 35 V, Io = 350 mA < 15% I

Efficiency Vin = 12 V, Io = 350 mA, V

= 3 to 8 V > 75%

OUT

Name Value

Q5 MMBT3904LT1G, SOT23

R8 15 k, resistor 0805

R10, R15

R11

R12 R

U1 NCP3065, SOIC8

100 mW, 0.5 W

10 kW, resistor 0805

1 kW, resistor 0805

1.2 kW, resistor 0805

±1%, 1206

SENSE

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NCP3065, NCV3065

Figure 18. 1.5 A Buck Demoboard Layout

= 7.2 V, Output Cap 100 mF

OUT

EFFICIENCY (%)

= 3.6 V, Output Cap 100 mF

OUT

4 8 12 16 20 28 36

24 32

VIN, INPUT VOLTAGE (V)

Figure 20. Efficiency vs. Input Voltage for the 1.5 A

Buck Demo Board at I

= 350 mA, T

out

= 255C, with

100 mF Output Capacitor

= 7.2 V, No Output Cap

OUT

EFFICIENCY (%)

= 3.6 V, No Output Cap

OUT

4 8 12 16 20 28 36

24 32

VIN, INPUT VOLTAGE (V)

Figure 19. Efficiency vs. Input Voltage for the 1.5 A

Buck Demo Board at I

= 700 mA, T

out

= 255C,

Without Output Capacitor

OUT

EFFICIENCY (%)

4 8 12 16 20 28 36

= 7.2 V, Output Cap 100 mF

OUT

= 3.6 V, Output Cap 100 mF

, INPUT VOLTAGE (V)

24 32

Figure 21. Efficiency vs. Input Voltage for the 1.5 A Buck Demo Board at I

= 700 mA, T

out

= 255C, with

100 mF Output Capacitor

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0R15

6x 1R0 ±1%R

R1 R2 R3 R4 R5 R6 R7

+VIN

0.1 mF

GND

+VAUX

BC807−LT1G

Q1 Q2

R10

ON/OFF

1k2

NCP3065, NCV3065

100 mH

N.C. SWC

220 mF / 50 V

COMP

NCP3065

1k0

R11

BC817−LT1G

Figure 22. Boost Demo Board Application Schematic

SWE

TCAP

GND

SENSE

−LED

MBRS140LT3G

2.2 nF

0.1 mF

MM3Z36VT1G

100 mF /

50 V

+VOUT

GND

Value of Components

Name Value

100 mF/50 V, Electrolytic Capacitor

C2, C5 100 nF, Ceramic Capacitor, 1206

220 mF/50 V, Electrolytic Capacitor

C4 2.2 nF, Ceramic Capacitor, 0805

D1 MBRS140LT3G, Schottky diode

D2 MMSZ36VT1G, Zener diode

100 mH, DO3340P−104ML Coilcraft Inductor

Test Results

Test Condition Results

Line Regulation Vin = 10 V to 20 V, Vo = 22 V, I

Output Ripple Vin = 8 V to 20 V, Vo = 22 V, I

Efficiency Vin = 10 to 20 V, I

= 350 mA > 83 %

OAVG

Name Value

Q2 BC817−LT1G, SOT23

150 mW, resistor 0.5 W

R8 1 k, resistor 0805

R9 Load current sense resistor, 1206

R10 1.2 k, resistor 0805

U1 NCP3065, SOIC8

= 350 mA 25 mA

OAVG

= 350 mA 50 mA

OAVG

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Figure 23. Boost Demoboard Layout

NCP3065, NCV3065

EFFICIENCY (%)

77 75

Figure 24. Efficiency vs. Input Voltage for the

OUT

16 20

14 22

VIN, INPUT VOLTAGE (V)

Boost Demo Board at I

= 350 mA,

OUT

1812108

= 22 V (6xLED with VF = 3.6 V), T

= 255C

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6x 1R0 ±1%R

0R04

R1 R2 R3 R4 R5 R6 R7

+VIN

GND

+VAUX

ON/OFF

1206 1206 1206 1206 1206 1206

0.1 mF

BC807−LT1G

Q1 Q2

R11

1k2

0805

Figure 25. Buck Demoboard with External Switch Application Schematic

1 mF / 50 V

220 mF / 50 V

BC817−LT1G

NCP3065, NCV3065

MMBT3904LT1G

R15

1 k

N.C. SWC

0.1 mF

10 k 0805

COMP

NCP3065

SOIC8

R14 NU

R13

SWE

TCAP

GND

MTB30P06V

MMSD4148

15 k

1.8 nF

C5 100 pF

R10

PF0504.223NL

1206

MBRS140LT3G

1 k0805

R16 0R15 ±1%

0.1 mF

R12 0R15 ±1%

+LED

220 mF /

50 V

−LED

GND

Value of Components

Name Value

C1, C4, C8 100 nF, Ceramic Capacitor, 1206

C2, C6

C3 2.2 nF, Ceramic Capacitor, 0805

C5 100 pF, Ceramic Capacitor, 0805

D1 MBRS540LT3G, Schottky Diode

D2 MMSD4148T1G, Diode

Q2 BC817−LT1G, SOT23

100 mF, 50 V, Electrolytic Capacitor

220 mF, 50 V, Electrolytic Capacitor

1 mF / 50 V, Ceramic Capacitor, 1206

22 mH

Name Value

Q4 MTB30P06V, P−MOS transistor

Q5 MMBT3904LT1G

R8 6k8, Resistor 0805

R9 10k, Resistor 0805

R10 1k, Resistor 0805

R11 1k2, Resistor 0805

R12, R16

U1 NCP3065, SOIC8

40 mW, Resistor 0.5 W

150 mW, Resistor 0.5 W

Test Results

Test Condition Results

Line Regulation Vin = 8 V to 35 V, Io = 3000 mA < 6%

Output Ripple Vin = 12 V, Io = 3000 mA < 6%

Efficiency Vin = 12 V, Io = 3000 mA > 78%

Short Circuit Current

Vin = 12 V, Rload = 0.15 W

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Figure 26. 3 A Buck Demoboard Layout

NCP3065, NCV3065

90 88

86 84

EFFICIENCY (%)

68 66

Figure 27. Efficiency vs. Input Voltage for the

16 20

14 36

VIN, INPUT VOLTAGE (v)

3 A Buck Demo Board at I

OUT

22 3024 28 3226 34

1812108

= 4 V, T

= 255C

OUT

= 3 A,

ORDERING INFORMATION

Device Package Shipping

NCP3065MNTXG DFN−8

(Pb−Free)

NCP3065PG PDIP−8

(Pb−Free)

NCP3065DR2G SOIC−8

(Pb−Free)

NCV3065MNTXG DFN−8

(Pb−Free)

NCV3065PG PDIP−8

(Pb−Free)

NCV3065DR2G SOIC−8

(Pb−Free)

†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging

Specifications Brochure, BRD8011/D.

4000 Units / Tape & Reel

50 Units / Rail

2500 Units / Tape & Reel

4000 Units / Tape & Reel

50 Units / Rail

2500 Units / Tape & Reel

†

http://onsemi.com

NOTE 2

−T−

SEATING PLANE

−B−

−A−

0.13 (0.005) B

NCP3065, NCV3065

PACKAGE DIMENSIONS

8 LEAD PDIP

CASE 626−05

ISSUE L

NOTES:

1. DIMENSION L TO CENTER OF LEAD WHEN FORMED PARALLEL.

2. PACKAGE CONTOUR OPTIONAL (ROUND OR SQUARE CORNERS).

3. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982.

DIM MIN MAX MIN MAX

A 9.40 10.16 0.370 0.400 B 6.10 6.60 0.240 0.260 C 3.94 4.45 0.155 0.175 D 0.38 0.51 0.015 0.020 F 1.02 1.78 0.040 0.070 G 2.54 BSC 0.100 BSC H 0.76 1.27 0.030 0.050 J 0.20 0.30 0.008 0.012 K 2.92 3.43 0.115 0.135 L 7.62 BSC 0.300 BSC M --- 10 --- 10 N 0.76 1.01 0.030 0.040

STYLE 1:

PIN 1. AC IN

2. DC + IN

3. DC - IN

4. AC IN

5. GROUND

6. OUTPUT

7. AUXILIARY

8. V

INCHESMILLIMETERS

http://onsemi.com

−Y−

−Z−

NCP3065, NCV3065

PACKAGE DIMENSIONS

SOIC−8 NB

CASE 751−07

ISSUE AH

−X−

0.25 (0.010) Z

SXS

0.25 (0.010)

SEATING PLANE

0.10 (0.004)

X 45

NOTES:

1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982.

2. CONTROLLING DIMENSION: MILLIMETER.

3. DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION.

4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE.

5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION.

6. 751−01 THRU 751−06 ARE OBSOLETE. NEW STANDARD IS 751−07.

MILLIMETERS

DIMAMIN MAX MIN MAX

4.80 5.00 0.189 0.197

B 3.80 4.00 0.150 0.157 C 1.35 1.75 0.053 0.069 D 0.33 0.51 0.013 0.020 G 1.27 BSC 0.050 BSC H 0.10 0.25 0.004 0.010

J 0.19 0.25 0.007 0.010 K 0.40 1.27 0.016 0.050 M 0 8 0 8

____

N 0.25 0.50 0.010 0.020

S 5.80 6.20 0.228 0.244

INCHES

SOLDERING FOOTPRINT*

1.52

0.060

7.0

0.275

0.6

0.024

*For additional information on our Pb−Free strategy and soldering

details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.

4.0

0.155

1.270

0.050

SCALE 6:1

inches

http://onsemi.com

IDENTIFICATION

SEATING

PLANE

PIN ONE

C0.10

C0.08

C0.15

TOP VIEW

C0.15

SIDE VIEW

NCP3065, NCV3065

PACKAGE DIMENSIONS

8 PIN DFN, 4x4

CASE 488AF−01

ISSUE B

NOTES:

NOTE 3

0.10 C

0.05 C

8X L

BOTTOM VIEW

(A3)

1. DIMENSIONS AND TOLERANCING PER ASME Y14.5M, 1994.

2. CONTROLLING DIMENSION: MILLIMETERS.

3. DIMENSION b APPLIES TO PLATED TERMINAL AND IS MEASURED BETWEEN

0.25 AND 0.30 MM FROM TERMINAL.

4. COPLANARITY APPLIES TO THE EXPOSED PAD AS WELL AS THE TERMINALS.

MILLIMETERS

DIM MIN MAX

A 0.80 1.00 A1 0.00 0.05 A3 0.20 REF

b 0.25 0.35

D 4.00 BSC D2 1.91 2.21

E 4.00 BSC E2 2.09 2.39

e 0.80 BSC

K 0.20 −−−

L 0.30 0.50

SOLDERING FOOTPRINT*

4.30

2.21

2.39

0.35

DIMENSIONS: MILLIMETERS

*For additional information on our Pb−Free strategy and soldering

details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.

ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others. SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer. This literature is subject to all applicable copyright laws and is not for resale in any manner.

0.63

0.40

0.80

PITCH

2.75

PUBLICATION ORDERING INFORMATION

LITERATURE FULFILLMENT:

Literature Distribution Center for ON Semiconductor P.O. Box 5163, Denver, Colorado 80217 USA

Phone: 303−675−2175 or 800−344−3860 Toll Free USA/Canada Fax: 303−675−2176 or 800−344−3867 Toll Free USA/Canada Email: orderlit@onsemi.com

N. American Technical Support: 800−282−9855 Toll Free

USA/Canada

Europe, Middle East and Africa Technical Support:

Phone: 421 33 790 2910

Japan Customer Focus Center

Phone: 81−3−5773−3850

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ON Semiconductor Website: www.onsemi.com

Order Literature: http://www.onsemi.com/orderlit

For additional information, please contact your local Sales Representative

NCP3065/D

ON Semiconductor NCP3065, NCV3065 Technical data

Specifications and Main Features

Frequently Asked Questions

User Manual