ON Semiconductor NCP1050, NCP1051, NCP1052, NCP1053, NCP1054 Technical data

查询NCP1050P100供应商

NCP1050, NCP1051,
NCP1052, NCP1053,
NCP1054, NCP1055

Monolithic High Voltage
Gated Oscillator Power
Switching Regulator

The NCP1050 through NCP1055 are monolithic high voltage
regulators that enable end product equipment to be compliant with low
standby power requirements. This device series combines the required
converter functions allowing a simple and economical power system
solution for office automation, consumer, and industrial products.
These devices are designed to operate directly from a rectified AC line
source. In flyback converter applications they are capable of providing
an output power that ranges from 6.0 W to 40 W with a fixed AC input
of 100 V, 115 V, or 230 V, and 3.0 W to 20 W with a variable AC input
that ranges from 85 V to 265 V.

This device series features an active startup regulator circuit that
eliminates the need for an auxiliary bias winding on the converter
transformer, fault detector and a programmable timer for converter
overload protection, unique gated oscillator c onfiguration f or e xtremely
fast loop response with double pulse suppression, power switch current
limiting, input undervoltage lockout with hysteresis, thermal shutdown,
and auto restart fault detection. These devices are available in
economical 8−pin dual−in−line and 4−pin SOT−223 packages.

Features

• Startup Circuit Eliminates the Need for Transformer Auxiliary Bias

Winding

• Optional Auxiliary Bias Winding Override for Lowest Standby

Power Applications

• Converter Output Overload and Open Loop Protection

• Auto Restart Fault Protection

• IC Thermal Fault Protection

• Unique, Dual Edge, Gated Oscillator Configuration for Extremely

Fast Loop Response

• Oscillator Frequency Dithering with Controlled Slew Rate Driver for

Reduced EMI

• Low Power Consumption Allowing European Blue Angel Compliance

• On−Chip 700 V Power Switch Circuit and Active Startup Circuit

• Rectified AC Line Source Operation from 85 V to 265 V

• Input Undervoltage Lockout with Hysteresis

• Oscillator Frequency Options of 44 kHz, 100 kHz, 136 kHz

T ypical Applications

• AC−DC Converters

• Wall Adapters

• Portable Electronic Chargers

• Low Power Standby and Keep−Alive Supplies

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MARKING

DIAGRAMS

8

DIP−8

8

1

Pin: 1. V

4

1

X = Current Limit (0, 1, 2, 3, 4, 5)
Z = Oscillator Frequency (A, B, C)
A = Assembly Location
WL, L = Wafer Lot
YY, Y = Year
WW, W = Work Week

ORDERING INFORMATION

See detailed ordering and shipping information on page 22 of
this data sheet.

CASE 626A

P SUFFIX

2. Control Input
3, 7−8. Ground

4. No Connection

5. Power Switch Drain

Pin: 1. V

CC

SOT−223

CASE 318E

ST SUFFIX

CC

2. Control Input

3. Power Switch Drain

4. Ground

NCP105XZ

AWL

YYWW

1

4

N5XZ

ALYW

1

 Semiconductor Components Industries, LLC, 2003

July, 2003 − Rev. 7

1 Publication Order Number:

NCP1050/D

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

AC Line
Input

+

Snubber

+

Converter
DC Output

+

Power Switch Circuit Output

V

CC

+

1

Startup & V

CC

Regulator Circuit

5

Power

Fault Detector

Switch
Circuit

Control Input

2

Oscillator &

Gating Logic

Ground

3, 7−8

Figure 1. T ypical Application

Pin Function Description

Pin

(SOT−223)

1 1 V

2 2 Control Input The Power Switch Circuit is turned off when a current greater than approximately

4 3, 7, 8 Ground This pin is the control circuit and Power Switch Circuit ground. It is part of the

− 4 No Connection
3 5 Power Switch

Pin

(DIP−8)

Function Description

CC

This is the positive supply voltage input. During startup, power is supplied to this input
from Pin 5. When V

reaches VCC(on), the Startup Circuit turns off and the output is

CC

allowed to begin switching with 1.0 V hysteresis on the V
connected to this pin programs fault timing and frequency modulation rate.

50 A is drawn out of or applied to this pin. A 10 V clamp is built onto the chip to
protect the device from ESD damage or overvoltage conditions.

integrated circuit lead frame.

This pin is designed to directly drive the converter transformer primary, and internally

Drain

connects to Power Switch and Startup Circuit.

pin. The capacitance

CC

−

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2

AC Line
Input

V

+

VCC Bypass/
Fault Timing/

Sweep

V

CO

Control

CC

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

Startup

Circuit

Turn On

Latch
R

Snubber

S

Q

R

Power Switch Circuit Output

Internal

Bias

Fault
Latch

Turn Off

Latch

48 A

10 V

V

CC

+

Startup/VCC Reg

+

−

+

7.5/8.5 V

Undervoltage
Lockout

−
+

+

4.5 V

= 10 A

I

H

Fault

Detector

Thermal

Shutdown

Oscillator

Driver

+

+

Converter
DC Output

−

Power
Switch
Circuit

Control
Input

10 V

48 A

2.6 V

3.3 V

+

+

I

= 10 A

H

Q

S

+

Current Limit
Comparator

−

Ground

Figure 2. Representative Block Diagram

Ck

Q

R

Leading Edge

Blanking

+

R

SENSE

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3

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

f

OSC (high)

8.5 V
f

V

CC

7.5 V

OSC (low)

Oscillator Duty

Oscillator Clock

I

Circuit Gate Drive

Primary Current

Cycle

CONTROL, SINK

Power Switch

47.5 A

37.5 A

0 A

Leading Edge On

Duty Cycle Off

Leading Edge On

Feedback Off

Delay On

Duty Cycle Off

Leading Edge On

Duty Cycle Off

No Second

Pulse

Leading Edge On

Current Limit Off

Current Limit
Threshold

Current Limit
Propagation
Delay

Figure 3. Timing Diagram for Gated Oscillator with Dual Edge PWM

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4

V

Hysteretic Regulation

V

V

CC

V

CC(reset)

6.3 mA

I

(start)

I

CC1

I

CC

0 mA

47.5 A

37.5 A

I

CONTROL, SINK

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

I

, Current Measurement

CC(on)

CC(off)

0 V

0 mA

I

CC2

I

CC3

I

(start)

0 A

CC1

I

, Current Measurement

CC2

I

, Current Measurement

CC3

V

(pin 5)

Fault Applied

Fault Removed

Figure 4. Non−Latching Fault Condition Timing Diagram

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5

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

MAXIMUM RATINGS (Note 1)

Rating Symbol Value Unit

Power Switch and Startup Circuit

Drain Voltage Range
Drain Current Peak During Transformer Saturation

Power Supply/VCC Bypass and Control Input

Voltage Range
Current

Thermal Characteristics

P Suffix, Plastic Package Case 626A−01

Junction−to−Lead
Junction−to−Air, 2.0 Oz. Printed Circuit Copper Clad

0.36 Sq. Inch

1.0 Sq. Inch

ST Suffix, Plastic Package Case 318E−04

Junction−to−Lead
Junction−to−Air, 2.0 Oz. Printed Circuit Copper Clad

0.36 Sq. Inch

1.0 Sq. Inch
Operating Junction Temperature T
Storage Temperature T

1. Maximum Ratings are those values beyond which damage to the device may occur. Exposure to these conditions or conditions beyond those
indicated may adversely affect device reliability. Functional operation under absolute maximum−rated conditions is not implied. Functional
operation should be restricted to the Recommended Operating Conditions.
A.This device series contains ESD protection and exceeds the following tests:

Pins 1−3: Human Body Model 2000 V per MIL−STD−883, Method 3015.

Machine Model Method 400 V.

Pin 5: Human Body Model 1000 V per MIL−STD−883, Method 3015.

Machine Model Method 400 V.

Pin 5 is connected to the power switch and start−up circuits, and is rated only to the max voltage of the part, or 700 V.

B.This device contains Latch−up protection and exceeds 100 mA per JEDEC Standard JESD78.

V

DS

I

DS(pk)

V

I

max

R



R



R



R



stg

0.3 to 700

Max

2.0 I

lim

IR

0.3 to 10

100

V
A

V

mA

°C/W

JL
JA

9.0

77
60

JL
JA

14

74
55

J

40 to +150 °C
65 to +150 °C

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6

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

ELECTRICAL CHARACTERISTICS (V

= 8.0 V, for typical values TJ = 25°C, for min/max values, TJ is the operating junction

CC

temperature range that applies (Note 2), unless otherwise noted.)

Characteristics

OSCILLATOR

Frequency (V

= 25°C:

T

J

= 7.5 V)

CC

A Suffix Device
B Suffix Device
C Suffix Device

= T

T

to T

J

low

high

A Suffix Device
B Suffix Device
C Suffix Device

Frequency (VCC = 8.5 V)

T

= 25°C:

J

A Suffix Device
B Suffix Device
C Suffix Device

= T

T

to T

J

low

high

A Suffix Device
B Suffix Device

C Suffix Device
Frequency Sweep (VCC = 7.5 V to 8.5 V, TJ = 25°C) %f
Maximum Duty Cycle D

CONTROL INPUT

Lower Window Input Current Threshold

Switching Enabled, Sink Current Increasing
Switching Disabled, Sink Current Decreasing

Upper Window Input Current Threshold

Switching Enabled, Source Current Increasing
Switching Disabled, Source Current Decreasing

Control Window Input Voltage

sink
source

= 25 A)

= 25 A)

Lower (I
Upper (I

2. Tested junction temperature range for the NCP105X series:
= −40°CT

T

low

= +125°C

high

Symbol Min Typ Max Unit

f

OSC(low)

f

OSC(high)

OSC

(max)

I

off(low)

I

on(low)

I

off(high)

I

on(high)

V

low

V

high

38
87

119

37
84

113

41
93

126

39
90

120

42.5
97

132

−

−

−

45.5

103
140

−

−

−

47
107
145

47
107
145

50
113
154

50
113
154

− 5.0 − %

74 77 80 %

−58

−50

1.1

4.2

37
25

−47.5

−37.5

47.5

37.5

1.35

4.6

−37

−25

58

50

1.6

5.0

kHz

kHz

A

V

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7

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

ELECTRICAL CHARACTERISTICS (V

= 8.0 V, for typical values TJ = 25°C, for min/max values, TJ is the operating junction

CC

temperature range that applies (Note 3), unless otherwise noted.)

Characteristics

Symbol Min Typ Max Unit

POWER SWITCH CIRCUIT

Power Switch Circuit On−State Resistance

NCP1050, NCP1051, NCP1052 (I

= 25°C

T

J

T

= 125°C

J

NCP1053, NCP1054, NCP1055 (I

T

= 25°C

J

= 125°C

T

J

= 50 mA)

D

= 100 mA)

D

Power Switch Circuit & Startup Breakdown Voltage

= 100 A, TA = 25°C)

(I

D(off)

Power Switch Circuit & Startup Circuit Off−State Leakage Current

= 650 V) TJ = 25°C

(V

DS

= 650 V) TJ = 125°C

(V

DS

Switching Characteristics (RL = 50 , VDS set for ID = 0.7 I

Iim

)

R

V

I

Turn−on Time (90% to 10%)
Turn−off Time (10% to 90%)

CURRENT LIMIT AND THERMAL PROTECTION

Current Limit Threshold (T

= 25°C) (Note 6)

J

NCP1050
NCP1051
NCP1052
NCP1053
NCP1054

NCP1055
Conversion Power Deviation (TJ = 25°C) (Note 7) I2f
Propagation Delay, Current Limit Threshold to Power Switch Circuit Output

NCP1050, NCP1051, NCP1052

NCP1053, NCP1054, NCP1055
Thermal Protection (VCC = 8.6 V) (Note 3, 4, 5)

Shutdown (Junction Temperature Increasing)

Hysteresis (Junction Temperature Decreasing)

STARTUP CONTROL

Startup/V

Startup Threshold/V

Minimum Operating/V

Regulation

CC

Regulation Peak (VCC Increasing)

CC

Valley Voltage After Turn−On

CC

V

V

Hysteresis
Undervoltage Lockout Threshold Voltage, VCC Decreasing V

CC(reset)

Startup Circuit Output Current (Power Switch Circuit Output = 40 V)

= 0 V

V

CC

T

= 25°C

J

= −40 to 125°C

T

J

V

= V

CC

= 25°C

T

J

= −40 to 125°C

T

J

Minimum Start−up Drain Voltage (I

CC(on)

− 0.2 V

= 0.5 mA, VCC = V

start

− 0.2 V) V

CC(on)

start(min)

Output Fault Condition Auto Restart

(V

Capacitor = 10 F, Power Switch Circuit Output = 40 V)

CC

Average Switching Duty Cycle

Frequency

3. Tested junction temperature range for the NCP105X series:
= −40°CT

T

low

4. Maximum package power dissipation limits must be observed.

= +125°C

high

5. Guaranteed by design only.

6. Adjust di/dt to reach I

7. Consult factory for additional options including test and trim for output power accuracy.

in 4.0 sec.

lim

DS(on)

(BR)DS

DS(off)

t

on

t

off

I

lim

OSC

t

PLH

T

sd

T

H

CC(on)
CC(off)

V

H

I

start

D

rst

f

rst



−

−

−

−

22
42

10
23

30
55

15
28

700 − − V

A

−

−

25
15

40
80

ns

−

−

20
10

−

−

mA

93
186
279
372
493
632

100
200
300
400
530
680

107
214
321
428
567
728

− 0 10 %A2Hz
ns

−

−

135
160

−

−
°C

140

−

160

75

−

−

V

8.0

7.0

−

8.5

7.5

1.0

9.0

8.0

−

4.0 4.5 5.0 V
mA

5.4

4.5

4.6

3.5

6.3

5.6

−

8.0

6.6

7.2

−

7.0

− 13.4 20 V

−

−

6.0

3.5

−

−

%

Hz

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8

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

ELECTRICAL CHARACTERISTICS (V

= 8.0 V, for typical values TJ = 25°C, for min/max values, TJ is the operating junction

CC

temperature range that applies (Note 8), unless otherwise noted.)

Characteristics

TOTAL DEVICE

Power Supply Current After UVLO Turn−On (Note 9)

Power Switch Circuit Enabled

NCP1050, NCP1051, NCP1052

A Suffix Device
B Suffix Device
C Suffix Device

NCP1053, NCP1054, NCP1055

A Suffix Device
B Suffix Device
C Suffix Device

Power Switch Circuit Disabled

Non−Fault Condition
Fault Condition

8. Tested junction temperature range for the NCP105X series:
= −40°CT

T

low

9. See Non−Latching Fault Condition Timing Diagram in Figure 4.

= +125°C

high

Symbol Min Typ Max Unit

mA

I

CC1

I

CC2

I

CC3

0.35

0.40

0.40

0.40

0.45

0.50

0.35

0.10

0.45

0.50

0.525

0.50

0.575

0.65

0.45

0.175

0.55

0.60

0.65

0.60

0.70

0.80

0.55

0.25

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9

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

46

45

44

43

42

41

OSCILLATOR FREQUENCY (kHz)

40

VCC = V

CC(on)

−25 25 50 150125−50 0 75 100

Figure 5. Oscillator Frequency (A Suffix)

142
140
138

136
134
132
130
128
126

OSCILLATOR FREQUENCY (kHz)

124

VCC = V

VCC = V

−25 25 50 150125−50 0 75 100

Figure 7. Oscillator Frequency (C Suffix)

VCC = V

CC(off)

TEMPERATURE (°C)

versus Temperature

CC(on)

CC(off)

TEMPERATURE (°C)

versus Temperature

104

VCC = V

102

100

98

VCC = V

96

94

OSCILLATOR FREQUENCY (kHz)

92

CC(on)

CC(off)

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

Figure 6. Oscillator Frequency (B Suffix)

versus Temperature

9
8
7
6
5
4
3
2

FREQUENCY SWEEP (kHz)

1
0

−25 25 50 150125−50 0 75 100

136 kHz

100 kHz

44 kHz

TEMPERATURE (°C)

Figure 8. Frequency Sweep versus

Temperature

77.6

77.4

77.2

77.0

76.8

76.6

MAXIMUM DUTY CYCLE (%)

76.4

76.2

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

Figure 9. Maximum Duty Cycle versus

Temperature

55

50

45

40

35

30

SINK CONTROL CURRENT THRESHOLD (A)

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10

CURRENT RISING

CURRENT FALLING

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

Figure 10. Lower Window Control Input

Current Thresholds versus Temperature

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

50

46

42

38

34

30

−50 25 50 1501250 100

−25 75
TEMPERATURE (°C)

SOURCE CONTROL CURRENT THRESHOLD (A)

Figure 11. Upper Window Control Input

CURRENT RISING

CURRENT FALLING

Current Thresholds versus Temperature

4.66

4.64

4.62

4.60

4.58

4.56

CLAMP VOLTAGE (V)

4.54

4.52

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

I

SOURCE

Figure 13. Control Input Upper Window Clamp

Voltage versus Temperature

= 25 A

1.39

1.38

1.37

1.36

1.35

1.34
I

1.33

1.32

1.31

CLAMP VOLTAGE (V)

1.30

1.29

1.28

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

SINK

= 25 A

Figure 12. Control Input Lower Window Clamp

Voltage versus Temperature

45
40

35
30
25
20
15

ON RESISTANCE ()

10

5
0

−25 25 50 150125−50 0 100

NCP1050,1,2

(I

= 50 mA)

D

75

TEMPERATURE (°C)

Figure 14. On Resistance versus T emperature

NCP1053,4,5

(I

= 100 mA)

D

120

100

80

60

TJ = −40°C

40

TJ = 25°C

LEAKAGE CURRENT (A)

20

0

100 300 700500 900

TJ = 125°C

200 400 8000 600

APPLIED VOLTAGE (V)

Figure 15. Power Switch and Startup Circuit

Leakage Current versus Voltage

100

TJ = 25°C

NCP1053,4,5

10

NCP1050,1,2

CAPACITANCE (pF)

1

100 300 7006000 200 400 500

APPLIED VOLTAGE (V)

Figure 16. Power Switch and Startup Circuit
Output Capacitance versus Applied Voltage

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11

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

1.02

1.00

0.98

0.96

0.94

0.92

0.90

NORMALIZED CURRENT LIMIT

0.88

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

Figure 17. Normalized Peak Current Limit

versus Temperature

4.56

4.54

4.52

4.50

4.48

4.46

4.44

4.42

4.40

4.38

4.36

UNDERVOLTAGE THRESHOLD (V)

4.34

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

Figure 19. Undervoltage Lockout Threshold

versus Temperature

8.6

8.4

8.2

8.0

7.8

7.6

SUPPLY THRESHOLD (V)

7.4

7.2

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

STARTUP

THRESHOLD

V

CC(on)

MINIMUM

OPERATING

THRESHOLD

V

CC(off)

Figure 18. Supply V oltage Thresholds versus

Temperature

8
7
6
5
4
3
2

START CURRENT (mA)

1
0

−25 25 50 150125−50 0 75 100

VCC = 0 V

VCC = 8.3 V

V

= 20 V

PIN 5

TEMPERATURE (°C)

Figure 20. Start Current versus Temperature

7

6

5

4

3

2

STARTUP CURRENT (mA)

1
0

134 9702 56

SUPPLY VOLTAGE (V)

Figure 21. Startup Current versus Supply

Voltage

TJ = 25°C
V

= 20 V

PIN 5

8

6

4

2

0

STARTUP CURRENT (mA)

8

−2

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12

VCC = 0 V

VCC = 8 V

TJ = 25°C

10 10001 100

PIN 5 VOLTAGE (V)

Figure 22. Startup Current versus Pin 5

Voltage

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

0.55
136 kHz

0.50
100 kHz

0.45

44 kHz

0.40

SUPPLY CURRENT (mA)

0.35

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

Figure 23. Supply Current versus Temperature

(NCP1050/1/2)

0.48

0.47

0.46

0.45

0.44

0.43

SUPPLY CURRENT (mA)

0.42

0.41

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

Figure 25. Supply Current When Switching

Disable versus T emperature

0.70

0.65

0.60

0.55

0.50

0.45

SUPPLY CURRENT (mA)

0.40

0.35

−25 25 50 150125−50 0 75 100

136 kHz

100 kHz

44 kHz

TEMPERATURE (°C)

Figure 24. Supply Current versus Temperature

(NCP1053/4/5)

0.21

0.20

0.19

0.18

0.17

0.16

0.15

0.14

SUPPLY CURRENT (mA)

0.13

0.12

−25 25 50 150125−50 0 75 100
TEMPERATURE (°C)

Figure 26. Supply Current in Fault Condition

versus Temperature

14.0

13.9

13.8

13.7

13.6

13.5

13.4

13.3

SUPPLY VOLTAGE (V)

13.2

13.1

13.0

−25 25 50 150125−50 0 75 100

CONDITION:
V

pin = 1 F to ground

CC

Control pin = open
Drain pin = 1 k to Power Supply,
Increase Voltage Until Switching

TEMPERATURE (°C)

Figure 27. Supply V oltage versus Temperature

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13

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

OPERATING DESCRIPTION

Introduction

The NCP105X series represents a new higher level of
integration by providing on a single monolithic chip all of
the active power, control, logic, and protection circuitry
required to implement a high voltage flyback converter and
compliance with very low standby power requirements for
modern consumer electronic power supplies. This device
series is designed for direct operation from a rectified 240
VAC line source and requires minimal external components
for a complete cost sensitive converter solution. Potential
markets include cellular phone chargers, standby power
supplies for personal computers, secondary bias supplies for
microprocessor keep−alive supplies and IR detectors. A
description of each of the functional blocks is given below,
and the representative block diagram is shown in Figure 2.

This device series features an active startup regulator
circuit that eliminates the need for an auxiliary bias winding
on the c onverter t ransformer, fault l ogic w ith a p rogrammable
timer for converter overload protection, unique gated
oscillator configuration f or e xtremely f ast l oop r esponse w ith
double pulse suppression, o scillator f requency d ithering w ith
a controlled slew rate driver for reduced EMI,
cycle−by−cycle current limiting, input undervoltage lockout
with hysteresis, t hermal s hutdown, a nd a uto r estart o r l atched
off fault detect device options. T hese d evices a re a vailable i n
economical 8−pin PDIP and 4−pin SOT−223 packages.

Oscillator

The Oscillator is a unique fixed−frequency, duty−cycle−
controlled oscillator. It charges and discharges an on chip
timing capacitor to generate a precise square wave signal
used to pulse width modulate the Power Switch Circuit.
During the discharge of the timing capacitor, the Oscillator
duty cycle output holds one input of the Driver low. This
action keeps the Power Switch Circuit off, thus limiting the
maximum duty cycle.

A frequency modulation feature is incorporated into the
IC in order to aide in EMI reduction. Figure 3 illustrates this
frequency modulation feature. The power supply voltage,
V

, acts as the input to the built−in voltage controlled

CC

oscillator. As the VCC voltage is swept across its nominal
operating range of 7.5 to 8.5 V, the oscillator frequency is
swept across its corresponding range.

The center oscillator frequency is internally programmed
for 44 kHz, 100 kHz, or 136 kHz operation with a controlled
charge to discharge current ratio that yields a maximum
Power Switch duty cycle of 77%. The Oscillator
temperature characteristics are shown in Figures 5
through 9. Contact an ON Semiconductor sales
representative for further information regarding frequency
options.

Control Input

The Control Input pin circuit has parallel source follower
input stages with voltage clamps set at 1.35 and 4.6 V.
Current sources clamp the input current through the

followers at approximately 47.5 A with 10 A hysteresis.
When a source or sink current in excess of this value is
applied to this input, a logic signal generated internally
changes state to block power switch conduction. Since the
output of the Control Input sense is sampled continuously
during t

(77% duty cycle), it is possible to turn the Power

on

Switch Circuit on or off at any time within ton. Because it
does not have to wait for the next cycle (rising edge of the
clock signal) to switch on, and because it does not have to
wait for current limit to turn off, the circuit has a very fast
transient response as shown in Figure 3.

In a typical converter application the control input current
is drawn by an optocoupler. The collector of the optocoupler
is connected to the Control Input pin and the emitter is
connected to ground. The optocoupler LED is mounted in
series with a shunt regulator (typically a TL431) at the DC
output of the converter. When the power supply output is
greater than the reference voltage (shunt regulator voltage
plus optocoupler diode voltage drop), the optocoupler turns
on, pulling down on the Control Input. The control input
logic is configured for line input sensing as well.

Turn On Latch

The Oscillator output is typically a 77% positive duty
cycle square waveform. This waveform is inverted and
applied to the reset input of the turn−on latch to prevent any
power switch conduction during the guaranteed off time.
This square wave is also gated by the output of the control
section and applied to the set input of the same latch.
Because of this gating action, the power switch can be
activated when the control input is not asserted and the
oscillator output is high.

The use of this unique gated Turn On Latch over an
ordinary Gated Oscillator allows a faster load transient
response. The power switch is allowed to turn on
immediately, within the maximum duty cycle time period,
when the control input signals a necessary change in state.

Turn Off Latch

A Turn Off Latch feature has been incorporated into this
device series to protect the power switch circuit from
excessive current, and to reduce the possibility of output
overshoot in reaction to a sudden load removal. If the Power
Switch current reaches the specified maximum current limit,
the Current Limit Comparator resets the Turn Off Latch and
turns the Power Switch Circuit off. The turn off latch is also
reset when the Oscillator output signal goes low or the
Control Input is asserted, thus terminating output MOSFET
conduction. Because of this response to control input
signals, it provides a very fast transient response and very
tight load regulation. The turn of f latch has an edge triggered
set input which ensures that the switch can only be activated
once during any oscillator period. This is commonly
referred to as double pulse suppression.

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14

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

Current Limit Comparator and Power Switch Circuit

The Power Switch Circuit is constructed with a

SENSEFET in order to monitor the drain current. A
portion of the current flowing through the circuit goes into
a sense element, R
if the voltage across R

. The current limit comparator detects

sense

exceeds the reference level that

sense

is present at its inverting input. If this level is exceeded, the
comparator quickly resets the Turn Off Latch, thus
protecting the Power Switch Circuit.

A Leading Edge Blanking circuit was placed in the current
sensing signal path to prevent a premature reset of the Turn
Off Latch. A potential premature reset signal is generated
each time the Power Switch Circuit is driven into conduction
and appears as a narrow voltage spike across current sense
resistor R

. The spike is due to the Power Switch Circuit

sense

gate to source capacitance, transformer interwinding
capacitance, and output rectifier recovery time. The Leading
Edge Blanking circuit has a dynamic behavior that masks the
current signal until the Power Switch Circuit turn−on
transition is completed. The current limit propagation delay
time is typically 135 to 165 nanoseconds. This time is
measured from when an overcurrent appears at the Power
Switch Circuit drain, to the beginning of turn−off. Care must
be taken during transformer saturation so that the maximum
device current limit rating is not exceeded.

The high voltage Power Switch Circuit is monolithically
integrated with the control logic circuitry and is designed to
directly drive the converter transformer. Because the
characteristics of the power switch circuit are well known,
the gate drive has been tailored to control switching
transitions to help limit electromagnetic interference (EMI).
The Power Switch Circuit is capable of switching 700 V
with an associated drain current that ranges nominally from

0.10 to 0.68 Amps.

Startup Circuit

Rectified AC line voltage is applied to the Startup Circuit
on Pin 5, through the primary winding. The circuit is
self−biasing and acts as a constant current source, gated by
control logic. Upon application of the AC line voltage, this
circuit routes current into the supply capacitor typically
connected to Pin 1. During normal operation, this capacitor
is hysteretically regulated from 7.5 to 8.5 V by monitoring
the supply voltage with a comparator and controlling the
startup current source accordingly. This Dynamic
Self−Supply (DSS) functionality offers a great deal of
applications flexibility as well. The startup circuit is rated at
a maximum 700 V (maximum power dissipation limits must
be observed).

Undervoltage Lockout

An Undervoltage Lockout (UVLO) comparator is
included to guarantee that the integrated circuit has
sufficient voltage to be fully functional. The UVLO
comparator monitors the supply capacitor input voltage at
Pin 1 and disables the Power Switch Circuit whenever the
capacitor voltage drops below the undervoltage lockout
threshold. When this level is crossed, the controller enters a
new startup phase by turning the current source on. The
supply voltage will then have to exceed the startup threshold
in order to turn off the startup current source. Startup and
normal operation of the converter are shown in Figure 3.

Fault Detector

The NCP105X series has integrated Fault Detector
circuitry for detecting application fault conditions such as
open loop, overload or a short circuited output. A timer is
generated by driving the supply capacitor with a known
current and hysteretically regulating the supply voltage
between set thresholds. The timer period starts when the
supply voltage reaches the nominal upper threshold of 8.5 V
and stops when the drain current of the integrated circuit
draws the supply capacitor voltage down to the undervoltage
lockout threshold of 7.5 V.

If, during this timer period, no feedback has been applied
to the control input, the fault detect logic is set to indicate an
abnormal condition. This may occur, for example, when the
optocoupler fails or the output of the application is
overloaded or completely shorted. In this case, the part will
stop switching, go into a low power mode, and begin to draw
down the supply capacitor to the reset threshold voltage of

4.5 V. At that time, the startup circuit will turn on again to
drive the supply to the turn on threshold. Then the part will
begin the cycle again, effectively sampling the control input
to determine if the fault condition has been removed. This
mode is commonly referred to as burst mode operation and
is shown is Figure 4.

Proper selection of the supply capacitor allows successful
startup with monotonically increasing output voltage,
without falsely sensing a fault condition. Figure 4 shows
successful startup and the evolution of the signals involved
in the presence of a fault.

Thermal Shutdown

The internal Thermal Shutdown block protects the device
in the event that the maximum junction temperature is
exceeded. When activated, typically at 160°C, one input of
the Driver is held low to disable the Power Switch Circuit.
The Power Switch is allowed to resume operation when the
junction temperature falls below 85°C. The thermal
shutdown feature is provided to prevent catastrophic device
failures from accidental overheating. It is not intended to be
used as a substitute for proper heatsinking.

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NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

APPLICATIONS

Two application examples have been provided in this
document, and they are described in detail in this section.
Figure 28 shows a Universal Input, 6 Watt Converter
Application as well as a 5.5 Watt Charger Application using
the NCP1053B. The Charger consists of the additional
components Q1, C13, and R7 through R10, as shown. These
were constructed and tested using the printed circuit board
layout shown in Figure 40. The board consists of a fiberglass
epoxy material (FR4) with a single side of two ounce per
square foot (70 m thick) copper foil. Test data from the tw o
applications is given in Figures 29 through 39.

Both applications generate a well−regulated output
voltage over a wide range of line input voltage and load
current values. The charger application transitions to a
constant current output if the load current is increased
beyond a preset range. This can be very effective for battery
charger application for portable products such as cellular
telephones, personal digital assistants, and pagers. Using the
NCP105X series in applications such as these offers a wide
range of flexibility for the system designer.

The NCP105X application offers a low cost alternative to
other applications. It uses a Dynamic Self−Supply (DSS)
function to generate its own operating supply voltage such
that an auxiliary transformer winding is not needed. (It also
offers the flexibility to override this function with an
auxiliary winding if ultra−low standby power is the
designer’s main concern.) This product also provides for
automatic output overload, short circuit, and open loop
protection by entering a programmable duty cycle burst
mode of operation. This eliminates the need for expensive
devices overrated for power dissipation or maximum
current, or for redundant feedback loops.

The application shown in Figure 28 can be broken down
into sections for the purpose of operating description.
Components C1, L1 and C6 provide EMI filtering for the
design, although this is very dependent upon board layout,
component type, etc. D1 through D4 along with C2 provide
the AC to bulk DC rectification. The NCP1053 drives the
primary side of the transformer, and the capacitor, C5, is an
integral part of the Dynamic Self−Supply. R1, C3, and D5
comprise an RCD snubber and R2 and C4 comprise a ringing
damper both acting together to protect the IC from voltage
transients greater than 700 volts and reduce radiated noise
from the converter . Diode D6 along with C7−9, L2, C11, and
C12 rectify the transformer secondary and filter the output

to provide a tightly regulated DC output. IC3 is a shunt
regulator that samples the output voltage by virtue of R5 and
R6 to provide drive to the optocoupler, IC2, Light Emitting
Diode (LED). C10 is used to compensate the shunt regulator .
When the application is configured as a Charger, Q1 delivers
additional drive to the optocoupler LED when in constant
current operation by sampling the output current through R7
and R8.

Component Selection Guidelines

Choose snubber components R1, C3, and D5 such that the
voltage on pin 5 is limited to the range from 0 to 700 volts.
These components protect the IC from substrate injection if
the voltage was to go below zero volts, and from avalanche
if the voltage was to go above 700 volts, at the cost of slightly
reduced efficiency. For lower power design, a simple RC
snubber as shown, or connected to ground, can be sufficient.
Ensure that these component values are chosen based upon
the worst−case transformer leakage inductance and
worst−case applied voltage. Choose R2 and C4 for best
performance radiated switching noise.

Capacitor C5 serves multiple purposes. It is used along
with the internal startup circuitry to provide power to the IC
in lieu of a separate auxiliary winding. It also serves to
provide timing for the oscillator frequency sweep for
limiting the conducted EMI emissions. The value of C5 will
also determine the response during an output fault (overload
or short circuit) or open loop condition as shown in Figure 4,
along with the total output capacitance.

Resistors R5 and R6 will determine the regulated output
voltage along with the reference voltage chosen with IC3.

The base to emitter voltage drop of Q1 along with the
value of R7 will set the fixed current limit value of the
Charger application. R9 is used to limit the base current of
Q1. Component R8 can be selected to keep the current limit
fixed with very low values of output voltage or to provide
current limit foldback with results as shown in
Figures 29 and 33. A relatively large value of R8 allows for
enough output voltage to effectively drive the optocoupler
LED for fixed current limit. A low value of R8, along with
resistor R10, provides for a low average output power using
the fault protection feature when the output voltage is very
low. C13 provides for output voltage stability when the
Charger application is in current limit.

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16

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

1.2 A

5.25 V
C12

C11

1.0

220

L2

5 H

D6

1N5822

T1

C4

50 p

C9

C8

C7

C3

R3

330

330

330

220 p

R6

47

R2

2.20 k

IC2

2.2 k

R4*

1.0 k

SFH 615A−4

D5

MUR160

220

R10*

1.0

C13*

C10

0.22

R9*

22 

IC3

Q1*

R5

2.00 k

TL431

2N3904

R8*

R7*

C6

1.2 /1 W

0.5 /1 W

100 p

R1

D1

1N4006

F1

2.0 A

91 k

D2

1N4006

L1

10 mH

C1

in

V

D3

1N4006

0.1

AC

85 − 265 V

C2

33

D4

1N4006

NCP1053B

C5

Figure 28. Universal Input 6/5 Watt Converter/Charger Application

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17

10

COOPER ELECTRONIC TECHNOLOGIES

PART # CTX22−15348

PRIMARY: 97 turns of #29 AWG, Pin 4 = start, Pin 5 = finish

SECONDARY: 5 turns of 0.40 mm, Pins 2 and 1 = start, Pins 7 and 8 = finish

GAP: Designed for Total 1.24 mH Primary Inductance

CORE: TSF−7070

BOBBIN: Pins 3 and 6 Removed, EE19

T1:

* Add Q1, C13, and R7−R10, and Change R4 to 2.0 k for Charger Output

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

Test Conditions Converter Results Charger Results

Line Regulation

Load Regulation

Output Ripple

Efficiency

No Load Input Power Vin = 110 VAC; I

Standby Output Power Vin = 110 VAC; Pin = 1 W

Short Circuit Load Input Power

Vin = 85 − 265 VAC; I

Vin = 85 − 265 VAC; I
V

= 85 − 265 VAC; I

in

Vin = 85 − 265 VAC; I

Vin = 85 − 265 VAC; I
V

= 85 − 265 VAC; I

in

Vin = 85 VAC; I
Vin = 110 VAC; I
V

= 230 VAC; I

in

V

= 265 VAC; I

in

Vin = 85 VAC; I
Vin = 110 VAC; I
V

= 230 VAC; I

in

V

= 265 VAC; I

in

Vin = 110 VAC; I
Vin = 230 VAC; I

Vin = 110 VAC; I
Vin = 230 VAC; I

Vin = 110 VAC; I
Vin = 230 VAC; I

out
out
out

out
out
out

= 120 mA − 1.2 A

out

= 120 mA − 1.2 A

out

= 120 mA − 1.2 A

out

= 120 mA − 1.2 A

out

= 100 mA − 1.00 A

out

= 100 mA − 1.00 A

out

= 100 mA − 1.00 A

out

= 100 mA − 1.00 A

out

= 1.2 A

out

= 1.2 A

out

= 1.00 A

out

= 1.00 A

out

= 1.2 A

out

= 1.2 A

out

Vin = 110 VAC; R8 = 1.2 , I
Vin = 230 VAC; R8 = 1.2 , I

Vin = 110 VAC; R8 = 0 , I
Vin = 230 VAC; R8 = 0 , I

= 0 A

Vin = 230 VAC; I

out
out

= 0 A

Vin = 230 VAC; Pin = 1 W
Vin = 110 VAC; V

Vin = 230 VAC; V

= 0 V (Shorted)

out

= 0 V (Shorted)

out

Vin = 110 VAC; R8 = 1.2 , V
Vin = 230 VAC; R8 = 1.2 , V

Vin = 110 VAC; R8 = 0 , V
Vin = 230 VAC; R8 = 0 , V

= 120 mA
= 600 mA
= 1.2 A

= 100 mA
= 500 mA
= 1.00 A

= 1.00 A

out

= 1.00 A

out

= 1.00 A

out

= 1.00 A

out

= 0 V (Shorted)

out

= 0 V (Shorted)

out

= 0 V (Shorted)

out

= 0 V (Shorted)

out

2 mV
1 mV
2 mV

12 mV
13 mV
12 mV
13 mV

86 mV

127 mV

72.4%

69.6%

100 mW
200 mW

680 mW
630 mW

400 mW
550 mW

p−p

p−p

11 mV
24 mV
41 mV

58 mV
65 mV
71 mV
67 mV

80 mV

155 mV

54.6%

53.6%

66.1%

63.3%

100 mW
200 mW

640 mW
540 mW

750 mW
900 mW

700 mW
850 mW

p−p

p−p

Figure 29. Converter and Charger Test Data Summary

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18

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

5.224

5.222

)

DC

5.220

5.218

5.216

5.214

5.212

OUTPUT VOLTAGE (V

5.210

5.208

6

5

4

3

2

OUTPUT VOLTAGE (V)

1
0

I

= 120 mA

out

I

= 600 mA

out

I

= 1.2 A

out

180 28080 130 230

LINE INPUT VOLTAGE (V

AC

)

Figure 30. Converter Line Regulation

Vin = 110 V

Vin = 230 V

Vin = 85 V

AC

LOAD CURRENT (A)

AC

Vin = 265 V

AC

120 0.5 1.5

AC

Figure 32. Converter Load Regulation

5.23

5.22

)

5.21

DC

5.20

5.19

5.18

5.17

5.16

OUTPUT VOLTAGE (V

5.15

5.14

6

5

4

3

2

OUTPUT VOLTAGE (V)

1

0

I

= 100 mA

out

I

= 500 mA

out

I

= 1 A

out

180 28080 130 230

LINE INPUT VOLTAGE (V

Figure 31. Charger Line Regulation

Vin = 85 V

Vin = 265 V

AC

Vin = 110 V

0.5
LOAD CURRENT (A)

AC

AC

1.0 1.50

Figure 33. Charger Load Regulation

)

AC

Vin = 230 V

AC

Ch1: V
Ch2: I

= 230 VAC)

(V

in

out

= 0.2 A/div

out

Ch1: V
Ch2: I
(V

= 230 VAC)

in

out

= 0.2 A/div

out

Figure 34. Converter Load Transient Response Figure 35. Charger Load Transient Response

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19

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

75

70

65

60

EFFICIENCY (%)

55

50

Vin = 110 V

Vin = 85 V

Vin = 230 V
Vin = 265 V

1.00 0.5 1.5

LOAD CURRENT (A)

Figure 36. Converter Efficiency

AC

AC

AC
AC

70

Vin = 85 V

65

60

55

EFFICIENCY (%)

Vin = 265 V

50

45

AC

Vin = 230 V

AC

Vin = 110 V

AC

AC

0.5 1.50 1.0
LOAD CURRENT (A)

Figure 37. Charger Efficiency

Ch1: V

out

Ch2: Rectified V

in

(Vin = 230 VAC,
I

= 0.5 A)

out

Figure 38. Converter On/Off Line Transient

Response

Ch1: V

out

Ch2: Rectified V

in

(Vin = 230 VAC,
I

= 0.5 A)

out

Figure 39. Charger On/Off Line Transient

Response

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20

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

Board Graphics

AC Input

NCP1050
Series

2.25″

DC Output

+

F1

C1

L1

D4

D2

D3

D1

C2

−

R1

+

C5

−

+

IC1

D5

R2

C3

C4

IC3

R4

IC2

C10

R9

R8

Q1
R7

C6

T1

R3

D6

−

R5

R6

C12

C11

+

−

L2

C9

+

−

C8

+

−

C7

+

−

Top View

2.75″

Bottom View

Figure 40. Printed Circuit Board and

Component Layout

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21

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

DIP−8

SOT−223

DEVICE ORDERING INFORMATION (Note 10)

R

DS(on)

Device

NCP1050PZZZ 100
NCP1051PZZZ
NCP1052PZZZ
NCP1053PZZZ
NCP1054PZZZ
NCP1055PZZZ 680
NCP1050STZZZT3 100
NCP1051STZZZT3
NCP1052STZZZT3
NCP1053STZZZT3
NCP1054STZZZT3
NCP1055STZZZT3 680

10.Consult factory for additional optocoupler fail−safe latching, frequency, current limit and line input options.

11.ZZZ = 44, 100, or 136 for different frequency options.

Package Shipping

DIP−8

CASE 626A

SOT−223

CASE 318E

50 Units/Rail

4000 Units/Tape & Reel

p

()

30

15

30

15

I

pk

(mA)

200
300
400
530

200
300
400
530

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22

NOTE 3

−T−

SEATING
PLANE

H

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

PACKAGE DIMENSIONS

DIP−8

P SUFFIX

CASE 626A−01

ISSUE O

NOTES:

1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.

2. CONTROLLING DIMENSION: MILLIMETER.

58

B

14

F

A

C

N

D

G

0.13 (0.005) B

L

M

J

K

M

M

A

T

M

3. PACKAGE CONTOUR OPTIONAL (ROUND OR
SQUARE CORNERS).

4. DIMENSION L TO CENTER OF LEAD WHEN
FORMED PARALLEL.

5. DIMENSIONS A AND B ARE DATUMS.

DIM MIN MAX MIN MAX

A 9.40 10.16 0.370 0.400
B 6.10 6.60 0.240 0.260
C 3.94 4.45 0.155 0.175
D 0.38 0.51 0.015 0.020
F 1.02 1.78 0.040 0.070

G 2.54 BSC 0.100 BSC

H 0.76 1.27 0.030 0.050
J 0.20 0.30 0.008 0.012
K 2.92 3.43 0.115 0.135
L 7.62 BSC 0.300 BSC

M −−− 10 −−− 10

N 0.76 1.01 0.030 0.040



INCHESMILLIMETERS

0.08 (0003)

S

L

H

A

F

4

123

G

SOT−223

ST SUFFIX

CASE 318E−04

ISSUE K

NOTES:

1. DIMENSIONING AND TOLERANCING PER ANSI
Y14.5M, 1982.

2. CONTROLLING DIMENSION: INCH.

B

D

J

C

M

INCHES

DIMAMIN MAX MIN MAX

0.249 0.263 6.30 6.70

B 0.130 0.145 3.30 3.70
C 0.060 0.068 1.50 1.75
D 0.024 0.035 0.60 0.89
F 0.115 0.126 2.90 3.20

G 0.087 0.094 2.20 2.40

H 0.0008 0.0040 0.020 0.100
J 0.009 0.014 0.24 0.35
K 0.060 0.078 1.50 2.00
L 0.033 0.041 0.85 1.05

M 0 10 0 10



S 0.264 0.287 6.70 7.30

K

MILLIMETERS

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23

NCP1050, NCP1051, NCP1052, NCP1053, NCP1054, NCP1055

The products described herein (NCP1050, 1051, 1052, 1053, 1054, 1055), may be covered by one or more of the following U.S. patents:
4,553,084; 5,418,410; 5,477,175; 6,137,696; 6,137,702; 6,271,735, 6,480,043, 6,362,067, 6,587,357. There may be other patents pending.
SENSEFET is a trademark of Semiconductor Components Industries, LLC (SCILLC)

ON Semiconductor and are registered trademarks of Semiconductor Components Industries, LLC (SCILLC). SCILLC reserves the right to make
changes without further notice to any products herein. SCILLC makes no warranty, representation or guarantee regarding the suitability of its products for any
particular purpose, nor does SCILLC assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all
liability, including without limitation special, consequential or incidental damages. “Typical” parameters which may be provided in SCILLC data sheets and/or
specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be
validated for each customer application by customer’s technical experts. SCILLC does not convey any license under its patent rights nor the rights of others.
SCILLC products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications
intended to support or sustain life, or for any other application in which the failure of the SCILLC product could create a situation where personal injury or death
may occur. Should Buyer purchase or use SCILLC products for any such unintended or unauthorized application, Buyer shall indemnify and hold SCILLC
and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees
arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that
SCILLC was negligent regarding the design or manufacture of the part. SCILLC is an Equal Opportunity/Affirmative Action Employer.

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For additional information, please contact your local
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NCP1050/D

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