The EL5156, EL5157, EL5256, and
EL5257 are 600MHz bandwidth -3dB
voltage mode feedback amplifiers with
DC accuracy of <0.01%, 1mV offsets and 40kV/V open loop
gains. These amplifiers are ideally suited for applications
ranging from precision measurement instrumentation to high
speed video and monitor applications demanding the very
highest linearity at very high frequency. Capable of operating
with as little as 6.0mA of current from a single supply ranging
from 5V to 12V and dual supplies ranging from ±2.5V to
±5.0V these amplifiers are also well suited for handheld,
portable and battery-powered equipment. With their
capability to output as much as 140mA, member of this
family is comfortable with demanding load conditions.
Single amplifiers are available in SOT-23 packages and
duals in a 10-pin MSOP package for applications where
board space is critical. Additionally, singles and duals are
available in the industry-standard 8-pin SO package. All
parts operate over the industrial temperature range of -40°C
to +85°C.
CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.
IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: TJ = TC = T
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1.8
1.6
1.4
1.136W
1.2
1
0.8
543mW
0.6
0.4
POWER DISSIPATION (W)
0.2
0
0
SOT23-5
=230°C/W
θ
JA
25125150751005085
AMBIENT TEMPERATURE (°C)
=110°C/W
θ
JA
SO8
FIGURE 33. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
9
FIGURE 32. LARGE SIGNAL FALL TIME
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1.2
1
781mW
POWER DISSIPATION (W)
0.8
0.6
0.4
0.2
0
0
488mW
SOT23-5
=256°C/W
θ
JA
2512515075
AMBIENT TEMPERATURE (°C)
=160°C/W
θ
JA
SO8
1005085
FIGURE 34. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
EL5156, EL5157, EL5256, EL5257
Typical Performance Curves (Continued)
JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
1
0.9
870mW
0.8
0.7
0.6
0.5
0.4
0.3
0.2
POWER DISSIPATION (W)
0.1
0
0255075100125
AMBIENT TEMPERATURE (°C)
MSOP8/10
θJA=115°C/W
85
FIGURE 35. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD
0.6
0.5
486mW
0.4
0.3
0.2
0.1
POWER DISSIPATION (W)
0
0 255075100125
AMBIENT TEMPERATURE (°C)
MSOP8/10
θJA=206°C/W
85
FIGURE 36. PACKAGE POWER DISSIPATION vs AMBIENT
TEMPERATURE
10
EL5156, EL5157, EL5256, EL5257
Product Description
The EL5156, EL5157, EL5256, and EL5257 are wide
bandwidth, single or dual supply, low power and low offset
voltage feedback operational amplifiers. Both amplifiers are
internally compensated for closed loop gain of +1 or greater.
Connected in voltage follower mode and driving a 500Ω
load, the -3dB bandwidth is about 610MHz. Driving a 150Ω
load and a gain of 2, the bandwidth is about 180MHz while
maintaining a 600V/µs slew rate. The EL5156 and EL5256
are available with a power down pin to reduce power to
17µA typically while the amplifier is disabled.
Input, Output and Supply Voltage Range
The EL5156 and EL5157 families have been designed to
operate with supply voltage from 5V to 12V. That means for
single supply application, the supply voltage is from 5V to
12V. For split supplies application, the supply voltage is from
±2.5V to ±5V. The amplifiers have an input common mode
voltage range from 1.5V above the negative supply (V
to 1.5V below the positive supply (V
signal is outside the above specified range, it will cause the
output signal distorted.
The outputs of the EL5156 and EL5157 families can swing
from -4V to 4V for V
lower, the output swing is lower. If the load resistor is 500Ω,
the output swing is about -4V at a 4V supply. If the load
resistor is 150Ω, the output swing is from -3.5V to 3.5V.
= ±5V. As the load resistance becomes
S
+ pin). If the input
S
Choice of Feedback Resistor and Gain Bandwidth
Product
For applications that require a gain of +1, no feedback
resistor is required. Just short the output pin to the inverting
input pin. For gains greater than +1, the feedback resistor
forms a pole with the parasitic capacitance at the inverting
input. As this pole becomes smaller, the amplifier's phase
margin is reduced. This causes ringing in the time domain
and peaking in the frequency domain. Therefore, RF can't be
very big for optimum performance. If a large value of RF
must be used, a small capacitor in the few Pico farad range
in parallel with RF can help to reduce the ringing and
peaking at the expense of reducing the bandwidth.
For gain of +1, RF = 0 is optimum. For the gains other than
+1, optimum response is obtained with RF between 500Ω to
750Ω.
The EL5156 and EL5157 families have a gain bandwidth
product of 210MHz. For gains > = 5, its bandwidth can be
predicted by the following equation: (Gain)X(BW) = 210MHz.
Video Performance
For good video performance, an amplifier is required to
maintain the same output impedance and the same
frequency response as DC levels are changed at the output.
This is especially difficult when driving a standard video load
of 150Ω, because of the change in output current with DC
level. The dG and dP for these families are about 0.006%
- pin)
S
and 0.04%, while driving 150Ω at a gain of 2. Driving high
impedance loads would give a similar or better dG and dP
performance.
Driving Capacitive Loads and Cables
The EL5156 and EL5157 families can drive 27pF loads in
parallel with 500Ω with less than 5dB of peaking at gain of
+1. If less peaking is desired in applications, a small series
resistor (usually between 5Ω to 50Ω) can be placed in series
with the output to eliminate most peaking. However, this will
reduce the gain slightly. If the gain setting is greater than 1,
the gain resistor RG can then be chosen to make up for any
gain loss which may be created by the additional series
resistor at the output.
When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, a back-termination series resistor at the
amplifier's output will isolate the amplifier from the cable and
allow extensive capacitive drive. However, other applications
may have high capacitive loads without a back-termination
resistor. Again, a small series resistor at the output can help
to reduce peaking.
Disable/Power-Down
The EL5156 and EL5256 can be disabled and their output
placed in a high impedance state. The turn off time is about
330ns and the turn on time is about 130ns. When disabled,
the amplifier's supply current is reduced to 17µA typically,
thereby effectively eliminating the power consumption. The
amplifier's power down can be controlled by standard TTL or
CMOS signal levels at the ENABLE pin. The applied logic
signal is relative to V
applying a signal that is less than 0.8V above V
the amplifier. The amplifier will be disabled when the signal
at ENABLE pin is above V
- pin. Letting the ENABLE pin float or
S
+ -1.5V.
S
- will enable
S
Output Drive Capability
The EL5156 and EL5157 families do not have internal short
circuit protection circuitry. They have a typical short circuit
current of 95mA and 70mA. If the output is shorted
indefinitely, the power dissipation could easily overheat the
die or the current could eventually compromise metal
integrity. Maximum reliability is maintained if the output
current never exceeds ±40mA. This limit is set by the design
of the internal metal interconnect. Note that in transient
applications, the part is robust.
Power Dissipation
With the high output drive capability of the EL5156 and
EL5157 families, it is possible to exceed the 125°C absolute
maximum junction temperature under certain load current
conditions. Therefore, it is important to calculate the
maximum junction temperature for the application to
determine if the load conditions or package types need to be
modified for the amplifier to remain in the safe operating
area.
11
EL5156, EL5157, EL5256, EL5257
The maximum power dissipation allowed in a package is
determined according to:
T
–
PD
MAX
JMAXTAMAX
-------------------------------------------- -=
Θ
JA
Where:
T
= Maximum junction temperature
JMAX
= Maximum ambient temperature
T
AMAX
= Thermal resistance of the package
θ
JA
The maximum power dissipation actually produced by an IC
is the total quiescent supply current times the total power
supply voltage, plus the power in the IC due to the load, or:
For sourcing:
PD
MAXVSISMAX
n
VSV
–()
∑
i1=
OUTi
V
-----------------
×+×=
OUTi
R
Li
For sinking:
n
V
–()
I
PD
MAXVSISMAX
∑
i1=
OUTiVS
×+×=
LOADi
Where:
Power Supply Bypassing and Printed Circuit
Board Layout
As with any high frequency device, a good printed circuit
board layout is necessary for optimum performance. Lead
lengths should be as sort as possible. The power supply pin
must be well bypassed to reduce the risk of oscillation. For
normal single supply operation, where the V
connected to the ground plane, a single 4.7µF tantalum
capacitor in parallel with a 0.1µF ceramic capacitor from V
to GND will suffice. This same capacitor combination should
be placed at each supply pin to ground if split supplies are to
be used. In this case, the V
- pin becomes the negative
S
supply rail.
For good AC performance, parasitic capacitance should be
kept to minimum. Use of wire wound resistors should be
avoided because of their additional series inductance. Use
of sockets should also be avoided if possible. Sockets add
parasitic inductance and capacitance that can result in
compromised performance. Minimizing parasitic capacitance
at the amplifier's inverting input pin is very important. The
feedback resistor should be placed very close to the
inverting input pin. Strip line design techniques are
recommended for the signal traces.
- pin is
S
S
+
V
= Supply voltage
S
= Maximum quiescent supply current
IS
MAX
= Maximum output voltage of the application
V
OUT
= Load resistance tied to ground
R
LOAD
= Load current
I
LOAD
N = number of amplifiers (Max = 2)
By setting the two PD
equations equal to each other, we
MAX
can solve the output current and R
overheat.
to avoid the device
LOAD
All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems.
Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality
Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.
For information regarding Intersil Corporation and its products, see www.intersil.com
12
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