intersil EL5156, EL5157, EL5256, EL5257 DATA SHEET

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EL5156, EL5157, EL5256, EL5257

PRELIMINARY

Data Sheet July 2, 2004

<1mV Voltage Offset, 600MHz Amplifiers

The EL5156, EL5157, EL5256, and
EL5257 are 600MHz bandwidth -3dB

voltage mode feedback amplifiers with
DC accuracy of <0.01%, 1mV offsets and 40kV/V open loop
gains. These amplifiers are ideally suited for applications
ranging from precision measurement instrumentation to high
speed video and monitor applications demanding the very
highest linearity at very high frequency. Capable of operating
with as little as 6.0mA of current from a single supply ranging
from 5V to 12V and dual supplies ranging from ±2.5V to
±5.0V these amplifiers are also well suited for handheld,
portable and battery-powered equipment. With their
capability to output as much as 140mA, member of this
family is comfortable with demanding load conditions.

Single amplifiers are available in SOT-23 packages and
duals in a 10-pin MSOP package for applications where
board space is critical. Additionally, singles and duals are
available in the industry-standard 8-pin SO package. All
parts operate over the industrial temperature range of -40°C
to +85°C.

Ordering Information

FN7386.2

Features

• 600MHz -3dB bandwidth, 240MHz 0.1dB bandwidth

• 700V/µs slew rate

• <1mV input offset

• Very high open loop gains 92dB

• Low supply current = 6mA

• 140mA output current

• Single supplies from 5V to 12V

• Dual supplies from ±2.5V to ±5V

• Fast disable on the EL5156 and EL5256

•Low cost

Applications

•Imaging

• Instrumentation

•Video

• Communications devices

PAR T

NUMBER PACKAGE TAPE & REEL PKG. DWG. #

EL5156IS 8-Pin SO - MDP0027

EL5156IS-T7 8-Pin SO 7” MDP0027

EL5156IS-T13 8-Pin SO 13” MDP0027

EL5157IW-T7 5-Pin SOT-23 7” (3K pcs) MDP0038

EL5157IW-T7A 5-Pin SOT-23 7” (250 pcs) MDP0038

EL5256IY 10-Pin MSOP - MDP0043

EL5256IY-T7 10-Pin MSOP 7” MDP0043

EL5256IY-T13 10-Pin MSOP 13” MDP0043

EL5257IS 8-Pin SO - MDP0027

EL5257IS-T7 8-Pin SO 7” MDP0027

EL5257IS-T13 8-Pin SO 13” MDP0027

EL5257IY 8-Pin MSOP - MDP0043

EL5257IY-T7 8-Pin MSOP 7” MDP0043

EL5257IY-T13 8-Pin MSOP 13” MDP0043

1

Copyright © Intersil Americas Inc. 2004. All Rights Reserved. Elantec is a registered trademark of Elantec Semiconductor, Inc.

CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures.

1-888-INTERSIL or 321-724-7143

| Intersil (and design) is a registered trademark of Intersil Americas Inc.

All other trademarks mentioned are the property of their respective owners.

Pinouts

EL5156

(8-PIN SO)

TOP VIEW

EL5156, EL5157, EL5256, EL5257

EL5157

(5-PIN SOT-23)

TOP VIEW

1

NC

IN-

2

IN+

3

VS-

4

(10-PIN MSOP)

TOP VIEW

INA+

1

CEA

2

VS-

3

4

CEB

INB+

5 6

-

+

EL5256

-

+

+

-

10

8

7

6

5

9

8

7

CE

VS+

OUT

NC

INA-

OUTA

VS+

OUTB

INB-

OUT

VS-

IN+

OUTA

INA-

INA+

VS-

1

2

3

(8-PIN SO)

TOP VIEW

1

2

3

4

-+

EL5257

­+

5

VS+

IN-

4

8

VS+

OUTB

7

INB-

6

­INB+

+

5

2

EL5156, EL5157, EL5256, EL5257

Absolute Maximum Ratings (T

Supply Voltage between V

Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . 50mA

Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . . GND -0.5V to V

Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves

CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the
device at these or any other conditions above those indicated in the operational sections of this specification is not implied.

IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests
are at the specified temperature and are pulsed tests, therefore: TJ = TC = T

and GND. . . . . . . . . . . . . . . . . . . 13.2V

S

Electrical Specifications V

= 25°C)

A

Junction Temperature . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . +125°C

Storage Temperature. . . . . . . . . . . . . . . . . . . . . . . . -65°C to +150°C

+0.5V

S

A

+ = +5V, VS- = -5V, CE = +5V, RF = RG = 562Ω, RL = 150Ω, TA = 25°C, unless otherwise specified.

S

Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C

Current into I

+, IN-, CE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 5mA

N

PARAMETER DESCRIPTION CONDITIONS MIN TYP MAX UNIT

AC PERFORMANCE

BW -3dB Bandwidth A

= +1, RL = 500Ω, CL = 4.7pF 600 MHz

V

AV = +2, RL = 150Ω 180 MHz

GBWP Gain Bandwidth Product R

BW1 0.1dB Bandwidth A

= 150Ω 210 MHz

L

= +2 70 MHz

V

SR Slew Rate VO = -3.2V to +3.2V, AV = +2, RL = 150Ω 500 640 V/µs

V

= -3.2V to +3.2V, AV = +1, RL = 500Ω 700 V/µs

O

t

S

dG Differential Gain Error A

0.1% Settling Time AV = +1 15 ns

= +2, RL = 150Ω 0.005 %

V

dP Differential Phase Error AV = +2, RL = 150Ω 0.04 °

V

N

I

N

Input Referred Voltage Noise 12 nV/√Hz

Input Referred Current Noise 5.5 pA/√Hz

DC PERFORMANCE

V

OS

T

CVOS

A

VOL

Offset Voltage -1 0.5 1 mV

Input Offset Voltage Temperature
Coefficient

Measured from T

MIN

to T

MAX

-3 µV/°C

Open Loop Gain VO is from -2.5V to 2.5V 10 40 kV/V

INPUT CHARACTERISTICS

CMIR Common Mode Input Range Guaranteed by CMRR test -2.5 +2.5 V

CMRR Common Mode Rejection Ratio V

I

B

Input Bias Current EL5156 & EL5157 -1 -0.4 +1 µA

= 2.5V to -2.5V 80 108 dB

CM

EL5256 & EL5257 -600 -200 +600 nA

I

R

C

OS

IN

IN

Input Offset Current -250 100 +250 nA

Input Resistance 10 25 MΩ

Input Capacitance 1pF

OUTPUT CHARACTERISTICS

V

I

OUT

OUT

Output Voltage Swing RL = 150Ω to GND ±3.4 ±3.6 V

= 500Ω to GND ±3.6 ±3.8 V

R

L

Peak Output Current RL = 10Ω to GND ±80 ±140 mA

ENABLE (EL5156 and EL5256 ONLY)

t

t

EN

DIS

Enable Time 200 ns

Disable Time 300 ns

3

EL5156, EL5157, EL5256, EL5257

Electrical Specifications V

+ = +5V, VS- = -5V, CE = +5V, RF = RG = 562Ω, RL = 150Ω, TA = 25°C, unless otherwise specified.

S

PARAMETER DESCRIPTION CONDITIONS MIN TYP MAX UNIT

I

IHCE

I

ILCE

V

IHCE

V

ILCE

CE Pin Input High Current CE = VS+0-1µA

CE Pin Input Low Current CE = VS- 5 13 25 µA

CE Input High Voltage for Power-down VS+ -1 V

CE Input Low Voltage for Power-up VS+ -3 V

SUPPLY

I

SON

I

SOFF

PSRR Power Supply Rejection Ratio DC, V

Supply Current - Enabled (per amplifier) No load, V

Supply Current - Disabled (per amplifier) No load, V

= ±3.0V to ±6.0V 75 90 dB

S

= 0V, CE = +5V 5.1 6.0 6.9 mA

IN

= 0V, CE = 5V 5 13 25 µA

IN

Typical Performance Curves

4

RL=150Ω

3

=4.7pF

C

L

2

1

0

-1

-2

-3

-4

NORMALIZED GAIN (dB)

-5

-6
100K 1M 100M 1G

AV=+10

AV=+5

10M

FREQUENCY (Hz)

AV=+2

AV=+1

135

RL=150Ω

90

=4.7pF

C

L

45

0

-45

-90

-135

PHASE (°)

-180

-225

-270

-315
100K 1M 100M 1G

AV=+5

AV=+10

10M

FREQUENCY (Hz)

AV=+2

FIGURE 1. SMALL SIGNAL FREQUENCY RESPONSE - GAIN FIGURE 2. SMALL SIGNAL FREQUENCY RESPONSE -

PHASE FOR VARIOUS GAINS

4

VS=±5V

3

A

=+2

V

=562Ω

R

2

F=RG

1

0

-1

-2

-3

-4

NORMALIZED GAIN (dB)

-5

-6
100K 1M 100M 1G

RL=500Ω

RL=150Ω

RL=750Ω

RL=50Ω

10M

FREQUENCY (Hz)

FIGURE 3. SMALL SIGNAL FREQUENCY RESPONSE FOR

VARIOUS R

L

FIGURE 4. SMALL SIGNAL FREQUENCY RESPONSE FOR

5

AV=+1

4

=500Ω

R

L

3

2

1

0

-1

GAIN (dB)

-2

-3

-4

-5
100K 1M 100M 1G

FREQUENCY (Hz)

VARIOUS C

L

CL=27pF

CL=10pF

CL=4.7pF

CL=1pF

10M

4

EL5156, EL5157, EL5256, EL5257

Typical Performance Curves (Continued)

5

AV=+2

4

R

=500Ω

L

=500Ω

R

3

F=RG

2

1

0

-1

-2

-3

NORMALIZED GAIN (dB)

-4

-5
100K 1M 100M 1G

10M

FREQUENCY (Hz)

22pF

10pF

8.2pF

4.7pF

0pF

FIGURE 5. SMALL SIGNAL FREQUENCY RESPONSE FOR

VARIOUS C

5

AV=+5

4

=500Ω

R

L

3

2

1

0

-1

-2

-3

NORMALIZED GAIN (dB)

-4

-5
100K 1M 100M 1G

L

100pF

82pF

68pF

22pF

10M

FREQUENCY (Hz)

16

AV=+2

14

12

10

8

6

4

GAIN (dB)

2

0

-2

-4
100K 1M 100M 1G

R
R

F=RG

=150Ω

L

=562Ω

180pF

100pF

33pF

10pF

0pF

10M

FREQUENCY (Hz)

FIGURE 6. SMALL SIGNAL FREQUENCY RESPONSE FOR

VARIOUS C

5

RL=500Ω

4

=4.7pF

C

L

3

A

=+1

V

2

1

0

-1

-2

NORMALIZED GAIN (dB)

-3

-4

100K 1M 10M 500M

L

±2.0V

±3.0V

±4.0V

±5.0V

100M

FREQUENCY (Hz)

FIGURE 7. SMALL SIGNAL FREQUENCY RESPONSE FOR

VARIOUS C

5

4

3

2

1

0

-1

-2
AV=+1

-3

NORMALIZED GAIN (dB)

=500Ω

R

L

=4.7pF

C

-4

L

-5

100K 1M 100M 1G

L

AV=+1

AV=+2

AV=+5

10M

FREQUENCY (Hz)

FIGURE 9. EL5256 SMALL SIGNAL FREQUENCY

RESPONSE FOR VARIOUS GAINS

5

FIGURE 8. FREQUENCY RESPONSE vs POWER SUPPLY

4

VS=±5V

3

R

=620Ω

F

=150Ω

R

2

L

1

0

-1

-2

-3

-4

NORMALIZED GAIN (dB)

-5

-6
100K 1M 100M 1G

FREQUENCY (Hz)

AV=-1

AV=-2

10M

FIGURE 10. SMALL SIGNAL INVERTING FREQUENCY

RESPONSE FOR VARIOUS GAINS

EL5156, EL5157, EL5256, EL5257

Typical Performance Curves (Continued)

4

AV=+1

3

=0.2pF

C

L

2

1

0

-1

-2

-3

-4

NORMALIZED GAIN (dB)

-5

-6
100K 1M 100M 1G

FREQUENCY (Hz)

RL=500Ω

RL=300Ω

RL=150Ω

10M

FIGURE 11. SMALL SIGNAL FREQUENCY RESPONSE FOR

VARIOUS R

5

AV=+2

4

=500Ω

R

L

3

=4.7pF

C

L

R

=500Ω

F

2

1

0

-1

-2

-3

NORMALIZED GAIN (dB)

-4

-5
100K 1M 100M 200M

L

12pF

8.2pF

4.7pF

0.2pF

0pF

10M

FREQUENCY (Hz)

5

AV=+1

4

=4.7pF

C

L

3

2

1

0

-1

-2

-3

NORMALIZED GAIN (dB)

-4

-5
100K 1M 100M 1G

10M

FREQUENCY (Hz)

500Ω

200Ω

100Ω

50Ω

FIGURE 12. EL5256 SMALL SIGNAL FREQUENCY

RESPONSE FOR VARIOUS R

4

AV=+5

3

C

=4.7pF

L

=500Ω

R

L

2

=102Ω

R

F

1

0

-1

-2

-3

NORMALIZED GAIN (dB)

-4

-5

100K 1M 100M 200M

68pF

47pF

22pF

4.7pF
0pF

FREQUENCY (Hz)

L

10M

FIGURE 13. SMALL SIGNAL FREQUENCY RESPONSE FOR

VARIOUS C

4

VS=±5V

3

=+2

A

V

2

=150Ω

R

L

=4.7pF

C

L

1

0

-1

-2

-3

-4

NORMALIZED GAIN (dB)

-5

-6
100K 1M 100M 1G

IN

RF=RG=1kΩ

350Ω

562Ω

500Ω

250Ω

10M

FREQUENCY (Hz)

FIGURE 15. SMALL SIGNAL FREQUENCY RESPONSE FOR

VARIOUS R

AND R

F

G

6

FIGURE 14. SMALL SIGNAL FREQUENCY RESPONSE FOR

VARIOUS C

6

AV=+2

5

=4.7pF

C

L

4

=500Ω

R

L

3

2

1

0

-1

NORMALIZED GAIN

-2

-3

-4
100K 1M 100M 1G

IN

RF=RG=3kΩ

2kΩ

1kΩ

500Ω

200Ω

10M

FREQUENCY (Hz)

FIGURE 16. EL5256 SMALL SIGNAL FREQUENCY

RESPONSE FOR VARIOUS R

F/RG

EL5156, EL5157, EL5256, EL5257

Typical Performance Curves (Continued)

5

AV=+2

4

=200Ω

R

L

=4.7pF

3

C

L

2

1

0

-1

-2

NORMALIZED GAIN (dB)

-3

-4

-5
100K 1M 10M 600M

15dBm

17dBm

20dBm

FREQUENCY (Hz)

-20dBm

10dBm

100M

FIGURE 17. LARGE SIGNAL FREQUENCY RESPONSE FOR

VARIOUS INPUT AMPLITUDES

0

AV=+5

-10

=500Ω

R

L

=4.7pF

C

-20

L

-30

-40

-50

-60

-70

CROSS TALK (10dB)

-80

-90

-100
100K 1M 100M 1G

10M

FREQUENCY (Hz)

FIGURE 19. EL5256 CROSS TALK vs FREQUENCY CHANNEL

A TO B & B TO A

5

4

3

2

1

0

-1

-2
AV=+1

-3

NORMALIZED GAIN (dB)

=500Ω

R

L

=4.7pF

C

-4

L

-5

100K 1M 100M 1G

CHANNEL #1

CHANNEL #2

10M

FREQUENCY (Hz)

FIGURE 18. CHANNEL TO CHANNEL FREQUENCY

RESPONSE

700

600

500

400

300

BW (MHz)

200

100

0

4.5 5.5 6.5 7.5 8.5 9.5 10.5 11.5

AV=+1,RL=500Ω, CL=5pF

AV=+1, RL=150Ω

AV=+2,RL=150Ω

V

(V)

S

FIGURE 20. BANDWIDTH vs SUPPLY VOLTAGE

4

AV=+5

3

=4.7pF

C

L

2

1

0

-1

-2

-3

-4

NORMALIZED GAIN (dB)

-5

-6
100K 1M 100M 1G

100Ω

50Ω

10M

FREQUENCY (Hz)

500Ω

1000Ω

FIGURE 21. SMALL SIGNAL FREQUENCY RESPONSE FOR

VARIOUS R

L

7

1K

100

V

10K

N

I

N

1M

VOLTAGE NOISE (nV/√Hz),

CURRENT NOISE (pA/√Hz)

10

1

100 100K 10M

10

1K

FREQUENCY (Hz)

FIGURE 22. VOLTAGE AND CURRENT NOISE vs FREQUENCY

EL5156, EL5157, EL5256, EL5257

Typical Performance Curves (Continued)

-20

-30

-40

-50

-60

-70

CMRR (dB)

-80

-90

-100

-110

100 1K 100K 100M

10K

FREQUENCY (Hz)

10M1M

1

0

0

0

AV=+2
R

=0Ω

L

=400Ω

R

0

1

0

G=RF

1

0

1

IMPEDANCE (Ω)

0

1

0

.

0

.

0

0

1

1K

10K 100K 100M

FREQUENCY (Hz)

1M

10M

FIGURE 23. CMRR

-10
VS=±5V

-20

=+2

A

V

R

=150Ω

-30

L

-40

-50

-60

-70

-80

-90

DISABLED ISOLATION (dB)

-100

-110
100K 1M 100M 1G

10M

FREQUENCY (Hz)

FIGURE 25. INPUT TO OUTPUT ISOLATION vs FREQUENCY -

DISABLE

AV=+2

=500Ω

R

L

SUPPLY=±5.0V
±12.3mA

ENABLE
192ns

TIME (400ns/DIV)

DISABLE
322ns

FIGURE 27. ENABLE/DISABLE RESPONSE

FIGURE 24. OUTPUT IMPEDANCE

6.1

6

5.9

5.8

(mA)

5.7

S

I

5.6

5.5

5.4

5.3

4.5 5 5.5 6 6.5 7 7.5 8 8.5 9 9.5 1010.5 1111.5 12

IS-

IS+

V

(V)

S

FIGURE 26. SUPPLY CURRENT vs SUPPLY VOLTAGE

0.8

A

=+1

V

0.7
RL=500Ω

0.6

=5pF

C

L

0.5

0.4

0.3

PEAKING (dB)

0.2

0.1

0

4.5 5.5 6.5 7.5 8.5 9.5 10.5 11.5
V

(V)

S

FIGURE 28. PEAKING vs SUPPLY VOLTAGE

8

EL5156, EL5157, EL5256, EL5257

Typical Performance Curves (Continued)

AV=+2

=500Ω

R

L

SUPPLY=±5.0V ±12.3mA
OUTPUT=200mV

P-P

0

(40mV/DIV)

OUT

V

RISE
20%-80%
∆T=2.025ns

TIME (4ns/DIV)

FIGURE 29. SMALL SIGNAL RISE TIME

AV=+2

=500Ω

R

L

SUPPLY=±5.0V ±12.3mA
OUTPUT=2.0V

0

(400mV/DIV)

OUT

V

P-P

RISE
20%-80%
∆T=1.657ns

TIME (2ns/DIV)

0

(40mV/DIV)

OUT

AV=+2

V

=500Ω

R

L

SUPPLY=±5.0V ±12.3mA
OUTPUT=200mV

P-P

TIME (4ns/DIV)

FALL
80%-20%
∆T=1.91ns

FIGURE 30. SMALL SIGNAL FALL TIME

AV=+2

=500Ω

R

L

SUPPLY=±5.0V ±12.3mA
OUTPUT=2.0V

0

(400mV/DIV)

OUT

V

TIME (2ns/DIV)

FALL
80%-20%
∆T=1.7ns

P-P

FIGURE 31. LARGE SIGNAL RISE TIME

JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD

1.8

1.6

1.4

1.136W

1.2

1

0.8

543mW

0.6

0.4

POWER DISSIPATION (W)

0.2

0

0

SOT23-5

=230°C/W

θ

JA

25 125 15075 10050 85

AMBIENT TEMPERATURE (°C)

=110°C/W

θ

JA

SO8

FIGURE 33. PACKAGE POWER DISSIPATION vs AMBIENT

TEMPERATURE

9

FIGURE 32. LARGE SIGNAL FALL TIME

JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD

1.2

1

781mW

POWER DISSIPATION (W)

0.8

0.6

0.4

0.2

0

0

488mW

SOT23-5

=256°C/W

θ

JA

25 125 15075

AMBIENT TEMPERATURE (°C)

=160°C/W

θ

JA

SO8

10050 85

FIGURE 34. PACKAGE POWER DISSIPATION vs AMBIENT

TEMPERATURE

EL5156, EL5157, EL5256, EL5257

Typical Performance Curves (Continued)

JEDEC JESD51-7 HIGH EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD

1

0.9

870mW

0.8

0.7

0.6

0.5

0.4

0.3

0.2

POWER DISSIPATION (W)

0.1

0

0 25 50 75 100 125

AMBIENT TEMPERATURE (°C)

MSOP8/10

θJA=115°C/W

85

FIGURE 35. PACKAGE POWER DISSIPATION vs AMBIENT

TEMPERATURE

JEDEC JESD51-3 LOW EFFECTIVE THERMAL
CONDUCTIVITY TEST BOARD

0.6

0.5
486mW

0.4

0.3

0.2

0.1

POWER DISSIPATION (W)

0

0 255075100125

AMBIENT TEMPERATURE (°C)

MSOP8/10

θJA=206°C/W

85

FIGURE 36. PACKAGE POWER DISSIPATION vs AMBIENT

TEMPERATURE

10

EL5156, EL5157, EL5256, EL5257

Product Description

The EL5156, EL5157, EL5256, and EL5257 are wide
bandwidth, single or dual supply, low power and low offset
voltage feedback operational amplifiers. Both amplifiers are
internally compensated for closed loop gain of +1 or greater.
Connected in voltage follower mode and driving a 500Ω
load, the -3dB bandwidth is about 610MHz. Driving a 150Ω
load and a gain of 2, the bandwidth is about 180MHz while
maintaining a 600V/µs slew rate. The EL5156 and EL5256
are available with a power down pin to reduce power to
17µA typically while the amplifier is disabled.

Input, Output and Supply Voltage Range

The EL5156 and EL5157 families have been designed to
operate with supply voltage from 5V to 12V. That means for
single supply application, the supply voltage is from 5V to
12V. For split supplies application, the supply voltage is from
±2.5V to ±5V. The amplifiers have an input common mode
voltage range from 1.5V above the negative supply (V
to 1.5V below the positive supply (V
signal is outside the above specified range, it will cause the
output signal distorted.

The outputs of the EL5156 and EL5157 families can swing
from -4V to 4V for V
lower, the output swing is lower. If the load resistor is 500Ω,
the output swing is about -4V at a 4V supply. If the load
resistor is 150Ω, the output swing is from -3.5V to 3.5V.

= ±5V. As the load resistance becomes

S

+ pin). If the input

S

Choice of Feedback Resistor and Gain Bandwidth
Product

For applications that require a gain of +1, no feedback
resistor is required. Just short the output pin to the inverting
input pin. For gains greater than +1, the feedback resistor
forms a pole with the parasitic capacitance at the inverting
input. As this pole becomes smaller, the amplifier's phase
margin is reduced. This causes ringing in the time domain
and peaking in the frequency domain. Therefore, RF can't be
very big for optimum performance. If a large value of RF
must be used, a small capacitor in the few Pico farad range
in parallel with RF can help to reduce the ringing and
peaking at the expense of reducing the bandwidth.

For gain of +1, RF = 0 is optimum. For the gains other than
+1, optimum response is obtained with RF between 500Ω to
750Ω.

The EL5156 and EL5157 families have a gain bandwidth
product of 210MHz. For gains > = 5, its bandwidth can be
predicted by the following equation: (Gain)X(BW) = 210MHz.

Video Performance

For good video performance, an amplifier is required to
maintain the same output impedance and the same
frequency response as DC levels are changed at the output.
This is especially difficult when driving a standard video load
of 150Ω, because of the change in output current with DC
level. The dG and dP for these families are about 0.006%

- pin)

S

and 0.04%, while driving 150Ω at a gain of 2. Driving high
impedance loads would give a similar or better dG and dP
performance.

Driving Capacitive Loads and Cables

The EL5156 and EL5157 families can drive 27pF loads in
parallel with 500Ω with less than 5dB of peaking at gain of
+1. If less peaking is desired in applications, a small series
resistor (usually between 5Ω to 50Ω) can be placed in series
with the output to eliminate most peaking. However, this will
reduce the gain slightly. If the gain setting is greater than 1,
the gain resistor RG can then be chosen to make up for any
gain loss which may be created by the additional series
resistor at the output.

When used as a cable driver, double termination is always
recommended for reflection-free performance. For those
applications, a back-termination series resistor at the
amplifier's output will isolate the amplifier from the cable and
allow extensive capacitive drive. However, other applications
may have high capacitive loads without a back-termination
resistor. Again, a small series resistor at the output can help
to reduce peaking.

Disable/Power-Down

The EL5156 and EL5256 can be disabled and their output
placed in a high impedance state. The turn off time is about
330ns and the turn on time is about 130ns. When disabled,
the amplifier's supply current is reduced to 17µA typically,
thereby effectively eliminating the power consumption. The
amplifier's power down can be controlled by standard TTL or
CMOS signal levels at the ENABLE pin. The applied logic
signal is relative to V
applying a signal that is less than 0.8V above V
the amplifier. The amplifier will be disabled when the signal
at ENABLE pin is above V

- pin. Letting the ENABLE pin float or

S

+ -1.5V.

S

- will enable

S

Output Drive Capability

The EL5156 and EL5157 families do not have internal short
circuit protection circuitry. They have a typical short circuit
current of 95mA and 70mA. If the output is shorted
indefinitely, the power dissipation could easily overheat the
die or the current could eventually compromise metal
integrity. Maximum reliability is maintained if the output
current never exceeds ±40mA. This limit is set by the design
of the internal metal interconnect. Note that in transient
applications, the part is robust.

Power Dissipation

With the high output drive capability of the EL5156 and
EL5157 families, it is possible to exceed the 125°C absolute
maximum junction temperature under certain load current
conditions. Therefore, it is important to calculate the
maximum junction temperature for the application to
determine if the load conditions or package types need to be
modified for the amplifier to remain in the safe operating
area.

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EL5156, EL5157, EL5256, EL5257

The maximum power dissipation allowed in a package is
determined according to:

T

–

PD

MAX

JMAXTAMAX

-------------------------------------------- -=

Θ

JA

Where:

T

= Maximum junction temperature

JMAX

= Maximum ambient temperature

T

AMAX

= Thermal resistance of the package

θ

JA

The maximum power dissipation actually produced by an IC
is the total quiescent supply current times the total power
supply voltage, plus the power in the IC due to the load, or:

For sourcing:

PD

MAXVSISMAX

n

VSV

–()

∑

i1=

OUTi

V

-----------------

×+×=

OUTi

R

Li

For sinking:

n

V

–()

I

PD

MAXVSISMAX

∑

i1=

OUTiVS

×+×=

LOADi

Where:

Power Supply Bypassing and Printed Circuit
Board Layout

As with any high frequency device, a good printed circuit
board layout is necessary for optimum performance. Lead
lengths should be as sort as possible. The power supply pin
must be well bypassed to reduce the risk of oscillation. For
normal single supply operation, where the V
connected to the ground plane, a single 4.7µF tantalum
capacitor in parallel with a 0.1µF ceramic capacitor from V
to GND will suffice. This same capacitor combination should
be placed at each supply pin to ground if split supplies are to
be used. In this case, the V

- pin becomes the negative

S

supply rail.

For good AC performance, parasitic capacitance should be
kept to minimum. Use of wire wound resistors should be
avoided because of their additional series inductance. Use
of sockets should also be avoided if possible. Sockets add
parasitic inductance and capacitance that can result in
compromised performance. Minimizing parasitic capacitance
at the amplifier's inverting input pin is very important. The
feedback resistor should be placed very close to the
inverting input pin. Strip line design techniques are
recommended for the signal traces.

- pin is

S

S

+

V

= Supply voltage

S

= Maximum quiescent supply current

IS

MAX

= Maximum output voltage of the application

V

OUT

= Load resistance tied to ground

R

LOAD

= Load current

I

LOAD

N = number of amplifiers (Max = 2)

By setting the two PD

equations equal to each other, we

MAX

can solve the output current and R
overheat.

to avoid the device

LOAD

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Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality

Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without
notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and
reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result
from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries.

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