Datasheet U211B3, U211B2 Datasheet (TEMIC)

U211B2/ B3

Phase Control Circuit - General Purpose Feedback

Description

The integrated circuit U211B2/ B3 is designed as a phase control circuit in bipolar technology with an internal frequency-voltage converter. Furthermore, it has an internal control amplifier which means it can be used for speedregulated motor applications.

Features

D

Internal frequency-to-voltage converter

D

Externally-controlled integrated amplifier

D

Overload limitation with a “fold back” characteristic

D

Optimized soft-start function

D

Tacho monitoring for shorted and open loop

D

Automatic retriggering switchable

It has an integrated load limitation, tacho monitoring and soft-start functions, etc. to realize sophisticated motor control systems.

D

Triggering pulse typ. 155 mA

D

Voltage and current synchronization

D

Internal supply-voltage monitoring

D

Temperature reference source

D

Current requirement ≤ 3 mA

Package: DIP18 - U211B2,

SO16 - U211B3

11(10)

10(9)

14(13)

15(14)

17(16) 1(1)

Voltage / Current

detector

Control amplifier

+

–

Load limitation

speed / time

controlled

current sink

5*)

Automatic retriggering

Phase

control unit

ö

= f (V12)

Soft start

–V

Ref

12(11) 13(12) 9(8) 8(7)

Frequency-

to-voltage

converter

Output

pulse

Supply voltage

limitation

Reference

voltage

Voltage

monitoring

Pulse-blocking

tacho

monitoring

4(4)

6(5)

7(6)

3(3)

2(2)

16(15)

18*)

95 10360

–V

S

GND

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

Figure 1. Block diagram (Pins in brackets refer to SO16)

*) Pins 5 and 18 connected internally

1 (20)

U211B2/ B3

L

M

1

D

W

18 k

1N4007

1

R

2 W

R

4

3

W

470 k

W

220 k

=

M

V

TIC

226

12

R

4

5

17 1

Set speed

voltage

230 V ~

8

R

W

1 M

180

2

R

6

pulse

Output

Automatic

retriggering

detector

Control

amplifier

Voltage / Current

11

W

19

R

100 k

10

C

W

1 W

33 m

3.3 nF

C

7

–

+

10

F

m

2.2 /16V

N

F

m

22

C

S

2

–V

3

Supply

voltage

Phase

control unit

F

m

25 V

2.2

1

C

GND

2

limitation

)

12

= f (V

ö

10

R

11

16

voltage

Voltage

Reference

controlled

speed / time

Load limitation

14

W

1 k

1 M

monitoring

15

9

R

C

tacho

Pulse blocking

to voltage

Frequency

Soft start

controlled

current sink

F

m

9

4.7 /16V

18

monitoring

converter

Ref

–V

12 13 9 8

95 10361

220 nF

11

R

Speed sensor

4

C

W

R

1 k

5

F

1 nF

C

m

16 V

2.2

3

8

C

220 nF

7

R

7

F

m

10 /16V

W

2 M

6

R

6

C

W

22 k

W

100 k

100 nF

C

voltage

Actual speed

5

2 (20)

R

31

W

100 k

W

13

R

47 k

W

14

R

56 k

Figure 2. Speed control, automatic retriggering, load limiting, soft start

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

Description

Mains Supply

The U211B2 is fitted with voltage limiting and can therefore be supplied directly from the mains. The supply

voltage between Pin 2 (+ pol/ă) and Pin 3 builds up

and R

across D

1

series resistance can be approximated using (see figure 2):

Further information regarding the design of the mains supply can be found in the data sheets in the appendix. The reference voltage source on Pin 16 of typ. –8.9 V is derived from the supply voltage and is used for regulation.

Operation using an externally stabilised DC voltage is not recommended.

If the supply cannot be taken directly from the mains because the power dissipation in R then the circuit shown in the following figure 3 should be used.

and is smoothed by C1. The value of the

1

V

–V

M

2I

S

would be too large,

1

+

R

1

U211B2/ B3

When the potential on Pin 7 reaches the nominal value predetermined at Pin 12, then a trigger pulse is generated whose width t

and hence the pulse width can be evaluated by

of C

2

is determined by the value of C

p

assuming 8 ms/nF). At the same time, a latch is set, so that as long as the automatic retriggering has not been activated, then no more pulses can be generated in that half cycle.

The current sensor on Pin 1 ensures that, for operations with inductive loads, no pulse will be generated in a new half-cycle as long as a current from the previous half cycle is still flowing in the opposite direction to the supply voltage at that instant. This makes sure that “gaps” in the load current are prevented.

The control signal on Pin 12 can be in the range 0 V to –7 V (reference point Pin 2).

= –7 V then the phase angle is at maximum =

If V

12

i.e., the current flow angle is a minimum. The phase angle

a

is minimum when V

min

= V2.

12

(the value

2

a

max

~

24 V~

123

C

R

1

Figure 3. Supply voltage for high current requirements

1

4

95 10362

5

Phase Control

There is a general explanation in the data sheet, TEA1007, on the common phase control function. The phase angle of the trigger pulse is derived by comparing the ramp voltage (which is mains synchronized by the voltage detector) with the set value on the control input Pin 12. The slope of the ramp is determined by C charging current. The charging current can be varied using R also be adjusted using R

on Pin 6. The maximum phase angle

2

.

2

a

max

and its

can

Voltage Monitoring

As the voltage is built up, uncontrolled output pulses are avoided by internal voltage surveillance. At the same time, all of the latches in the circuit (phase control, load limit regulation, soft start) are reset and the soft-start capacitor is short circuited. Used with a switching hysteresis of 300 mV, this system guarantees defined start-up behavior each time the supply voltage is switched on or after short interruptions of the mains supply.

Soft-Start

As soon as the supply voltage builds up (t1), the integrated soft-start is initiated. The figure below shows the behaviour of the voltage across the soft-start capacitor and is identical with the voltage on the phase control input on Pin 12. This behaviour guarantees a gentle start-up for the motor and automatically ensures the optimum run-up time.

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

3 (20)

U211B2/ B3

V

C3

V

12

V

0

t

1

t

2

Figure 4. Soft-start

t

3

t

tot

95 10272

t

t1 = build-up of supply voltage

= charging of C3 to starting voltage

t

2

+ t2 = dead time

t

1

= run-up time

t

3

= total start-up time to required speed

t

tot

C

is first charged up to the starting voltage V

3

typical 45 mA current (t

). By then reducing the charging

2

0

with

current to approx. 4 mA, the slope of the charging function is substantially reduced so that the rotational speed of the motor only slowly increases. The charging current then increases as the voltage across C

increases giving a

3

progressively rising charging function which accelerates the motor more and more strongly with increasing rotational speed. The charging function determines the acceleration up to the set-point. The charging current can have a maximum value of 55 mA.

Frequency to Voltage Converter

The internal frequency to voltage converter (f/Vconverter) generates a DC signal on Pin 10 which is proportional to the rotational speed using an AC signal from a tacho-generator or a light beam whose frequency is in turn dependent on the rotational speed. The high impedance input Pin 8, compares the tacho-voltage to a switch-on threshold of typ. –100 mV. The switch-off threshold is given with –50 mV. The hysteresis guarantees very reliable operation even when relatively simple tacho-generators are used. The tacho-frequency is given by:

n

f

+

60

where: n = revolutions per minute

p(Hz)

p = number of pulses per revolution

The converter is based on the charge pumping principle. With each negative half wave of the input signal, a quantity of charge determined by C amplified and then integrated by C

is internally

5

at the converter

6

output on Pin 10. The conversion constant is determined

, its charge transfer voltage of Vch, R6 (Pin 10) and

by C

5

the internally adjusted charge transfer gain.

I

10

ƪ

ƫ

G

k = G

+

i

8.3

I

9

C5 R6 V

i

ch

The analog output voltage is given by

V

= k @ f

O

The values of C

and C

5

must be such that for the highest

6

possible input frequency, the maximum output voltage

does not exceed 6 V. While C5 is charging up, the R

V

O

on Pin 9 is .approx. 6.7 kW. To obtain good linearity of the f/V converter the time constant resulting from R

and C

i

should be considerably less (1/5) than the time span of the negative half-cycle for the highest possible input frequency. The amount of remaining ripple on the output

, C

voltage on Pin 10 is dependent on C

and the internal

5

6

charge amplification.

Gi Vch C

=

∆V

O

The ripple ∆V

. However, the increasing speed will then also be

C

6

C

6

can be reduced by using larger values of

o

5

reduced. The value of this capacitor should be chosen to fit the

particular control loop where it is going to be used.

Pulse Blocking

The output of pulses can be blocked using Pin 18 (standby operation) and the system reset via the voltage monitor if

≥ –1.25 V. After cycling through the switching point

V

18

hysteresis, the output is released when V followed by a soft-start such as that after turn on.

Monitoring of the rotation can be carried out by connecting an RC network to Pin 18. In the event of a short or open circuit, the triac triggering pulses are cut off by the time delay which is determined by R and C. The capacitor C is discharged via an internal resistance

= 2 kW with each charge transfer process of the f/V

R

i

converter. If there are no more charge transfer processes C is charged up via R until the switch-off threshold is exceeded and the triac triggering pulses are cut off. For operation without trigger pulse blocking or monitoring of the rotation, Pins 18 and 16 must be connected together.

≤ –1.5 V

18

i

5

4 (20)

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

C = 1 F

10 V

R = 1 M

18



123

Figure 5. Operation delay

17 16 15

4

95 10363

Control Amplifier (Figure 2)

The integrated control amplifier with differential input compares the set value (Pin 11) with the instantaneous value on Pin 10 and generates a regulating voltage on the output Pin 12 (together with the external circuitry on Pin 12) which always tries to hold the actual voltage at the value of the set voltages. The amplifier has a transmittance of typically 1000 A/V and a bipolar current source output on Pin 12 which operates with typically ±110 A. The amplification and frequency response are determined by R out). For open loop operation, C

can be omitted. Pin 10 should be connected with

R

11

, C7, C8 and R11 (can be left

7

, C5, R6, R7, C7, C8 and

4

Pin 12 and Pin 8 with Pin 2. The phase angle of the triggering pulse can be adjusted using the voltage on Pin 11. An internal limitation circuit prevents the voltage on Pin 12 from becoming more negative than V

+ 1 V.

16

Load Limitation

The load limitation, with standard circuitry, provides absolute protection against overloading of the motor. the function of the load limiting takes account of the fact that motors operating at higher speeds can safely withstand large power dissipations than at lower speeds due to the increased action of the cooling fan. Similary, considerations have been made for short term overloads for the motor which are, in practice, often required. These finctions are not damaging and can be tolerated.

In each positive half-cycle, the circuit measures via R the load current on Pin 14 as a potential drop across R and produces a current proportional to the voltage on Pin 14. This current is available on Pin 15 and is integrated by C a large phase angle for current flow, the voltage on C exceeds an internally set threshold of approx. 7.3 V

. If, following high current amplitudes or

9

U211B2/ B3

(reference voltage Pin 16) then a latch is set and the load limiting is turned on. A current source (sink) controlled by the control voltage on Pin 15 now draws current from Pin 12 and lowers the control voltage on Pin 12 so that the phase angle  is increased to

The simultaneous reduction of the phase angle during which current flows causes firstly: a reduction of the rotational speed of the motor which can even drop to zero if the angular momentum of the motor is excessively large, and secondly: a reduction of the potential on C which in turn reduces the influence of the current sink on Pin 12. The control voltage can then increase again and bring down the phase angle. This cycle of action sets up a “balanced condition” between the “current integral” on Pin 15 and the control voltage on Pin 12.

Apart from the amplitude of the load current and the time during which current flows, the potential on Pin 12 and hence the rotational speed also affects the function of the load limiting. A current proportional to the potential on Pin 10 gives rise to a voltage drop across R so that the current measured on Pin 14 is smaller than the actual current through R

.

8

This means that higher rotational speeds and higher current amplitudes lead to the same current integral. Therefore, at higher speeds, the power dissipation must be greater than that at lower speeds before the internal threshold voltage on Pin 15 is exceeded. The effect of speed on the maximum power is determined by the resistor R

and can therefore be adjusted to suit each

10

individual application. If, after the load limiting has been turned on, the

momentum of the load sinks below the “o-momentum” set using R

, then V15 will be reduced. V12 can then in-

10

crease again so that the phase angle is reduced. A smaller phase angel corresponds to a larger momentum of the motor and hence the motor runs up - as long as this is allowed by the load momentum. For an already rotating machine, the effect of rotation on the measured “current integral” ensures that the power dissipation is able to increase with the rotational speed. the result is: a current controlled accelleration run-up., which ends in a small peak of accelleraton when the set point is reached. The latch of the load limiting is simultaneously reset. The speed of the motor is then again under control and it is capable of carrying its full load. The above mentioned peak of accelleration

10

depends upon the ripple of actual speed voltage. A large

8

amount of ripple also leads to a large peak of accelleration.

The measuring resistor R ensures that the amplitude of the voltage across it does not

9

8

exceed 600 mV.

.



max

10

should have a value which

9

, via Pin 14,

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

5 (20)

U211B2/ B3

Design Hints

Practical trials are normally needed for the exact determination of the values of the relevant components in the load limiting. To make this evaluation easier, the

following table shows the effect of the circuitry on the important parameters of the load limiting and summarises the general tendencies.

Parameters

R

10

P

max

P

min

P

/

max

min

t

d

t

r

P

– maximum continuous power dissipation P1 = f

max

– power dissipation with no rotation P1 = f

P

min

– operation delay time

t

d

– recovery time

t

r

increases decreases n.e. increases decreases n.e. increases n.e. n.e. n.e. decreases increases n.e. increases increases

n.e – no effect

Pulse Output Stage

The pulse output stage is short circuit protected and can typically deliver currents of 125 mA. For the design of smaller triggering currents, the function I

= f(RGT) has

GT

been given in the data sheets in the appendix.

Automatic Retriggering

The variable automatic retriggering prevents half cycles without current flow, even if the triac is turned off earlier e.g. due to a collector which is not exactly centered (brush lifter) or in the event of unsuccessful triggering. If it is necessary, another triggering pulse is generated after a time lapse which is determined by the repetition rate set by resistance between Pin 5 and Pin 3 (R maximum repetition rate (Pin 5 directly connected to Pin 3), the next attempt to trigger comes after a pause of

and this is repeated until either the triac fires or the

4.5 t

p

half-cycle finishes. If Pin 5 is connected, then only one trigger pulse per half-cycle is generated. Because the value of R repetition rate set using R

.

of C

2

determines the charging current of C2, any

5-3

is only valid for a fixed value

5-3

). With the

5-3

Component affected

R

9

n 0 0

(n)

n = 0

(n)

C

9

General Hints and Explanation of Terms

To ensure safe and trouble-free operation, the following points should be taken into consideration when circuits are being constructed or in the design of printed circuit boards.

– The connecting lines from C

should be as short as possible: The connection to Pin 2 should not carry any additional high current such as the load current. When selecting C temperature coefficient is desirable.

– The common (earth) connections of the set-point

generator, the tacho-generator and the final interference suppression capacitor C converter should not carry load current.

– The tacho-generator should be mounted without

influence by strong stray fields from the motor.

– The connections from R

10

as possible.

To achieve a high noise immunity, a maximum ramp voltage of 6 V should be used.

The typical resistance R

can be calculated from Iö as

ö

follows:

(kW)

R

ö

T(ms) 1.13(V) 10

+

CńnF) 6(V)

T = Period duration for mains frequency

(10 ms at 50 Hz)

C

= Ramp capacitor, max. ramp voltage 6 V

ö

and constant voltage drop at R

A 10% lower value of Rö (under worst case conditions) is recommended.

to Pin 7 and Pin 2

2

and C

should be as short

5

, a low

2

of the f/V

4

3

= 1.13 V.

ö

6 (20)

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

U211B2/ B3

V

Mains Supply

Trigger Pulse

Load Voltage

Load Current

V

GT

V

L

I

L

p

/2

t

p

t

pp

F

= 4.5 t

ö

3/2

p

Figure 6. Explanation of terms in phase relationship

95 10716

2

p

Design Calculations for Mains Supply

The following equations can be used for the evaluation of the series resistor R

V

R

1max

P

(R1max)

+

0.85

(V

Mmin

Mmax

2R

2I

–V

1

tot

Smin

Smax

)

R

2

–V

where:

= Mains voltage

V

M

V

= Supply voltage on Pin 3

S

= Total DC current requirement of the circuit

I

tot

I

Smax

I

p

I

x

can be easily evaluated from the figures 20 to 22.

R

1

+ Ip + I

= I

S

x

= Current requirement of the IC in mA = Average current requirement of the triggering pulse = Current requirement of other peripheral components

1min

VM–V

+

2I

Smin

Smax

for worst case conditions:

1

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

7 (20)

U211B2/ B3

Absolute Maximum Ratings

Reference point Pin 2, unless otherwise specified

Parameters Symbol Value Unit

Current requirement Pin 3 –I

t ≤ 10 ms

Synchronization current Pin 1

Pin 17 t t 10 ms Pin 1 t t 10 ms Pin 17

f/V converter Pin 8 Input current I

t t 10 ms

Load limiting Pin 14 Limiting current, neg. half wave I

t t 10 ms

Input voltage Pin 14

Pin 15

Phase control

Input voltage Pin 12 –V Input current Pin 12

Pin 6

Soft-start

Input voltage Pin 13 –V

Pulse output

Reverse voltage Pin 4 V

Pulse blocking

Input voltage Pin 18 –V

Amplifier

Input voltage Pin 11 Pin 9 open Pin 10

Reference voltage source

Output current Pin 16 I Storage temperature range T Junction temperature T Ambient temperature range T

I

syncV

S

–i

s

syncI

±i ±i

I

±i

I

±V –V

±I –I

R

V

I

–V

o

stg

j

amb

30 mA

100

5

mA

5

I I

35 35

3 mA

I

13

5 mA

35

i

I

I I

I

1

 to 0

V

16

0 to 7 V

500

1

V16 to 0 V

V

m

A

mA

VS to 5 V

I

V16 to 0 V

0 to V

S

V16 to 0

V

7.5 mA

–40 to +125 °C

125 °C

–10 to +100 °C

Thermal Resistance

Parameters Symbol Maximum Unit

Junction ambient DIP18

SO16 on p.c. SO16 on ceramic

8 (20)

R

thJA

120

K/W 180 100

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

Electrical Characteristics

U211B2/ B3

–VS = 13.0 V, T

= 25°C, reference point Pin 2, unless otherwise specified

amb

Parameters Test Conditions / Pins Symbol Min. Typ. Max. Unit

Supply voltage for mains op-

Pin 3 –V

eration Supply voltage limitation –IS = 4 mA Pin 3

= 30 mA

–I

S

DC current requirement –VS = 13.0 V Pin 3 I Reference voltage source –IL = 10 mA Pin 16

= 5 mA

–I

L

–V

Temperature coefficient Pin 16 –TC

Voltage monitoring

Turn-on threshold Pin 3 –V Turn-off threshold Pin 3 –V

Phase control currents

Synchronization current Pin 1

Pin 17

Voltage limitation

"

IL = 5 mA Pins 1 and 17

"

Reference ramp, figure 7 Charge current I7 = f (R6);

= 50 k to 1 MW Pin 7 I

R

6

Rö-reference voltage

a ≥ 180

°C Pins 6 and 3 V

Temperature coefficient Pin 6 TC Pulse output, figure 18 Pin 4 Output pulse current RGT = 0, VGT = 1.2 V I Reverse current I Output pulse width Cϕ = 10 nF t

Amplifier

Common mode signal range Pins 10 and 11 V10, Input bias current Pin 11 I Input offset voltage Pins 10 and 11 V Output current Pin 12 –I

Short circuit forward, transmittance

Figure 14

= f(V

I

12

) Pin 12 Y

10 -11

Pulse blocking, tacho-monitoring Pin 18 Logic-on –V Logic-off –V Input current V

= V

18

= V

V

18

TOFF 16

= 1.25 V

Output resistance R

–V –V

S Ref

VRef

SON

SOFF

I

syncI

I

syncV

V

7

Ref

ö

VöRef

o

or

p

IO

10

O

+I

O

TON

TOFF

I

O

S

S S

13.0 V

14.6

14.7

Limit

16.6

16.8

V

1.2 2.5 3.0 mA

8.6

8.3

8.9 9.2

9.1

V

0.5 mV/K

11.2 13.0 V

9.9 10.9 V

0.35 2.0 mA

0.35 2.0

I

1.4 1.6 1.8 V

1 20

m

A

1.06 1.13 1.18 V

0.5 mV/K

100 155 190 mA

0.01 3.0 80

11

V

16

–1 V

0.01 1

m

A

m

s

m

A

10 mV

75 88

f

110 120

1000

145 165

m

A

A/V

3.7 1.5 V

1.25 1.0

0.3 1

m

A

14.5

1.5 6 10 k

W

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

9 (20)

U211B2/ B3

O

m

O

p

pp20p

Frequency to voltage converter Pin 8 Input bias current I Input voltage limitation Figure 13

= –1 mA

I

= +1 mA

I

Turn-on threshold –V Turn-off threshold –V

Charge amplifier

Discharge current Figure 2

= 1 nF,

C

5

Pin 9 Charge transfer voltage Pins 9 to 16 V Charge transfer gain I10/I

9

Conversion factor Figure 2

= 1 nF, R6 = 100 k

C

5

Output operating range Pins 10 to 16 V Linearity Soft-start, figures 8, 9, 10, 11, 12 f/v-converter non-active Starting current V13 = V Final current V13 = 0.5 Pin 13

f/v-converter active

Starting current V13 = V Final current V13 = 0.5 Discharge current Restart pulse Pin 13 I Automatic retriggering, figure 19 Pin 5 Repetition rate R

= 0 t

5-3

R

= 15 k

5-3

Load limiting, figures 15, 16, 17 Pin 14 Operating voltage range Pin 14 V Offset current V10 = V

= V2 via 1 k

V

14

Input current V10 = 4.5 V Pin 14 I Output current V14 = 300 mV Pin 15–16 I Overload ON Pin 15–16 V

Pins 9 and 10 G

W

V8 = V2Pin 13 I

16,

16

Pin 13 I

W

16

Pin 14

W

Pin 15–16

UnitMax.Typ.Min.SymbolTest Conditions / PinsParameters

IB

–V

+V

TON

TOFF

I

dis

0.6 2

I

660

7.25

750

8.05

100 150 mV

20 50 mV

0.5 mA

ch

i

6.50 6.70 6.90 V

7.5 8.3 9.0

m

mV

V

K 5.5 mV/Hz

O

20 45 55

0-6 V



1 %

m

50 85 130

O

2 4 7

30 55 80

O

pp

I

O

0.5 3 10 mA

3 4.5 6 t

–1.0 1.0 V

5

12

m m

m

1.0

I

O

TON

0.1

60 90 120

110 140

7.05 7.4 7.7 V

A

A A

p

A

10 (20)

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

U211B2/ B3

240

200

°



160

120

Phase Angle ( )

80

0

95 10302

100

80

60



13

I ( A )

40

Phase Control

Reference Point Pin 2

10nF 4.7nF

2.2nF

C

=1.5nF



/t

0 0.2 0.4 0.6 0.8

R ( M )

Figure 7.

Soft Start

1.0

13

V ( V )

95 10305

13

V ( V )

10

8

6

4

2

0

10

Soft Start

8

f/V-Converter Active Reference Point Pin 16

6

4

Soft Start

f/V-Converter Non Active Reference Point Pin 16

t=f

(C3)

Figure 10.

95 10303



13

I ( A )

95 10304

20

f/V-Converter Non Active Reference Point Pin 16

0

02468

V13 ( V )

Figure 8.

100

Soft Start

80

f/V-Converter Active Reference Point Pin 16

60

40

20

0

02468

V13 ( V )

Figure 9.

2

0

10

95 10306

t=f

(C3)

Figure 11.

10

Soft Start

8

Reference Point Pin 16

6

13

V ( V )

4

2

0

t=f

10

Motor Standstill ( Dead Time )

Motor in Action

(C3)

95 10307

Figure 12.

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

11 (20)

U211B2/ B3

500

f/V–Converter

250

Reference Point Pin 2

m

0

8

I ( A )

–250

–500

–10 –8 –6 –4 –2

95 10308

V8 ( V )

Figure 13.

100

50

m

0

12

I ( A )

–50

Reference Point

–100

for I

= –4V

12

–300 –200 –100 0 200

95 10309

V

10–11

02

Control Amplifier

100

( V )

300

200

Load Limit Control

150

m

100

14–2

I ( A)

50

0

4

95 10311

024 6

V

(V)

10–16

8

Figure 16.

250

Load current detection

200

150

m

15–16

100

I ( A )

95 10312

50

V

10=V16

0

0 100 200 300 400

I15=f ( V

V

Shunt

14–2

)

( mV )

500 600

700

m

12–16

–I ( A)

95 10310

12 (20)

Figure 14.

200

Load Limit Control

150

100

50

0

024 6

V

( V )

15–16

Figure 15.

Figure 17.

100

Pulse Output

80

60

GT

I ( mA )

40

1.4V

VGT=0.8V

20

0

8

95 10313

0 200 400 600 800

RGT ( W )

1000

Figure 18.

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

U211B2/ B3

20

15

W

10

5–3

R ( k )

5

0

95 10314

50

40

30

W

1

R ( k )

20

Automatic Retriggering

0 6 12 18 24

tpp/t

p

Figure 19.

Mains Supply

6

5

Mains Supply

4

3

(R1)

P ( W )

2

1

95 10316

0

0102030

( kW )

R

1

40

30

Figure 21.

6

5

Mains Supply

P ( W )

4

3

(R1)

2

95 10315

10

0

04812

I

( mA )

tot

Figure 20.

1

95 10317

0

03 6 912

I

( mA )

tot

15

16

Figure 22.

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

13 (20)

U211B2/ B3

9

R

11

C

BZX55

F

m

2.2

10

C

R

W

100 k

8

C

F

m

4.7

9

C

W

470 k

F

m

2.2

10 V

6

220 nF

10 V

T1

100 nF

6

C

14

R

11

R

C

F

m

2.2

W

10 k

W

47 k

15

31

R

3

10 V

16

R

W

250 k

W

1 M

T2

voltage

Set speed

7

C

W

47 k

10 V F

m

2.2 /

W

220 k

W

13

R

47 k

10

11

13 12

14

W

7

R

15 k

5

C

4

220 nF

680 pF

C

9

W

5

1 k

8

7

R

56

R

/t

ö

C

2

ö

C

R

2

W

2.2 nF

Speed sensor

1 M

U211B2

4

S

16 15

17

18

3

R

1

D

1N4004

W

10

R

2.2 k

M

–V

GND

12

123

R

W

1.5 W

18 k

1

R

W

4

470 k

W

180

F

m

22

C

25 V

1

W

= 3 x 11 m R

1 W

8

95 10364

L

Figure 23. Speed control, automatic retriggering, load switch-off, soft start

The switch-off level at maximum load shows in principle the same speed dependency as the original version (see figure 2), but when reaching the maximum load, the motor is switched off completely.

14 (20)

230 V~

N

This function is effected by the thyristor (formed by T and T

which ignites when the voltage at Pin 15 reaches

2)

typ. 7.4 V (Reference point Pin 16). The circuit is thereby switched into the “stand-by” over the release Pin 18.

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

1

U211B2/ B3

F

m

2.2

10

C

R

10 V

6

C

31

R

100 nF

W

250 k

voltage

Set speed

7

C

W

100 k

11

R

1 M

220 nF

8

C

F

m

4.7

10 V

9

C

F

11

m

C

2.2

C

F

m

2.2

3

10 V

F

m

2.2 /10 V

W

13

R

47 k

10

11

13 12

14

W

7

15 k

R

5

C

4

220 nF

680 pF

C

9

W

5

1 k

8

567

R

/t

ö

C

2

ö

C

R

2

W

R

2.2 nF

Speed sensor

1 M

U211B2

S

16 15

GND –V

17

W

12

R

180

W

4

R

470 k

F

m

22

1

C

25 V

W

1 W

= 3 x 11 m

8

R

M

W

18 k

1

R

1234

1.5 W

18

T1

W

14

R

10 k

W

220 k

3

R

T2

1

D

10

R

1N4004

W

2.2 k

W

16

R

47 k

W

9

R

470 k

W

15

R

33 k

BZX55

95 10366

L

Figure 24. Speed control, automatic retriggering, load switch-off, soft-start

The maximum load regulation shows the principle in the same speed dependency as the original version (see figure 2). When reaching the maximum load, the control unit is turned to

, adjustable with R2. Then only I

a

max

flows. This function is effected by the thyristor, formed by T

and T

1

which ignites as soon as the voltage at Pin 15

2

reaches ca. 6.8 V (Reference point Pin 16). The potential

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

230 V~

N

at Pin 15 is lifted and kept by R

over the internally

14

operating threshold whereby the maximum load regulation starts and adjusts the control unit constantly to

(IO), inspite of a reduced load current. The motor

a

O

max

shows that the circuit is still in operation by a quiet buzzing noise.

15 (20)

U211B2/ B3

F

m

2.2

10

C

R

W

68 k

8

C

R

9

C

10 V

6

9

220 nF

W

1 M

F

m

4.7

100 nF

6

C

W

31

R

voltage

250 k

Set speed

7

C

W

11

R

1.5 M

3

C

F

m

2.2

10 V

13

R

47 k

F

m

2.2 /10 V 10

11

13 12

14

W

7

R

22 k

5

C

1 nF

4

C

220 nF

9

W

5

1 k

ö

R

W

1 M

R

Speed sensor

/t

ö

C

2

C

2.2 nF

8

7

2

R

56

U211B2

4

S

16 15

–V

95 10365

F

W

1 M

m

1 /10 V

W

220 k

11

C

22 nF

17

12

18

3

R

1

D

123

R

W

18 k

1.5 W

1

R

W

4

470 k

1N4004

M

GND

W

10

R

1 k

L

230 V~

N

Figure 25. Speed control, automatic retriggering, load limiting, soft-start, tacho control

W

220

F

m

22

1

C

25 V

W

= 3 x 11 m R

1 W

8

16 (20)

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

U211B2/ B3

W

470

min

18

Set speed

R

W

31

R

13

C

F

m

4.7

10 V

100 k

10 V F

m

10

13

R

C

max

Set speed

W

11

R

16 k

7

8

C

CNY 70

470 nF

W

4

C

220 nF

W

8

R

47 k

W

470 k

7

R

3

C

F

m

2.2

10 V

11

C

22 nF

10

11

13 12

14

U211B2

9

6

C

8

7

2

R

56

4

S

16 15

W

18 k

R

1.5 W

1

GND –V

123

5

R

W

220 k

17

18

4

R

1N4004

1

D

680 pF

ö

R

W

1 M

6

R

W

100

W

470 k

R

/t

ö

C

2

C

3

R

= 50 mA

GT

I

220 k

9

5

C

3.3 nF

W

4.7 k

R

W

100

470 nF

W

1.5 k

R

F

m

47

1

C

16

17

10

25 V

BZX55

3

Z

F

m

100

10 V

10

C

/ 8 W

W

3.5 k

1N4004

C9V1

15

R

2

D

Figure 26. Speed control with reflective opto coupler CNY70 as emitter

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

1

L

all diodes BYW83

ca 220 Pulses / Revolution

2

L

M

W

14

100

230 V~

R

150 nF

12

C

250 V~

95 10687

17 (20)

U211B2/ B3

9 V

min

14

Set speed

R

W

31

R

3

F

m

2.2

10 V

C

W

820 k

R

11

220 k

11

22 nF

F

m

10

C

F

m

47

10 V

6

C

470 nF

W

6

R

82 k

C

F

m

4.7

10 V

9

C

W

220 k

9

R

13

Set speed

R

C

max

W

18

R

470

CNY 70

W

7

R

16 k

F

m

8

7

470 nF

C

1

W

5

C

10

11

9

8

7

2

R

14 13 12

56

U211B2

ö

R

W

1 M

12

R

680 pF

/t

ö

C

10 k

3.3 nF

2

W

17

R

33 k

13

C

16

R

1 nF

4

C

5

W

R

2.2 k

4

W

S

100

17 16 15

GND –V

18 (20)

W

10 k

1

R

123

1.1 W

= 50 mA

GT

W

220 k

I

F

m

22

25 V

1

C

4

R

W

110 k

18

3

R

1N4004

1

D

M

W

100

W

10

95 10688

R

1.1 k

150 nF

250 V~

12

C

230 V~

Figure 27. Speed control, max. load control with reflective opto coupler CNY70 as emitter

TELEFUNKEN Semiconductors

W

= 3 x 0.1

8

R

Rev . A1, 29-May-96

U211B2/ B3

The circuit is designed as a speed control on the reflection-coupled principle with 4 periods per revolution and a max. speed of 30.000 rpm. The separation of the coupler from the rotating aperture should be 1 mm approximately. In this experimental circuit, the power supply for the coupler was provided externally because of the relatively high current consumption.

Dimensions in mm

Package: DIP18 – U211B2

Instructions for adjusting:

D

In the initial adjustment of the phase-control circuit,

should be adjusted so that when R

R

2

= 0 and R

14

in min. position, the motor just turns.

D

The speed can now be adjusted as desired by means of

between the limits determined by R13 and R14.

R

31

D

The switch-off power of the limit load control can be set by R

. The lower R9, the higher the switch-off

9

power.

31

are

Package: SO16 – U211B3

94 8877

94 8875

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96

19 (20)

U211B2/ B3

Ozone Depleting Substances Policy Statement

It is the policy of TEMIC TELEFUNKEN microelectronic GmbH to

1. Meet all present and future national and international statutory requirements.

2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment.

It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances (ODSs).

The Montreal Protocol ( 1987) and its London Amendments (1990 ) intend to severely restrict the use of ODSs and forbid their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these substances.

TEMIC TELEFUNKEN microelectronic GmbH semiconductor division has been able to use its policy of continuous improvements to eliminate the use of ODSs listed in the following documents.

1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively

2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental Protection Agency (EPA) in the USA

3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively.

TEMIC can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances.

We reserve the right to make changes to improve technical design and may do so without further notice.

Parameters can vary in different applications. All operating parameters must be validated for each customer

application by the customer. Should the buyer use TEMIC products for any unintended or unauthorized

application, the buyer shall indemnify TEMIC against all claims, costs, damages, and expenses, arising out of,

directly or indirectly, any claim of personal damage, injury or death associated with such unintended or

unauthorized use.

20 (20)

TEMIC TELEFUNKEN microelectronic GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany

Telephone: 49 (0)7131 67 2831, Fax number: 49 (0)7131 67 2423

TELEFUNKEN Semiconductors

Rev . A1, 29-May-96