Datasheet TDA5140A, TDA5140AT Datasheet (Philips)

INTEGRATED CIRCUITS

DATA SH EET

TDA5140A

Brushless DC motor drive circuit

Product specification
Supersedes data of March 1992
File under Integrated Circuits, IC02

Philips Semiconductors

April 1994

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

FEATURES

• Full-wave commutation (using push/pull drivers at the
output stages) without position sensors

• Built-in start-up circuitry

• Three push-pull outputs:

– 0.8 A output current (typ.)

APPLICATIONS

• VCR

• Laser beam printer

• Fax machine

• Blower

• Automotive.

– low saturation voltage
– built-in current limiter

• Thermal protection

• Flyback diodes

• Tacho output without extra sensor

• Position pulse stage for phase-locked-loop control

GENERAL DESCRIPTION

The TDA5140A is a bipolar integrated circuit used to drive
3-phase brushless DC motors in full-wave mode. The
device is sensorless (saving of 3 hall-sensors) using the
back-EMF sensing technique to sense the rotor position.

• Transconductance amplifier for an external control
transistor.

QUICK REFERENCE DATA Measured over full voltage and temperature range.

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

V
V

P
VMOT

supply voltage note 1 4 − 18 V
input voltage to the output

note 2 1.7 − 16 V

driver stages
V
I

DO

LIM

drop-out output voltage IO = 100 mA − 0.93 1.05 V

current limiting V

= 10 V; RO= 3.9 Ω 0.7 0.8 1 A

VMOT

Notes

1. An unstabilized supply can be used.

2. V

= VP; +AMP IN = −AMP IN = 0 V; all outputs IO = 0 mA.

VMOT

ORDERING INFORMATION

PACKAGE

EXTENDED TYPE NUMBER

PINS PIN POSITION MATERIAL CODE

TDA5140A 18 DIL plastic SOT102
TDA5140AT 20 SOL plastic SOT163A

April 1994 2

Philips Semiconductors Product specification

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Brushless DC motor drive circuit TDA5140A

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Fig.1 Block diagram (SOT102; DIL18).

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Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

PINNING

SYMBOL

MOT1 1 1 driver output 1
TEST 2 2 test input/output
n.c. 3 not connected
MOT2 3 4 driver output 2
VMOT 4 5 input voltage for the output driver stages
PG IN 5 6 position generator: input from the position detector sensor to the position

PG/FG 6 7 position generator/frequency generator: output of the rotation speed and position

GND2 7 8 ground supply return for control circuits
V

P

CAP-CD 9 10 external capacitor connection for adaptive communication delay timing
CAP-DC 10 11 external capacitor connection for adaptive communication delay timing copy
CAP-ST 11 12 external capacitor connection for start-up oscillator
CAP-TI 12 13 external capacitor connection for timing
+AMP IN 13 14 non-inverting input of the transconductance amplifier

−AMP IN 14 15 inverting input of the transconductance amplifier
AMP OUT 15 16 transconductance amplifier output (open collector)
MOT3 16 17 driver output 3
n.c. − 18 not connected
MOT0 17 19 input from the star point of the motor coils
GND1 18 20 ground (0 V) motor supply return for output stages

PIN

DIL18

8 9 positive supply voltage

PIN

SO20

DESCRIPTION

detector stage (optional); only if an external position coil is used

detector stages (open collector digital output, negative-going edge is valid)

April 1994 4

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

Fig.2 Pin configuration (SOT102; DIL18). Fig.3 Pin configuration (SOT163A; SO20L).

FUNCTIONAL DESCRIPTION

The TDA5140A offers a sensorless three phase motor
drive function. It is unique in its combination of sensorless
motor drive and full-wave drive. The TDA5140A offers
protected outputs capable of handling high currents and
can be used with star or delta connected motors. It can
easily be adapted for different motors and applications.
The TDA5140A offers the following features:

• Sensorless commutation by using the motor EMF.

• Built-in start-up circuit.

• Optimum commutation, independent of motor type or

motor loading.

• Built-in flyback diodes.

• Three phase full-wave drive.

• High output current (0.8 A).

• Outputs protected by current limiting and thermal

protection of each output transistor.

• Low current consumption by adaptive base-drive.

• Accurate frequency generator (FG) by using the

motor EMF.

• Amplifier for external position generator (PG) signal.

• Suitable for use with a wide tolerance, external PG

sensor.

• Built-in multiplexer that combines the internal FG and
external PG signals on one pin for easy use with a
controlling microprocessor.

• Uncommitted operational transconductance amplifier
(OTA), with a high output current, for use as a control
amplifier.

April 1994 5

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

LIMITING VALUES

In accordance with the Absolute Maximum Rating System (IEC 134).

SYMBOL PARAMETER CONDITIONS MIN. MAX. UNIT

V

P

V

I

V

VMOT

V

O

V

I

T

stg

T

amb

P

tot

V

es

supply voltage − 18 V
input voltage; all pins except

VI< 18 V −0.3 VP + 0.5 V

VMOT
VMOT input voltage −0.5 17 V
output voltage

AMP OUT and PG/FG GND V
MOT1, MOT2 and MOT3 −1V

input voltage CAP-ST, CAP-TI,

− 2.5 V

P
VMOT

+ V

DHF

V
V

CAP-CD and CAP-DC
storage temperature −55 +150 °C
operating ambient temperature 0 +70 °C
total power dissipation see Figs 4 and 5 −− W
electrostatic handling see “Handling” − 500 V

o

T ( C)

amb

MBD535

P

(W)

tot

2.28

1.05

3

2

0

50

0 200

50 100 150

70

Fig.4 Power derating curve (SOT102; DIL18).

HANDLING

Every pin withstands the ESD test in accordance with

“MIL-STD-883C class 2”

3 pulses + and 3 pulses − on each pin referenced to ground.

MBD536

o

T ( C)

amb

P
(W)

1.38

3

tot

2

1

0

50

0 200

50 100 150

70

Fig.5 Power derating curve (SOT163A; SO20L).

. Method 3015 (HBM 1500 Ω, 100 pF)

April 1994 6

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

CHARACTERISTICS

V

= 14.5 V; T

P

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

Supply

V

P

I

P

V

VMOT

Thermal protection

T

SD

∆T reduction in temperature before

=25°C; unless otherwise specified.

amb

supply voltage note 1 4 − 18 V
supply current note 2 − 3.7 5 mA
input voltage to the output driver

see Fig.1 1.7 − 16 V

stages

local temperature at

130 140 150 °C
temperature sensor causing
shut-down

after shut-down − T

− 30 − K

SD

switch-on

MOT0; centre tap

V
I

I

V
∆V

I

CSW

CSW

input voltage −0.5 − V
input bias current 0.5 V < VI< V
comparator switching level note 3 ±20 ±30 ±40 mV
variation in comparator

switching levels

V

hys

comparator input hysteresis − 75 −µV

MOT1, MOT2 and MOT3

V

∆V

DO

OL

drop-out output voltage IO = 100 mA − 0.93 1.05 V

variation in saturation voltage
between lower transistors

∆V

OH

variation in saturation voltage
between upper transistors

I

LIM

V

DHF

V

DLF

I

DM

current limiting V
diode forward voltage (diode DH)IO = −500 mA; notes 4

diode forward voltage (diode DL)IO = 500 mA; notes 4 and

peak diode current note 5 −− 1A

+AMP IN and −AMP IN

V

I

input voltage −0.3 − VP− 1.7 V
differential mode voltage without

'latch-up'

I

b

C

I

V

offset

input bias current −− 650 nA
input capacitance − 4 − pF
input offset voltage −− 10 mV

V

− 1.5 V −10 − 0 µA

VMOT

VMOT

−3 0 +3 mV

I

= 500 mA − 1.65 1.80 V

O

IO = 100 mA −− 180 mV

IO = −100 mA −− 180 mV

= 10 V; RO= 6.8 Ω 0.7 0.8 1 A

VMOT

−− 1.5 V

and 5; see Fig.1

−1.5 −−V

5; see Fig.1

−− ±V

P

V

April 1994 7

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

AMP OUT (open collector)

I

I

V

sat

V

O

SR slew rate R
G

tr

PG IN

V

I

I

b

R

I

V

CWS

V

hys

PG/FG (open collector)

V

OL

V

OH(max)

t

THL

δ duty factor − 50 − %
t

PL

CAP-ST

I

sink

I

source

V

SWL

V

SWH

CAP-TI

I

sink

I

source

V

SWL

V

SWM

V

SWH

output sink current 40 −−mA
saturation voltage II = 40 mA − 1.5 2.1 V
output voltage −0.5 − +18 V

= 330 Ω; CL = 50 pF − 60 − mA/µs

L

transfer gain 0.3 −−S

input voltage −0.3 − +5 V
input bias current −− 650 nA
input resistance 5 − 30 kΩ
comparator switching level 86 − 107 mV
comparator input hysteresis −±8− mV

LOW level output voltage IO = 1.6 mA −− 0.4 V
maximum HIGH level output

V

P

−−V

voltage
HIGH-to-LOW transition time CL = 50 pF; RL = 10 kΩ− 0.5 −µs
ratio of PG/FG frequency and

− 1 : 2 −

commutation frequency

pulse width LOW after a PG IN pulse 5 7 18 µs

output sink current 1.5 2.0 2.5 µA
output source current −2.5 −2.0 −1.5 µA
LOW level switching voltage − 0.20 − V
HIGH level switching voltage − 2.20 − V

output sink current − 28 −µA
output source current 0.05 V < V

0.3V<V

CAP-TI

< 0.3 V −−57 −µA

CAP-TI

< 2.2 V −−5−µA
LOW level switching voltage − 50 − mV
MIDDLE level switching voltage − 0.30 − V
HIGH level switching voltage − 2.20 − V

April 1994 8

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

SYMBOL PARAMETER CONDITIONS MIN. TYP. MAX. UNIT

CAP-CD

I

sink

I

source

I

sink/Isource

V

IL

V

IH

CAP-DC

I

sink

I

source

I

sink/Isource

V

IL

V

IH

Notes

1. An unstabilized supply can be used.

2. V

VMOT

3. Switching levels with respect to MOT1, MOT2 and MOT3.

4. Drivers are in the high-impedance OFF-state.

5. The outputs are short-circuit protected by limiting the current and the IC temperature.

output sink current 10.6 16.2 22 µA
output source current −5.3 −8.1 −11 µA
ratio of sink to source current 1.85 2.05 2.25
LOW level input voltage 850 875 900 mV
HIGH level input voltage 2.3 2.4 2.55 V

output sink current 10.1 15.5 20.9 µA
output source current −20.9 −15.5 −10.1 µA
ratio of sink to source current 0.9 1.025 1.15
LOW level input voltage 850 875 900 mV
HIGH level input voltage 2.3 2.4 2.55 V

= VP, all other inputs at 0 V; all outputs at VP; IO = 0 mA.

APPLICATION INFORMATION

(1) Value selected for 3 Hz start-up oscillator frequency.

Fig.6 Application diagram without use of the operational transconductance amplifier (OTA).

April 1994 9

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

Introduction (see Fig.7)

Full-wave driving of a three phase motor requires three
push-pull output stages. In each of the six possible states
two outputs are active, one sourcing (H) and one sinking
(L). The third output presents a high impedance (Z) to the
motor which enables measurement of the motor
back-EMF in the corresponding motor coil by the EMF
comparator at each output. The commutation logic is
responsible for control of the output transistors and
selection of the correct EMF comparator. In Table 1 the
sequence of the six possible states of the outputs has
been depicted.

Table 1 Output states.

STATE MOT1

(1)

MOT2

(1)

MOT3

(1)

1ZLH
2HLZ
3HZL
4ZHL
5LHZ
6LZH

Note

1. H = HIGH state;
L = LOW state;
Z = high impedance OFF-state.

Because of high inductive loading the output stages
contain flyback diodes. The output stages are also
protected by a current limiting circuit and by thermal
protection of the six output transistors.

The detected zero-crossings are used to provide speed
information. The information has been made available on
the PG/FG output pin. This is an open collector output and
provides an output signal with a frequency that is half the
commutation frequency. A VCR scanner also requires a
PG phase sensor. This circuit has an interface for a simple
pick-up coil. A multiplexer circuit is also provided to
combine the FG and PG signals in time.

The system will only function when the EMF voltage from
the motor is present. Therefore, a start oscillator is
provided that will generate commutation pulses when no
zero-crossings in the motor voltage are available.

A timing function is incorporated into the device for internal
timing and for timing of the reverse rotation detection.

The TDA5140A also contains an uncommitted
transconductance amplifier (OTA) that can be used as a
control amplifier. The output is capable of directly driving
an external power transistor.

The TDA5140A is designed for systems with low current
consumption: use of I2L logic, adaptive base drive for the
output transistors (patented), possibility of using a pick-up
coil without bias current.

The zero-crossing in the motor EMF (detected by the
comparator selected by the commutation logic) is used to
calculate the correct moment for the next commutation,
that is, the change to the next output state. The delay is
calculated (depending on the motor loading) by the
adaptive commutation delay block.

April 1994 10

Philips Semiconductors Product specification

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Brushless DC motor drive circuit TDA5140A

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April 1994 11

Fig.7 Typical application of the TDA5140A as a scanner driver, with use of OTA.

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Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

Adjustments

The system has been designed in such a way that the
tolerances of the application components are not critical.
However, the approximate values of the following
components must still be determined:

• The start capacitor; this determines the frequency of the

start oscillator.

• The two capacitors in the adaptive commutation delay

circuit; these are important in determining the optimum
moment for commutation, depending on the type and
loading of the motor.

• The timing capacitor; this provides the system with its

timing signals.

T

HE START CAPACITOR (CAP-ST)

This capacitor determines the frequency of the start
oscillator. It is charged and discharged, with a current of
2 µA, from 0.05 to 2.2 V and back to 0.05 V. The time
taken to complete one cycle is given by:

t

= (2.15 × C) s (with C in µF)

start

The start oscillator is reset by a commutation pulse and so
is only active when the system is in the start-up mode. A
pulse from the start oscillator will cause the outputs to
change to the next state (torque in the motor). If the
movement of the motor generates enough EMF the
TDA5140A will run the motor. If the amount of EMF
generated is insufficient, then the motor will move one step
only and will oscillate in its new position. The amplitude of
the oscillation must decrease sufficiently before the arrival
of the next start pulse, to prevent the pulse arriving during
the wrong phase of the oscillation. The oscillation of the
motor is given by:

f

osc

=

1

---------------------------------- ­K

I× p×

t

---------------------- -

2π

J

where:

= torque constant (N.m/A)

K

t

I = current (A)
p = number of magnetic pole-pairs
J = inertia J (kg.m2)

Example: J = 72 × 10-6kg.m2, K = 25 × 10-3N.m/A, p = 6
and I = 0.5 A; this gives f

= 5 Hz. If the damping is high

osc

then a start frequency of 2 Hz can be chosen or t = 500 ms,
thus C = 0.5/2 = 0.25 µF, (choose 220 nF).

T

HE ADAPTIVE COMMUTATION DELAY (CAP-CD AND

CAP-DC)
In this circuit capacitor CAP-CD is charged during one

commutation period, with an interruption of the charging
current during the diode pulse. During the next
commutation period this capacitor (CAP-CD) is discharged
at twice the charging current. The charging current is

8.1 µA and the discharging current 16.2 µA; the voltage
range is from 0.9 to 2.2 V. The voltage must stay within this
range at the lowest commutation frequency of interest, f

f 1.3×

6–

×

6231

------------ ­f

c1

(C in nF)

8.1 10

C

==

--------------------------

C1

If the frequency is lower, then a constant commutation
delay after the zero-crossing is generated by the discharge

from 2.2 to 0.9 V at 16.2 µA.
maximum delay = (0.076 × C) ms (with C in nF)
Example: nominal commutation frequency = 900 Hz and

the lowest usable frequency = 400 Hz, so:

CAP-CD

6231

------------ ­400

(choose 18 nF)

15.6==

The other capacitor, CAP-DC, is used to repeat the same
delay by charging and discharging with 15.5 µA. The same
value can be chosen as for CAP-CD. Figure 8 illustrates
typical voltage waveforms.

:

April 1994 12

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

Fig.8 CAP-CD and CAP-DC typical voltage waveforms in normal running mode.

THE TIMING CAPACITOR (CAP-TI)
Capacitor CAP-TI is used for timing the successive steps

within one commutation period; these steps include some
internal delays.

The most important function is the watchdog time in which
the motor EMF has to recover from a negative diode-pulse
back to a positive EMF voltage (or vice versa). A watchdog
timer is a guarding function that only becomes active when
the expected event does not occur within a predetermined
time.

The EMF usually recovers within a short time if the motor
is running normally (<<ms). However, if the motor is
motionless or rotating in the reverse direction, then the
time can be longer (>>ms).

A watchdog time must be chosen so that it is long enough
for a motor without EMF (still) and eddy currents that may
stretch the voltage in a motor winding; however, it must be
short enough to detect reverse rotation. If the watchdog

time is made too long, then the motor may run in the wrong
direction (with little torque).

The capacitor is charged, with a current of 57 µA, from

0.2 to 0.3 V. Above this level it is charged, with a current of
5 µA, up to 2.2 V only if the selected motor EMF remains
in the wrong polarity (watchdog function). At the end, or, if
the motor voltage becomes positive, the capacitor is
discharged with a current of 28 µA. The watchdog time is
the time taken to charge the capacitor, with a current of
5 µA, from 0.3 to 2.2 V.

To ensure that the internal delays are covered CAP-TI
must have a minimum value of 2 nF. For the watchdog
function a value for CAP-TI of 10 nF is recommended.

To ensure a good start-up and commutation, care must be
taken that no oscillations occur at the trailing edge of the
flyback pulse. Snubber networks at the outputs should be
critically damped.

Typical voltage waveforms are illustrated by Fig.9.

April 1994 13

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

If the chosen value of CAP-TI is too small oscillations can occur in certain positions of a blocked rotor. If the chosen value is too large, then it
is possible that the motor may run in the reverse direction (synchronously with little torque).

Fig.9 Typical CAP-TI and V

voltage waveforms in normal running mode.

MOT1

Other design aspects

There are other design aspects concerning the application
of the TDA5140A besides the commutation function. They
are:

• Generation of the tacho signal FG

• A built-in interface for a PG sensor

• General purpose operational transconductance

amplifier (OTA)

• Possibilities of motor control

• Reliability.

FG

SIGNAL

The FG signal is generated in the TDA5140A by using the
zero-crossing of the motor EMF from the three motor
windings. Every zero-crossing in a (star connected) motor
winding is used to toggle the FG output signal. The FG
frequency is therefore half the commutation frequency.
All transitions indicate the detection of a zero-crossing
(except for PG). The negative-going edges are called FG
pulses because they generate an interrupt in a controlling
microprocessor.

The accuracy of the FG output signal (jitter) is very good.
This accuracy depends on the symmetry of the motor's
electromagnetic construction, which also effects the
satisfactory functioning of the motor itself.

Example: A 3-phase motor with 6 magnetic pole-pairs at
1500 rpm and with a full-wave drive has a commutation
frequency of 25 × 6 × 6 = 900 Hz, and generates a tacho
signal of 450 Hz.

PG

SIGNAL

The accuracy of the PG signal in applications such as VCR
must be high (phase information). This accuracy is
obtained by combining the accurate FG signal with the PG
signal by using a wide tolerance external PG sensor. The
external PG signal (PG IN) is only used as an indicator to
select a particular FG pulse. This pulse differs from the

other FG pulses in that it has a short LOW-time of 18 µs
after a HIGH-to-LOW transition. All other FG pulses have
a 50% duty factor (see Fig.10).

For more information also see

EIE/AN 93014”

.

“application note

April 1994 14

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

Fig.10 Timing and the FG and PG IN signals.

The special PG pulse is derived from the negative-going
zero-crossing from the MOT3 output (pin 16). The external
PG signal (PG IN on pin 5) must sense a positive-going
voltage (>80 mV) within 1.5 to 7.5 commutation periods
before the negative-going zero-crossing in MOT3
(see Fig.10).

The voltage requirements of the PG IN input are such that
an inexpensive pick-up coil can be used as a sensor
(see Fig.11).

Example: If p = 6, then one revolution contains 6 × 6=36
commutations. The tolerance is 6 periods, that is 60
degrees (mechanically) or 6.67 ms at 1500 rpm.

If a PG sensor is not used, the PG IN input must be
grounded, this will result in a 50% duty factor FG signal.

2.2 kΩ

22 nF

MBD696

PG IN

GND2

Fig.11 Pick-up coil as PG sensor.

April 1994 15

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

THE OPERATIONAL TRANSCONDUCTANCE AMPLIFIER (OTA)
The OTA is an uncommitted amplifier with a high output

current (40 mA) that can be used as a control amplifier.
The common mode input range includes ground (GND)
and rises to VP− 1.7 V. The high sink current enables the
OTA to drive a power transistor directly in an analog
control amplifier.

Although the gain is not extremely high (0.3 S), care must
be taken with the stability of the circuit if the OTA is used
as a linear amplifier as no frequency compensation has
been provided.

The convention for the inputs (inverting or not) is the same
as for a normal operational amplifier: with a resistor (as
load) connected from the output (AMP OUT) to the positive
supply, a positive-going voltage is found when the
non-inverting input (+AMP IN) is positive with respect to
the inverting input (−AMP IN). Confusion is possible
because a 'plus' input causes less current, and so a
positive voltage.

M

OTOR CONTROL

DC motors can be controlled in an analog manner using
the OTA.

ELIABILITY

R

It is necessary to protect high current circuits and the

output stages are protected in two ways:

• Current limiting of the 'lower' output transistors. The
'upper' output transistors use the same base current as
the conducting 'lower' transistor (+15%). This means
that the current to and from the output stages is limited.

• Thermal protection of the six output transistors is
achieved by each transistor having a thermal sensor
that is active when the transistor is switched on. The
transistors are switched off when the local temperature
becomes too high.

It is possible, that when braking, the motor voltage (via the
flyback diodes and the impedance on VMOT) may cause
higher currents than allowed (>0.6 A). These currents
must be limited externally.

For the control an external transistor is required. The OTA
can supply the base current for this transistor and act as a
control amplifier (see Fig.7).

April 1994 16

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

PACKAGE OUTLINES

seating plane

3.9

3.4

0.85
max

22.00

21.35

3.7

4.7

max

max

0.51
min

2.54
(8x)

1.4 max

18

1

0.53
max

10

0.254 M

6.48

6.14

9

0.32 max

8.25

7.80

7.62

9.5

8.3

MSA259

Dimensions in mm.

Fig.12 18-pin dual in-line; plastic (SOT102).

April 1994 17

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

handbook, full pagewidth

S

pin 1

index

13.0

12.6

0.1 S

0.9

(4x)

0.4

1120

2.45

0.3

2.25

0.1

110

detail A

1.27

0.49

0.36

0.25 M

(20x)

7.6

7.4

10.65

10.00

1.1

0.5

1.1

1.0

0.32

0.23

0 to 8

MBC234 - 1

A

2.65

2.35

o

Dimensions in mm.

Fig.13 20-pin small-outline; plastic (SO20L; SOT163A).

April 1994 18

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

SOLDERING
Plastic dual in-line packages

Y DIP OR WAVE

B
The maximum permissible temperature of the solder is

260 °C; this temperature must not be in contact with the
joint for more than 5 s. The total contact time of successive
solder waves must not exceed 5 s.

The device may be mounted up to the seating plane, but
the temperature of the plastic body must not exceed the
specified storage maximum. If the printed-circuit board has
been pre-heated, forced cooling may be necessary
immediately after soldering to keep the temperature within
the permissible limit.

R

EPAIRING SOLDERED JOINTS

Apply the soldering iron below the seating plane (or not
more than 2 mm above it). If its temperature is below
300 °C, it must not be in contact for more than 10 s; if
between 300 and 400 °C, for not more than 5 s.

Plastic small-outline packages

BYWAVE
During placement and before soldering, the component

must be fixed with a droplet of adhesive. After curing the
adhesive, the component can be soldered. The adhesive
can be applied by screen printing, pin transfer or syringe
dispensing.

Y SOLDER PASTE REFLOW

B

Reflow soldering requires the solder paste (a suspension
of fine solder particles, flux and binding agent) to be
applied to the substrate by screen printing, stencilling or
pressure-syringe dispensing before device placement.

Several techniques exist for reflowing; for example,
thermal conduction by heated belt, infrared, and
vapour-phase reflow. Dwell times vary between 50 and
300 s according to method. Typical reflow temperatures
range from 215 to 250 °C.

Preheating is necessary to dry the paste and evaporate
the binding agent. Preheating duration: 45 min at 45 °C.

R

EPAIRING SOLDERED JOINTS (BY HAND-HELD SOLDERING

IRON OR PULSE

-HEATED SOLDER TOOL)

Fix the component by first soldering two, diagonally
opposite, end pins. Apply the heating tool to the flat part of
the pin only. Contact time must be limited to 10 s at up to
300 °C. When using proper tools, all other pins can be
soldered in one operation within 2 to 5 s at between 270
and 320 °C. (Pulse-heated soldering is not recommended
for SO packages.)

For pulse-heated solder tool (resistance) soldering of VSO
packages, solder is applied to the substrate by dipping or
by an extra thick tin/lead plating before package
placement.

Maximum permissible solder temperature is 260 °C, and
maximum duration of package immersion in solder bath is
10 s, if allowed to cool to less than 150 °C within 6 s.
Typical dwell time is 4 s at 250 °C.

A modified wave soldering technique is recommended
using two solder waves (dual-wave), in which a turbulent
wave with high upward pressure is followed by a smooth
laminar wave. Using a mildly-activated flux eliminates the
need for removal of corrosive residues in most
applications.

April 1994 19

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

DEFINITIONS

Data sheet status

Objective specification This data sheet contains target or goal specifications for product development.
Preliminary specification This data sheet contains preliminary data; supplementary data may be published later.
Product specification This data sheet contains final product specifications.

Limiting values

Limiting values given are in accordance with the Absolute Maximum Rating System (IEC 134). Stress above one or
more of the limiting values may cause permanent damage to the device. These are stress ratings only and operation
of the device at these or at any other conditions above those given in the Characteristics sections of the specification
is not implied. Exposure to limiting values for extended periods may affect device reliability.

Application information

Where application information is given, it is advisory and does not form part of the specification.

LIFE SUPPORT APPLICATIONS

These products are not designed for use in life support appliances, devices, or systems where malfunction of these
products can reasonably be expected to result in personal injury. Philips customers using or selling these products for
use in such applications do so at their own risk and agree to fully indemnify Philips for any damages resulting from such
improper use or sale.

April 1994 20

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

NOTES

April 1994 21

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

NOTES

April 1994 22

Philips Semiconductors Product specification

Brushless DC motor drive circuit TDA5140A

NOTES

April 1994 23

Philips Semiconductors – a worldwide company

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Philips Semiconductors