Datasheet HV9921, HV9922, HV9923 Datasheet

HV9921/HV9922/HV9923

3-Pin Switch-Mode LED Lamp Driver ICs

Features

• Constant output current:

- HV9921 – 20mA

- HV9922 – 50mA

- HV9923 – 30mA

• Universal 85 - 264VAC operation

• Fixed off-time buck converter

• Internal 475V power MOSFET

Applications

• Decorative lighting

• Low power lighting fixtures

Description

HV9921/HV9922/HV9923 are pulse-width modulated
(PWM), high-efficiency, LED driver control ICs. They
allow efficient operation of LED strings from voltage
sources ranging up to 400VDC. HV9921/22/23 include
an internal high voltage switching MOSFET controlled
with fixed off-time (T
LED string is driven at constant current, thus providing
constant light output and enhanced reliability. The out­put current is internally fixed at 20mA for HV9921,
50mA for HV992, and 30mA for HV9923. The peak cur­rent control scheme provides good regulation of the
output current throughout the universal AC line voltage
range of 85 to 264VAC or DC input voltage of 20 to
400V.

) of approximately 10s. The

OFF

 2014 Microchip Technology Inc. DS20005311A-page 1

HV9921/HV9922/HV9923

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DS20005311A-page 2  2014 Microchip Technology Inc.

PIN DIAGRAM

1

2

3

(SOT-89)

HV9921/HV9922/HV9923

2

1

3

TO-92TO-243AA

See Table 2-1 for Pin information.

TYPICAL APPLICATION CIRCUIT

AC

HV9921/22/23

3 VDD

GND

2

DRAIN 1

LED

-

LED

1

n

 2014 Microchip Technology Inc. DS20005311A-page 3

HV9921/HV9922/HV9923

1.0 ELECTRICAL CHARACTERISTICS

ABSOLUTE MAXIMUM RATINGS

Supply Voltage VDD................................ -0.3V to +10V

Supply Current I

Operating Ambient temperature ...........-40°C to +85°C

Operating Junction Temperature ........-40°C to +125°C

Storage temperature ..........................-65°C to +150°C

Power dissipation @+25°C for TO-92 .............740 mW

Power dissipation @+25°C for SOT-89....... 1600 mW*

* Mounted on FR4 board, 24mmx25mmx1.57mm

Note: Stresses above those listed under “Absolute
Maximum Ratings” may cause permanent damage to
the device. This is a stress rating only and functional
operation of the device at those or any other condi­tions, above those indicated in the operational listings
of this specification, is not implied. Exposure to maxi­mum rating conditions for extended periods may affect
device reliability.

1.1 ELECTRICAL SPECIFICATIONS

..............................................+5mA

DD

TABLE 1-1: ELECTRICAL CHARACTERISTICS1

Symbol Parameter Notes Min Typ Max Units Conditions

Regulator (VDD)

V

DD

V

DRAIN

V

UVLO

V

UVLO

I

DD

Output (DRAIN)

V

BR

R

ON

C

DRAIN

I

SAT

Current Sense Comparator

I

THL

T

BLANK

T

ON(MIN)

OFF-Time Generator

T

OFF

1 Specifications are T
2 Applies over the full operating ambient temperature range of -40°C < T
3 For design guidance only

V

Regulator Output - - 7.5 - V

DD

V

V

V

Operating Supply Current - - 200 350 A

Breakdown Voltage

ON Resistance - - - 210 

Output Capacitance

MOSFET Saturation Current

Threshold Current - HV9921

Threshold Current - HV9922

Threshold Current - HV9923

Leading Edge Blanking Delay

Supply Voltage - 20 - - V

DRAIN

Under-voltage Threshold - 5.0 - - V

DD

Under-voltage Lockout Hysteresis - - 200 - mV

DD

2

475 - - V

3

3

2

2

2

2, 3

-15pFV

100 150 - mA

18.5 - 25.5 mA

49 - 63 mA

28.2 - 38.2 mA

200 300 400 ns

V

DD(EXT)

= 40V

I

DRAIN

I

DRAIN

I

DRAIN

DRAIN

Minimum ON Time - - - 650 ns

OFF Time - 8 10.5 13 S

= 25°C, V

A

= 50V unless otherwise noted.

DRAIN

< +125°C.

A

= 8.5V, V

DRAIN

= 20mA (HV9921)
= 50mA (HV9922)
= 30mA (HV9923)

= 400V

DS20005311A-page 4  2014 Microchip Technology Inc.

HV9921/HV9922/HV9923

THERMAL RESISTANCE

Package θja

TO-92 132°C/W

TO-243AA(SOT-89) 133°C/W

FIGURE 1-1: TYPICAL PERFORMANCE CHARACTERISTICS (TJ= 25°C UNLESS OTHERWISE NOTED)

1.10

1.05

1.00

0.95

0.90

0.85

Normalized Threshold Current

0.80

-40 -15 10 35 60 85 110

Junction Temperature, °C

12

200

180

160

140

120

100

80

60

ON Resistance (μΩ)

40

20

0

-40 -15 10 35 60 85 110

Junction Temperature (°C)

1000

10

8

6

4

OFF Time (μS)

2

0

-40 -15 10 35 60 85 110

Junction Temperature (°C)

580

570

560

550

540

530

520

510

DRAIN Breakdown Voltage (V)

500

490

-40 -15 10 35 60 85 110

Junction Temperature (°C)

100

10

DRAIN Capacitance (pF)

1

0 10 20 30 40

180

160

140

120

100

80

60

DRAIN Current (mA)

40

20

0

0 10 20 30 40

DRAIN Voltage (V)

TJ = 25°C
TJ = 125°C

DRAIN Voltage (V)

 2014 Microchip Technology Inc. DS20005311A-page 5

HV9921/HV9922/HV9923

2.0 PIN DESCRIPTION

See Pin Diagram on page 3 for the figures.

TABLE 2-1: PIN DESCRIPTION

Pin # Name Description

1 Drain Drain terminal of the output switching MOSFET and a linear regulator input

2 GND Common connection for all circuits

3 VDD

Power Supply pin for all control circuits. By pass this pin with a 0.1 F low-impedance
capacitor

3.0 FUNCTIONAL DESCRIPTION

The HV9921/22/23 are PWM peak current controllers
designed to control a buck converter topology in contin­uous conduction mode (CCM). The output current is
internally preset at 20mA for HV9921, 50mA for
HV992, and 30mA for HV9923.

When the input voltage of 20 to 400V appears at the
DRAIN pin, the internal high-voltage linear regulator
seeks to maintain a voltage of 7.5VDC at the V
Until this voltage exceeds the internally programmed
under-voltage threshold, the output switching MOSFET
is non-conductive. When the threshold is exceeded,
the MOSFET turns on. The input current begins to flow
into the DRAIN pin. Hysteresis is provided in the under­voltage comparator to prevent oscillation.

When the input current exceeds the internal preset
level, a current sense comparator resets an RS flip­flop, and the MOSFET turns off. At the same time, a
one-shot circuit is activated that determines the dura­tion of the off-state (10.5s typical). As soon as this
time is over, the flip-flop sets again. The new switching
cycle begins.

A “blanking” delay of 300ns is provided that prevents
false triggering of the current sense comparator due to
the leading edge spike caused by circuit parasitics.

DD

pin.

4.0 APPLICATION INFORMATION

HV9921/22/23 are low-cost off-line buck converter ICs
specifically designed for driving multi-LED strings.
They can be operated from either universal AC line
range of 85 to 264VAC, or 20 to 400VDC, and drive up
to tens of high-brightness LEDs. All LEDs can be run in
series, and the HV9921/22/23 regulate at constant cur­rent, yielding uniform illumination. HV9921/22/23 are
compatible with triac dimmers. The output current is
internally fixed at 20mA for HV9921, 50mA for HV9922,
and 30mA for HV9923. These parts are available in
space saving TO-92 and SOT-89 packages.

4.1 Selecting L1 and D1

There is a certain trade-off to be considered between
optimal sizing of the output inductor L1 and the toler­ated output current ripple. The required value of L1 is
inversely proportional to the ripple current I

VOT



OFF

------------------------------ -

L1

=

is the forward voltage of the LED string. T

V

O

off-time of HV9921/22/23. The output current in the
LED string (I

where I
The ripple current introduces a peak-to-average error
in the output current setting that needs to be accounted
for. Due to the constant off-time control technique used
in HV9921/22/23, the ripple current is independent of
the input AC or DC line voltage variation. Therefore, the
output current will remain unaffected by the varying
input voltage.

Adding a filter capacitor across the LED string can

reduce the output current ripple even further, thus per­mitting a reduced value of L1. However, keep in mind
that the peak-to-average current error is affected by the
variation of T
accuracy might be sacrificed at large ripple current in
L1.

Another important aspect of designing an LED driver

with the HV9921/22/23 is related to certain parasitic
elements of the circuit, including distributed coil capac­itance of L1, junction capacitance and reverse recovery
of the rectifier diode D1, capacitance of the printed cir­cuit board traces C
of the controller itself. These parasitic elements affect
the efficiency of the switching converter and could
potentially cause false triggering of the current sense
comparator if not properly managed. Minimizing these
parasitics is essential for efficient and reliable operation
of the HV9921/22/23.

) is calculated then as:

O

IOI

is the current sense comparator threshold.

TH

. Therefore, the initial output current

OFF

PCB

IO

1

–=

-- - IO

TH

2

and output capacitance C

in it.

O

OFF

is the

DRAIN

DS20005311A-page 6  2014 Microchip Technology Inc.

HV9921/HV9922/HV9923

Coil capacitance of inductors is typically provided in the
manufacturer’s data books either directly or in terms of
the self-resonant frequency (SRF).



=

SRF 1 2 LC

where L is the inductance value, and C







L

is the coil

L

capacitance.) Charging and discharging this capaci­tance every switching cycle causes high-current spikes
in the LED string. Therefore, connecting a small capac­itor C

(~10nF) is recommended to bypass these

O

spikes.

Using an ultra-fast rectifier diode for D1 is recom­mended to achieve high efficiency and reduce the risk
of false triggering of the current sense comparator.
Using diodes with shorter reverse recovery time, t
and lower junction capacitance, C
performance. The reverse voltage rating, V

, achieves better

J

, of the

R

diode must be greater than the maximum input voltage
of the LED lamp.

The total parasitic capacitance present at the DRAIN

pin of the HV9921/22/23 can be calculated as:

CPC

+++=

DRAINCPCBCLCJ

4.2 Estimating Power Loss

Discharging the parasitic capacitance CP into the
DRAIN pin of the HV9921/22/23 is responsible for the
bulk of the switching power loss. It can be estimated
using the following equation:

2

V

C

IN

P



----------------- - V



2

I

IN

SAT

where F

P

SWITCH

is the switching frequency, I

S

rated DRAIN current of the HV9921/22/23. The switch­ing loss is the greatest at the maximum input voltage.

The switching frequency is given by the following equa-

,

rr

tion.

VINVO–

F

------------------------ -=

S

V



INTOFF

When the HV9921/22/23 LED driver is powered from
the full-wave rectified AC input, the switching power
loss can be estimated as:

P

SWITCH

1

------------------- - V



2T

OFF

ACCP

2I

SATtrr

F

trr+

=

is the satu-

SAT

+VACVO–

S

When the switching MOSFET turns on, the capaci­tance C

is discharged into the DRAIN pin of the IC.

P

The discharge current is limited to about 150mA typi-

cally. However, it may become lower at increased junc­tion temperature. The duration of the leading edge
current spike can be estimated as:

VINCP

SPIKE

------------------- - trr+=
I

SAT

T

In order to avoid false triggering of the current sense
comparator, C

must be minimized in accordance with

P

the following expression:

where T

BLANK(MIN)

200ns, and V

I

SATTBLANK MINtrr

C

-------------------------------------------------------- -

P

V

IN MAX

is the minimum blanking time of

is the maximum instantaneous

IN(MAX)

–

input voltage.

V

is the input AC line voltage.

AC

The switching power loss associated with turn-off tran­sitions of the DRAIN pin can be disregarded. Due to the
large amount of parasitic capacitance connected to this
switching node, the turn-off transition occurs essen­tially at zero-voltage.

Conduction power loss in the HV9921/22/23 can be
calculated as:

P

COND

where D = V
tance, I

is the internal linear regulator current.

DD

O/VIN

2

DI

RONIDDVIN1D–+=

O

is the duty ratio, RON is the on-resis-

When the LED driver is powered from the full-wave rec­tified AC line input, the exact equation for calculating
the conduction loss is more cumbersome. However, it
can be estimated using the following equation:

P

CONDKCIO

where V
K

and Kd can be determined from the minimum duty

C

is the input AC line voltage. The coefficients

AC

2

RONKdIDDVAC+=

ratio of the HV9921/22/23.

 2014 Microchip Technology Inc. DS20005311A-page 7

HV9921/HV9922/HV9923

F



FIGURE 4-1: CONDUCTION LOSS

COEFFICIENTS KC AND K

0.7

0.6

0.5

Kd(Dm)

0.4

Kc(Dm)

0.3

0.2

0.1
0 0.1 0.2 0.3 0.4 0.5 0.6 0.7

Dm

4.3 EMI Filter

As with all off-line converters, selecting an input filter is
critical to obtaining good EMI. A switching side capaci­tor, albeit of small value, is necessary in order to ensure
low impedance to the high frequency switching cur­rents of the converter. As a rule of thumb, this capacitor
should be approximately 0.1-0.2 F/W of LED output
power. A recommended input filter is shown in

Figure 4-2 for the following design example.

Select L1 68mH, I = 30mA. Typical SRF = 170KHz.

d

Calculate the coil capacitance.

C

L

1

----------------------------------------- -

L1 2 SRF



------------------------------------------------------------ - 13p

2

68mH 2 170KHz

1



===

2

4.3.1.2 Step 2. Selecting D1

Usually, the reverse recovery characteristics of ultra­fast rectifiers at I

= 20 ~ 50mA are not provided in the

F

manufacturer’s data books. The designer may want to
experiment with different diodes to achieve the best
result.

Select D1 MUR160 with V
20mA, I

= 100mA) and CJ  8pF (VF > 50V).

RR

= 600V, trr  20ns (IF =

R

4.3.1.3 Step 3. Calculating total parasitic
capacitance

5pF 5pF 13pF 8pF 13pF=++ +=

C

p

4.3.1.4 Step 4. Calculating the leading edge
spike duration

T

264V 2 31pF

-------------------------------------------- 20ns 136ns T

SPIKE

100mA

+=

BLANK MIN

4.3.1.5 Step 5. Estimating power dissipation
in HV9921 at 265VAC

4.3.1 DESIGN EXAMPLE

The following example designs a HV9921 LED lamp
driver meeting the following specifications:

• Input: Universal AC, 85-265VAC

• Output Current: 20mA

• Load: String of 10 LED (LW541C by OSRAM VF
= 4.1V max. each)

4.3.1.1 Step 1. Calculating L1.

The output voltage VO = 10 x VF  41V (max.). Use this
equation assuming a 30% peak-to-peak ripple.

41V 10.5s

L1

--------------------------------- - 72mH==

0.3 20mA

Switching power loss:

SWITCH

264V 41V–



-------------------------- 264V 31pF 2 100mA 20ns+
2 10.5s

131mW

P

1

Minimum duty ratio:

M

41V

------------------------- - 0.11=
265V 2

D

Conduction power loss:

P

0.25 20mA

COND

 210 0.63 200A 264V

2

55mW

Total power dissipation in HV9921:

P

TOTAL

131mW 55mW 186mW=+=

+=

DS20005311A-page 8  2014 Microchip Technology Inc.

HV9921/HV9922/HV9923

4.3.1.6 Step 6. Selecting input capacitor C

IN

OutputPower 41V 20mA 820mW==

Select CIN ECQ-E4104KF by Panasonic® (0.1F,
400V, Metalized Polyester Film).

FIGURE 4-2: UNIVERSAL 85-264VAC LED LAMP DRIVER

L

D2 D3

C

IN2

IN

C

IN

C

O

LED

- LED

1

12

D4 D5

D1

HV9921/22/23

VDD

3

DRAIN

GND

2

L1

1

AC Line

85-265V

VRD1

C

DD

F1

FIGURE 4-3: TYPICAL EFFICIENCY FIGURE 4-4: SWITCH-OFF TRANSITION

82

80

78

76

74

72

70

Efficiency (%)

68

66

64

62

75 100 125 150 175 200 225 250 275

Input AC Line Voltage (VAC)

Ch1:V

ZERO VOLTAGE
TRANSITION

DRAIN

, Ch3: I

DRAIN

 2014 Microchip Technology Inc. DS20005311A-page 9

HV9921/HV9922/HV9923

FIGURE 4-5: TYPICAL EFFICIENCY FIGURE 4-6: SWITCH-OFF TRANSITION

Ch1:V

LEADING EDGE SPIKE

SWITCH OFF

25mA

FIGURE 4-7: FUNCTIONAL BLOCK DIAGRAM

DRAIN

, Ch3: I

DRAIN

T

= 10.5μs

OFF

S

REF

-

+

T

BLANK

Q

R

Q

= 300ns

HV9921/HV9922/HV9923

VDD

DRAINGND

Regulator

7.5V

R

DS20005311A-page 10  2014 Microchip Technology Inc.

5.0 LAYOUT CONSIDERATIONS

HV9921/HV9922/HV9923

For a recommended circuit board layout for the
HV9921/22/23, see Figure 5-1.

5.1 Single Point Grounding

Use a single point ground connection from the input fil­ter capacitor to the area of copper connected to the
GND pin.

5.2 Bypass Capacitor (CDD)

The VDD pin bypass capacitor CDD should be located

as near as possible to the V

and GND pins.

DD

5.3 Switching Loop Areas

The area of the switching loop connecting the input fil-

ter capacitor C
together should be kept as small as possible.

The switching loop area connecting the output filter

capacitor C
together should be kept as small as possible.

, the diode D1 and the HV9921/22/23

IN

, the inductor L1 and the diode D1

O

5.4 Thermal Considerations vs. Radiated EMI

The copper area where GND pin is connected acts not
only as a single point ground, but also as a heat sink.
This area should be maximized for good heat sinking,
especially when the SOT-89 package is used. The
same applies to the cathode of the free-wheeling diode
D1. Both nodes are quiet; therefore, they will not cause
radiated RF emission. The switching node copper area
connected to the DRAIN pin of the HV9921/22/23, the
anode of D1 and the inductor L1 needs to be mini­mized. A large switching node area can increase high
frequency radiated EMI.

5.5 Input Filter Layout Considerations

The input circuits of the EMI filter must not be placed in
the direct proximity to the inductor L1 in order to avoid
magnetic coupling of its leakage fields. This consider­ation is especially important when unshielded con­struction of L1 is used. When an axial input EMI filter
inductor L
nal with respect to L1. The loop area formed by C
L

and CIN should be minimized. The input lead wires

IN

must be twisted together.

is selected, it must be positioned orthogo-

IN

IN2

,

FIGURE 5-1: RECOMMENDED CIRCUIT BOARD LAYOUT WITH HV9921/22/23

COMPONENT SIDE VIEW

C

O

LED +

LED -

AC Line

85-264VAC

F1

VRD1

D2-5

L

IN

D1

IN2

C

IN

C

DD

C

L1

U1

 2014 Microchip Technology Inc. DS20005311A-page 11

HV9921/HV9922/HV9923

6.0 PACKAGING INFORMATION

6.1 Package Marking Information

3-lead TO-243AA*

(SOT-89)

XXXYYWW

NNN

3-lead TO-92

XXXXXX
XXXX
YWWNNN

e3

Example

H21YYWW

NNN

Example

HV9921

e3

N3
YWWNNN

Legend: XX...X Product Code or Customer-specific information

Y Year code (last digit of calendar year)
YY Year code (last 2 digits of calendar year)

WW Week code (week of January 1 is week ‘01’)
NNN Alphanumeric traceability code

3

e

Pb-free JEDEC
* This package is Pb-free. The Pb-free JEDEC designator ( )

can be found on the outer packaging for this package.

Note: In the event the full Microchip part number cannot be marked on one line, it will

be carried over to the next line, thus limiting the number of available
characters for product code or customer-specific information. Package may or
may not include the corporate logo.

DS20005311A-page 12  2014 Microchip Technology Inc.

®

designator for Matte Tin (Sn)

3

e

HV9921/HV9922/HV9923

3-Lead TO-243AA (SOT-89) Package Outline (N8)

D

12 3

L

D1

H

E

E1

C

b

e

e1

Top View

Note: For the most current package drawings, see the Microchip Packaging Specification at www.microchip.com/packaging.Note: For the most current package drawings, see the Microchip Packaging Specification at www.microchip.com/packaging.

Symbol A b b1 C D D1 E E1 e e1 H L

Dimensions

(mm)

JEDEC Registration TO-243, Variation AA, Issue C, July 1986.

† This dimension differs from the JEDEC drawing
Drawings not to scale.

MIN 1.40 0.44 0.36 0.35 4.40 1.62 2.29 2.00

NOM-------- --

MAX 1.60 0.56 0.48 0.44 4.60 1.83 2.60 2.29 4.25 1.20

b1

A

Side View

†

1.50
BSC

3.00

BSC

3.94 0.73

†

 2014 Microchip Technology Inc. DS20005311A-page 13

HV9921/HV9922/HV9923

Note: For the most current package drawings, see the Microchip Packaging Specification at www.microchip.com/packaging.

DS20005311A-page 14  2014 Microchip Technology Inc.

APPENDIX A: REVISION HISTORY

Revision A (October 2014)

• Original Release of this Document.

HV9921/HV9922/HV9923

 2014 Microchip Technology Inc. DS20005311A-page 15

HV9921/HV9922/HV9923

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Technical support is available through the web site
at: http://microchip.com/support

Microchip’s customer notification service helps keep
customers current on Microchip products. Subscribers
will receive e-mail notification whenever there are
changes, updates, revisions or errata related to a
specified product family or development tool of interest.

To register, access the Microchip web site at

www.microchip.com. Under “Support”, click on

“Customer Change Notification” and follow the
registration instructions.

DS20005311A-page 16  2014 Microchip Technology Inc.

HV9921/HV9922/HV9923

PRODUCT IDENTIFICATION SYSTEM

To order or obtain information, e.g., on pricing or delivery, refer to the factory or the listed sales office.

PART NO.

Device

Device: HV9921 = 3-Pin Switch-Mode LED Lamp Driver IC,

Package

Options

-

XX

Environmental

HV9922 = 3-Pin Switch-Mode LED Lamp Driver IC,

HV9923 = 3-Pin Switch-Mode LED Lamp Driver IC,

-

X

20 mA output current

50 mA output current

30 mA output current

X

Reel

Examples:

a) HV9921N3-G: 20 mA output current,

b) HV9923N8-G: 30 mA output current,

TO-92 package, 1000/
bag

TO-243AA(SOT-89)
package, 2000/reel

Package: N3 = TO-92

Environmental G = Lead (Pb)-free/ROHS-compliant package

Reel: (nothing) = 1000/bag for N3 package, 2000/reel for N8

N8 = TO-243AA (SOT-89)

package

 2014 Microchip Technology Inc. DS20005311A-page 17

Note the following details of the code protection feature on Microchip devices:

• Microchip products meet the specification contained in their particular Microchip Data Sheet.

• Microchip believes that its family of products is one of the most secure families of its kind on the market today, when used in the
intended manner and under normal conditions.

• There are dishonest and possibly illegal methods used to breach the code protection feature. All of these methods, to our
knowledge, require using the Microchip products in a manner outside the operating specifications contained in Microchip’s Data
Sheets. Most likely, the person doing so is engaged in theft of intellectual property.

• Microchip is willing to work with the customer who is concerned about the integrity of their code.

• Neither Microchip nor any other semiconductor manufacturer can guarantee the security of their code. Code protection does not
mean that we are guaranteeing the product as “unbreakable.”

Code protection is constantly evolving. We at Microchip are committed to continuously improving the code protection features of our
products. Attempts to break Microchip’s code protection feature may be a violation of the Digital Millennium Copyright Act. If such acts
allow unauthorized access to your software or other copyrighted work, you may have a right to sue for relief under that Act.

Information contained in this publication regarding device
applications and the like is provided only for your convenience
and may be superseded by updates. It is your responsibility to
ensure that your application meets with your specifications.
MICROCHIP MAKES NO REPRESENTATIONS OR
WARRANTIES OF ANY KIND WHETHER EXPRESS OR
IMPLIED, WRITTEN OR ORAL, STATUTORY OR
OTHERWISE, RELATED TO THE INFORMATION,
INCLUDING BUT NOT LIMITED TO ITS CONDITION,
QUALITY, PERFORMANCE, MERCHANTABILITY OR
FITNESS FOR PURPOSE. Microchip disclaims all liability
arising from this information and its use. Use of Microchip
devices in life support and/or safety applications is entirely at
the buyer’s risk, and the buyer agrees to defend, indemnify and
hold harmless Microchip from any and all damages, claims,
suits, or expenses resulting from such use. No licenses are
conveyed, implicitly or otherwise, under any Microchip
intellectual property rights.

Trademarks

The Microchip name and logo, the Microchip logo, dsPIC,
FlashFlex, KEELOQ, KEELOQ logo, MPLAB, PIC, PICmicro,
PICSTART, PIC32 logo, rfPIC, SST, SST Logo, SuperFlash
and UNI/O are registered trademarks of Microchip
Technology Incorporated in the U.S.A. and other countries.

FilterLab, Hampshire, HI-TECH C, Linear Active Thermistor,
MTP, SEEVAL and The Embedded Control Solutions
Company are registered trademarks of Microchip Technology
Incorporated in the U.S.A.

Silicon Storage Technology is a registered trademark of
Microchip Technology Inc. in other countries.

Analog-for-the-Digital Age, Application Maestro, BodyCom,
chipKIT, chipKIT logo, CodeGuard, dsPICDEM,
dsPICDEM.net, dsPICworks, dsSPEAK, ECAN,
ECONOMONITOR, FanSense, HI-TIDE, In-Circuit Serial
Programming, ICSP, Mindi, MiWi, MPASM, MPF, MPLAB
Certified logo, MPLIB, MPLINK, mTouch, Omniscient Code
Generation, PICC, PICC-18, PICDEM, PICDEM.net, PICkit,
PICtail, REAL ICE, rfLAB, Select Mode, SQI, Serial Quad I/O,
Total Endurance, TSHARC, UniWinDriver, WiperLock, ZENA
and Z-Scale are trademarks of Microchip Technology
Incorporated in the U.S.A. and other countries.

SQTP is a service mark of Microchip Technology Incorporated
in the U.S.A.

GestIC and ULPP are registered trademarks of Microchip
Technology Germany II GmbH & Co. KG, a subsidiary of
Microchip Technology Inc., in other countries.

All other trademarks mentioned herein are property of their
respective companies.

© 2014, Microchip Technology Incorporated, Printed in the
U.S.A., All Rights Reserved.

Printed on recycled paper.

ISBN: 978-1-63276-708-0

Microchip received ISO/TS-16949:2009 certification for its worldwide
headquarters, design and wafer fabrication facilities in Chandler and
Tempe, Arizona; Gresham, Oregon and design centers in California
and India. The Company’s quality system processes and procedures
are for its PIC
devices, Serial EEPROMs, microperipherals, nonvolatile memory and
analog products. In addition, Microchip’s quality system for the design
and manufacture of development systems is ISO 9001:2000 certified.

®

MCUs and dsPIC® DSCs, KEELOQ

®

code hopping

DS20005311A-page 18  2014 Microchip Technology Inc.

Worldwide Sales and Service

AMERICAS

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03/25/14

DS20005311A-page 19  2014 Microchip Technology Inc.