Cirrus Logic CS1616 User Manual

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CS1615

Mains

BR1

CS1615/16

FBAUX

GND

IAC

LED+

VDD

SOURCE

eOTP

NTC

LED-

FBSENSE

Sense

SGN D4CTRL1 CTRL2

CTRL1

CTRL2

C1 C2

rect

AUX

R4 R5

CS1616

Single Stage Dimmable Offline AC/DC

Controller for LED Lamps

Features

• Best-in-class Dimmer Compatibility

- Leading-edge (TRIAC) Dimmers

- Trailing-edge Dimmers

- Digital Dimmers (Dimmers with an Integrated Power Supply)

• Flicker-free Dimming

• 0% to 100% Smooth Dimming

• Primary-side Regulation (PSR)

• Active Power Factor Correction (PFC)

- >0.9 Power Factor

• Constant-current Output

- Flyback

- Buck-boost

• Tight LED Current Regulation: Better than ±5%

• Low THD: Less Than 20%

• Up to 90% Efficiency

• Fast Startup

• IEC61000-3-2 Compliant

• Meets NEMA SSL 6 Dimming Standard

- Closely Matches Incandescent S-curve

• Protection Features

- Output Open Circuit

- Output Short Circuit

- External Overtemperature Using NTC

Overview

The CS1615 and CS1616 are high-performance single stage dimmable offline AC/DC controllers. The CS1615/ 16 is a cost-effective solution that provides unmatched singleand multi-lamp dimmer-compatibility performance for dimmable LED applications. The CS1615 is designed for 120VAC line voltage applications, and the CS1616 is designed for 230VAC line voltage applications.

Across a broad range of dimmers, the CS1615/16 provides smooth flicker free dimming, and consistently dims to nearly zero light output, which closely matches the dimming performance of incandescent light bulbs. Cirrus Logic’s patent pending approach to dimmer compatibility provides full functionality on a wide range of dimmers, including leading-edge, trailing-edge, and digital dimmers.

Applications

• Retro-fit LED Lamps

• External LED Drivers

• LED Luminaries

• Commercial Lighting

Ordering Information

See page 14.

Cirrus Logic, Inc.

http://www.cirrus.com

JUN’13

DS961F1

1. INTRODUCTION

IAC

SOURCE

SGND

15k

ADC

ref

FBSENSE

DAC

Peak

Contr ol

GND

OLP

OCP

Blank

CLAMP

OCP( th)

OLP(th)

Pk_Max(th)

CLAMP

-V

SOURCE(th)

MUX

CONNECT

CONNECT(th)

CTRL2

CTRL1

eOTP

FBAUX

Zer o-cur rent

Detect

Output

Over voltag e

ZCD(th)

OVP(th)

VAUX

VDD

DD(on)

DD(off)

Volt age

Regul ator

POR

VDD

FSTA RT(th )

CS1615/16

Figure 1. CS1615/16 Block Diagram

A typical schematic using the CS1615/16 IC is shown on the previous page.

Startup current is provided from a patent-pending, external, highvoltage source-follower network. In addition to providing startup current, this unique topology is integral in providing compatibility with digital dimmers by ensuring V

power is always available

to the IC. During normal operation, an auxiliary winding on the flyback transformer or buck-boost inductor back-biases the source-follower circuit and provides steady-state operating current to the IC to improve system efficiency.

Rectified input voltage V and is used to control the adaptive dimmer-compatibility

is sensed as a current into pin IAC

rect

algorithm and to extract the phase of the input voltage for output dimming control. The SOURCE pin is used to provide a control signal for the high-voltage source-follower circuit during Leadingedge Mode and Trailing-edge Mode; it also provides the current during startup.

2 DS961F1

The digital dual-mode controller is implemented with peakcurrent mode primary-side regulation, which eliminates the need for additional components to provide feedback from the secondary and reduces system cost and complexity. Voltage across a user-selected resistor is sensed through pin FBSENSE to control the peak current of the primary-side inductor. Leadingedge and trailing-edge blanking on pin FBSENSE prevents false triggering. The required target LED current and average flyback transformer and buck-boost inductor input current are set by attaching resistors R CTRL2, respectively. The controller ensures half line-cycle averaged constant output current.

Pin FBAUX is used for zero-current detection to ensure quasi-resonant switching of the single stage output. When an external negative temperature coefficient (NTC) thermistor is connected to pin eOTP, the CS1615/16 monitors the system temperature, allowing the controller to reduce the output current of the system. If the temperature reaches a designated high set point, the IC is shut down and stops switching.

CTRL1

and R

on pins CTRL1 and

CTRL2

2. PIN DESCRIPTION

16 -lead SOIC and TSSOP

Zero-current DetectFBAUX

No ConnectNC

IC Supply Vol tageVDD

GD Gate Drive

eOTP External Over tem per atur e Pr otec ti on

FBSENSE Fl yback Curr ent Sense

GND Gr ound

LED Load Cur r entCTRL2

No Connect NC

IACRectifier Voltage Sense

Voltage Clam p C ur r ent Sour ce CLAMP

SGNDSource Gr ound

Source Switch SOURCE

NCNo Connect

No Connect NC

CTRL1Dimmer Hold Current

CS1615/16

Figure 2. CS1615/16 Pin Assignments

Pin Name Pin # I/O

Description

NC 1INNo Connect — Leave pin unconnected.

IAC 2IN

CLAMP 3OUT

Rectifier Voltage Sense — A current proportional to the rectified line voltage is fed

into this pin. The current is measured with an A/D converter.

Voltage Clamp Current Source — Connect to a voltage clamp circuit on the source-switched dimmer-compatibility circuit.

SGND 4PWRSource Ground — Common reference current return for the SOURCE pin.

SOURCE 5IN

Source Switch — Connected to the source of the source-switched external high-volt-

age FET.

NC 6INNo Connect — Connect this pin to VDD using a 47k pull-up resistor.

NC 7INNo Connect — Connect this pin to VDD using a 47kpull-up resistor.

CTRL1 8IN

Dimmer Hold Current — Connect a resistor to this pin to set the minimum input cur-

rent being pulled by the flyback / buck-boost stage.

CTRL2 9INLED Load Current — Connect a resistor to this pin to set the LED current.

eOTP 10 IN

External Overtemperature Protection — Connect an external NTC thermistor to this

pin, allowing the internal A/D converter to sample the change to NTC resistance.

Feedback Current Sense — The current flowing in the power FET is sensed across a

FBSENSE 11 IN

resistor. The resulting voltage is applied to this pin and digitized for use by the computational logic to determine the FET's duty cycle.

GND 12 PWR

Ground — Common reference. Current return for both the input signal portion of the

IC and the gate driver.

GD 13 OUT Gate Drive — Gate drive for the power FET.

IC Supply Voltage — Connect a storage capacitor to this pin to serve as a reservoir

VDD 14 PWR

for operating current for the device, including the gate drive current to the power transistor.

NC 15 - No Connect — Leave pin unconnected.

FBAUX 16 IN

Zero-current Detect — Connect to the flyback/buck-boost inductor auxiliary winding

for demagnetization current zero-crossing detection.

DS961F1 3

3. CHARACTERISTICS AND SPECIFICATIONS

3.1 Electrical Characteristics

CS1615/16

Typical characteristics conditions:

=25°C, VDD=12V, GND=0V

•T

• All voltages are measured with respect to GND.

Minimum/Maximum characteristics conditions:

•TJ= -40°C to +125 °C, VDD= 11V to 17V, GND = 0 V

• Unless otherwise specified, all currents are positive when flowing into the IC.

Parameter Condition Symbol Min Typ Max Unit

VDD Supply Voltage

Operating Range

Turn-on Threshold Voltage

Turn-off Threshold Voltage (UVLO)

Zener Voltage

(Note 1)

After Turn-on

VDD Increasing

VDD Decreasing

=20mA

ST(th)

STP(th)

11 - 17 V

-8.5-V

-7.5-V

18.5 - 19.8 V

VDD Supply Current

Startup Supply Current

Operating Supply Current

(Note 2)

VDD<V

ST(th)

= 0.25nF, fsw70 kHz

--200A

-4.5-mA

Reference

Reference Current

CS1615 CS1616

rect

=200V =400V

ref

133 133

A A

Zero-current Detect

FBZCD Threshold V

FBZCD Blanking t

ZCD Sink Current

FBAUX Upper Voltage

(Note 3) I

=1mA

ZCD

FBZCD(th)

FBZCB

ZCD

-200-mV

-2-s

-2 - - mA

-VDD+0.6 - V

Current Sense

Max Peak Control Threshold V

Pk_Max(th)

Leading-edge Blanking t

LEB

-1.4-V

-550-ns

Delay to Output --100ns

Pulse Width Modulator

Minimum On Time - 0.55 - s

Maximum On Time - 12.8 - s

Minimum Switching Frequency t

Maximum Switching Frequency t

FB(Min)

FB(Max)

-6-kHz

-200-kHz

Gate Driver

Output Source Resistance Z

Output Sink Resistance Z

Rise Time

Fall Time

CL=0.25nF

OUT

-24-

-11-

--30ns

--20ns

4 DS961F1

CS1615/16

Parameter Condition Symbol Min Typ Max Unit

Flyback/Buck-boost Protections

Overcurrent Protection (OCP)

Overvoltage Protection (OVP)

Open Loop Protection (OLP)

(Note 4) V

(Note 5) V

(Note 4) V

OCP(th)

OVP(th)

OLP(th)

External Overtemperature Protection (eOTP)

Pull-up Current Source – Maximum I

Conductance Accuracy

Conductance Offset

(Note 6) --±5

(Note 6) -±250-nS

Current Source Voltage Threshold V

CONNECT

CONNECT(th)

Internal Overtemperature Protection (iOTP)

Thermal Shutdown Threshold

Thermal Shutdown Hysteresis

Notes: 1. The CS1615/ 16 has an internal shunt regulator that limits the voltage on the VDD pin. Shunt regulation voltage VZ is defined in

the VDD Supply Voltage section on page 4.

2. For test purposes, load capacitance C

3. External circuitry should be designed to ensure that the ZCD current drawn from the internal clamp diode when it is forward biased does not exceed specification.

4. Protection is implemented using pin FBSENSE. See the CS1615/ 16 Block Diagram on page 2.

5. Protection is implemented using pin FBAUX. See the CS1615/ 16 Block Diagram on page 2

6. The conductance is specified in Siemens (S or 1/ ). Each LSB of the internal ADC corresponds to 250 nS or one parallel 4 M resistor. Full scale corresponds to 256 parallel 4M resistors or 15.625 k.

7. Specifications are guaranteed by design and are characterized and correlated using statistical process methods.

(Note 7) T

is connected to pin GD and is equal to 0.25nF.

SD(Hy)

-1.69-V

-1.25-V

-200-mV

-80-A

-1.25-V

-135-ºC

-14-ºC

DS961F1 5

CS1615/16

3.2 Thermal Resistance

Symbol Parameter SOIC TSSOP Unit



Junction-to-Ambient Thermal Impedance 2 Layer PCB

Junction-to-Case Thermal Impedance 2 Layer PCB

4 Layer PCB

3.3 Absolute Maximum Ratings

Characteristics conditions:

All voltages are measured with respect to GND.

Pin Symbol Parameter Value Unit

14 V

2,8,9,

10,11,16

2,8,9,

10,11,16

13 V

13 I

SOURCE

CLAMP

-P

-T

All Pins ESD

IC Supply Voltage 18.5 V

Analog Input Maximum Voltage -0.5 to (V

Analog Input Maximum Current 5 mA

Gate Drive Output Voltage -0.3 to (VDD+0.3) V

Gate Drive Output Current -1.0 / +0.5 A

Current into Pin 1.1 A

Clamp Output Current 15 mA

Total Power Dissipation 400 mW

Junction Temperature Operating Range (Note 8) -40 to +125 °C

Storage Temperature Range -65 to +150 °C

Stg

Electrostatic Discharge Capability Human Body Model

Charged Device Model

119 105

50 44

138 103

44 28

2000

500

+0.5) V

°C/W °C/W

V V

Note: 8. Long-term operation at the maximum junction temperature will result in reduced product life. Derate internal power dissipation at

the rate of 50 mW /°C for variation over temperature.

WARNING:

Operation at or beyond these limits may result in permanent damage to the device.

Normal operation is not guaranteed at these extremes.

6 DS961F1

4. TYPICAL PERFORMANCE PLOTS

-50 0 50 100 150

UVLO Hysteresis

Temperature (ºC)

-2

02468101214161820

(mA)

VDD(V)

Falling Edge

Rising Edge

-50 0 50 100 150

VDD (V)

Temperature (ºC)

Turn Off

Turn On

18.5

19.5

1251058555255-20-45

(V)

Temperature (ºC)

Resistance ()

Temperature (ºC)

Sink

Source

-43 25 125

-2.25

-1.75

-1.25

-0.75

-0.25

0.25

1251058555255-20-45

Drift (%)

CS1615/16

Figure 3. UVLO Characteristics

Figure 5. Turn On/Off Threshold Voltage vs. Temperature

Figure 4. Supply Current vs. Voltage

Figure 6. Zener Voltage vs. Temperature

Figure 7. Gate Drive Resistance vs. Temperature

DS961F1 7

Temperature (°C)

Figure 8. Reference Current (I

) Drift vs. Temperature

ref

CS1615/16

Figure 9. No-dimmer Mode Waveform

Figure 10. Leading-edge Mode Phase-cut Waveform

5. GENERAL DESCRIPTION

5.1 Overview

The CS1615 and CS1616 are high-performance single stage dimmable offline AC/DC controllers. The CS1615 /16 is a costeffective solution that provides unmatched single- and multi-lamp dimmer-compatibility performance for dimmable LED applications. The CS1615 is designed for 120VAC line voltage applications, and the CS1616 is designed for 230VAC line voltage applications.

5.2 IC Startup

A high-voltage source-follower circuit is used to deliver startup current to the IC. During steady-state operation, an auxiliary winding on the transformer/inductor biases this circuit to an off state to improve system efficiency, and all IC supply current is provided from the auxiliary winding. The patent-pending technology of the high-voltage source-follower circuit enables system compatibility with digital dimmers (dimmers containing an internal power supply) by providing a continuous path for the dimmer’s power supply to recharge during its off state. During steady-state operation, high-voltage FET Q1 in this circuit is source-controlled by a variable internal current source on the SOURCE pin to create the dimmer-compatibility circuit. A Schottky diode with a forward voltage of less than 0.6V is recommended for diode D1. Schottky diode D1 will limit inrush current through the internal diode, preventing damage to the IC.

During initial power-up, the IC executes a fast startup algorithm, which drives the converter with peak currents that are above normal to charge the output capacitor. Once the output capacitor reaches a defined voltage, the IC drives the converter with nominal peak currents until normal operation is achieved.

appropriate operating mode for the IC. The dimmer switch detection algorithm uses the input line voltage slope and dimmer phase angle to determine the operating mode that matches the type of dimmer switch in the system. From there on, it periodically learns the dimmer type and can change the operating mode if the type of dimmer switch changes.

5.3.1.1 No-dimmer Mode

If the CS1615/ 16 determines that the line is not phase cut by a dimmer switch, the IC operates the flyback/ buck-boost in PFC mode to achieve a power factor greater than 0.9 while regulating the load current to a level set by resistor R No-dimmer Mode algorithm is applied to the source-controlled dimmer-compatibility circuit for optimal performance, including less than 20% of THD and highest possible overall efficiency.

. In addition, a

CTRL2

5.3.1.2 Leading-edge Mode

If the CS1615/16 determines that the line is phase cut by a leading-edge dimmer switch, the IC operates the flyback/buckboost in Dimmer Mode and the IC sets the dimmer firing current as well as the attach current using a source-controlled dimmercompatibility circuit for stable TRIAC dimmer operation.

5.3 IC Operation

5.3.1 Dimmer Detection

The CS1615/16 dimmer switch detection algorithm determines if a non-dimming switch, a leading-edge dimmer switch, or a trailing-edge dimmer switch controls the solid-state lighting (SSL) system. For each type of switch, the IC uses a different operating mode: for a non-dimming switch, No-dimmer Mode is used; for a leading-edge dimmer switch, Leading-edge Mode is used; for a trailing-edge dimmer switch, Trailing-edge Mode is used. As a result, the overall performance is optimized in terms of power losses, efficiency, power factor, THD, and dimmer compatibility.

When the IC completes UVLO, it executes in Leading-edge Mode until the dimmer switch detection algorithm determines the

8 DS961F1

5.3.1.3 Trailing-edge Mode

If the CS1615/16 determines that the line is phase cut by a trailing-edge dimmer switch, the IC operates the flyback/buckboost in Dimmer Mode. The IC charges the capacitor in the

CS1615/16

Figure 11. Trailing-edge Mode Phase-cut Waveform

CLAMP

Clamp

CLAMP

rect

CS1615 /16

VDD

R6C6

Sense

IAC

Figure 12. CLAMP Pin Model

CTRL2

FBAU X

GND

912

CS1615/16

R6C6

Sense

rect

FBSEN SE

LED+

LED-

AUX

Figure 13. Flyback Model

dimmer switch on the falling edge of the input voltage using a source-controlled dimmer-compatibility circuit.

5.3.2 Switch Overpower Protection

To prevent excessive power dissipation on the source-switched FET Q1, the CS1615/16 monitors voltage across FET Q1 and current flow through FET Q1 to calculate average power dissipation. If the calculated power exceeds the overpower protection threshold a fault condition occurs. The IC output is disabled and the controller attempts to restart after approximately thirty seconds.

5.4 Voltage Clamp Circuit

To keep trailing-edge dimmer switches conducting and from misfiring, the dimmer switch internal capacitor has to be charged quickly around the trailing edge of the phase-cut waveform. In addition to the dimmer compatible circuit, an optional clamp circuit provides a high-current sinking path for delivering the required amount of charge onto the dimmer switch capacitor in a short amount of time.

The CS1615 / 16 provides active clamp circuitry on the CLAMP pin, as shown in Figure 12.

5.4.1 Clamp Overpower Protection

The CS1615 /16 clamp overpower protection (COP) control logic averages the turn-on time of the clamp circuit. If the output of the averaging logic exceeds 10%, a COP event is actuated. The clamp circuit is disabled as well as the flyback/buck-boost controller and the dimmer-compatibility circuit. The COP fault state is not cleared until the power to the IC is recycled.

5.5 Dimmer Angle Extraction and the Dim Mapping Algorithm

When operating with a dimmer, the dimming signal is extracted in the time domain and is proportional to the conduction angle of the dimmer. A control variable is passed to the quasi-resonant flyback/ buck-boost controller to achieve a wide range of output currents.

5.6 Dual-mode Flyback/Buck-boost

The CS1615/16 is configurable for isolated or non-isolated topologies using a flyback transformer or buck-boost inductor, respectively. The CS1615/16 controls the dual-mode flyback/ buck-boost to satisfy the dimmer hold current requirement in Dimmer Mode and provide power factor correction in No-dimmer Mode. The dual-mode ensures a minimum average input current greater than the required dimmer hold current when behind a dimmer and shapes the line current when not behind a dimmer to provide power factor correction. It also ensures half line-cycle averaged constant output current.

Figure 13 illustrates the dual-mode flyback topology. The CS1615/16 regulates output current using primary-side control, which eliminates the need for opto-coupler feedback. The control loop operates in peak current control mode. Demagnetization time of the transformer is sensed by the FBAUX pin using an auxiliary winding and is used as an input to the control loop.

DS961F1 9

CS1615/16

CTRL2

FBAUX

GND

912

CS1615/16

Sense

rect

FBSENSE

LED+

LED-

AUX

Figure 14. Buck-boost Model

CTRL2

1.4V N 4 M

1.25 511 R

SenseIOUT



----------------------------------------------------------------------- -

[Eq.1]

CTRL1

1.4V 4M

511 I

IN CCRSense



----------------------------------------------------------- -

[Eq.2]

PK max

1.4

Sense

------------------ -

[Eq.3]

Figure 14 illustrates the dual-mode buck-boost topology. The CS1615/16 regulates the output current by controlling the peak current to ensure that the target output charge is achieved every half line-cycle. Demagnetization time of the inductor is sensed by the FBAUX pin using an auxiliary winding and is used as an input to the control loop.

5.6.1 Primary-Side Current Control

All input current shaping and output power transfer is attained using a peak current control algorithm. Demagnetization time of the primary inductor is sensed by the FBAUX pin using an auxiliary winding and is used as an input to the control algorithm. The values obtained from resistors R

CTRL1

and R

CTRL2

are the other inputs to the control algorithm that help shape the input current and control the LED current, respectively.

5.6.2 Output Current Regulation

The CS1615/16 regulates output current by controlling the charge transferred over a half line-cycle. The full-scale output current target is set using resistor R pin CTRL2. This pin is sampled periodically by an ADC. The value of this resistor can be determined using Equation 1.

, which is connected on

CTRL2

the target output charge is achieved every half line-cycle, thus regulating the output current.

5.6.3 Input Current Shaping

The CS1615/16 shapes the input current by controlling the peak primary current and the flyback/buck-boost switching frequency. It shapes the currents differently when behind a dimmer compared to when not behind a dimmer.

5.6.3.1 Operation Behind a Dimmer

Operating behind a dimmer, the CS1615/16 controls the switching frequency to ensure that the average input current is greater than the dimmer hold current requirement. The dimmer hold current level is sensed using resistor R

on pin CTRL1,

CTRL1

which is sampled periodically by an ADC. The value of this resistor can be determined using the formula shown in Equation 2.

where,

= constant input current used when designing circuit

IN(CC)

= resistor attached to pin FBSENSE

Sense

5.6.3.2 Operation in No-dimmer Mode

Operating in No-dimmer Mode, the CS1615/16 controls the switching frequency to ensure that the average input current follows the line voltage to provide power factor correction. In Nodimmer Mode the controller is designed to operate in quasiresonant mode to improve efficiency.

5.6.4 Max Primary-side Switching Current

Maximum primary-side switching current I resistor R

connected to pin FBSENSE of the CS1615/16.

Sense

The maximum primary-side switching current can be calculated using Equation 3.

PK(max)

is set using

5.6.5 Auxiliary Winding Configuration

The auxiliary winding is used for zero-current detection (ZCD), overvoltage protection (OVP), fast startup, and the steady-state

where,

N = turns ratio

= current through LED at maximum output

OUT

= resistor attached to pin FBSENSE

Sense

When designing a buck-boost topology the turns ratio N is set to one.

The CS1615/16 uses the value obtained from the resistor along with the phase-cut and line-cycle period information to determine the corresponding target full-scale output charge. The IC controls the inductor switching frequency and peak current to ensure that

10 DS961F1

power supply. The voltage on the auxiliary winding is sensed through pin FBAUX of the CS1615/16 for zero-current detection, overvoltage protection, and fast startup. The auxiliary winding is also used to provide the steady-state power supply to the CS1615/16.

5.6.6 Output Open Circuit Protection

Output open circuit protection and output overvoltage protection (OVP) are implemented by monitoring the output voltage through the transformer auxiliary winding. If the voltage on the FBAUX pin exceeds a threshold V The IC output is disabled and the controller attempts to restart after approximately one second.

of 1.25V, a fault condition occurs.

OVP(th)

CS1615/16

CONNECT

(th)

Com p_Out

eOTP

Control

eOTP

NTC

(Optional)

Figure 15. eOTP Functional Diagram

Temperature (°C)

Cu rrent (I

LED

, Nom. )

125

50%

100%

Figure 16. eOTP Temperature vs. Impedance

5.6.7 Overcurrent Protection

Overcurrent protection (OCP) is implemented by monitoring the voltage across the sense resistor. If this voltage exceeds a threshold V

of 1.69V, a fault condition occurs. The IC

OCP(th)

output is disabled and the controller attempts to restart after approximately one second.

5.6.8 Open Loop Protection

Open loop protection (OLP) and sense resistor short protection are implemented by monitoring the voltage across the resistor. If the voltage on pin FBSENSE does not reach the protection threshold V

of 200mV, the IC output is disabled, and the

OLP(th)

controller attempts to restart after approximately one second.

5.7 Overtemperature Protection

The CS1615 / 16 incorporates internal overtemperature protection (iOTP) and the ability to connect an external overtemperature sense circuit for IC protection. Typically, an NTC thermistor is used.

5.7.1 Internal Overtemperature Protection

Internal overtemperature protection (iOTP) is activated, and switching is disabled when the die temperature of the devices exceeds 135°C. There is a hysteresis of about 14°C before resuming normal operation.

5.7.2 External Overtemperature Protection

The external overtemperature protection (eOTP) pin is used to implement overtemperature protection. A negative temperature coefficient (NTC) thermistor resistive network is connected to pin eOTP, usually in the form of a series combination of a resistor R and a thermistor R samples the resistance connected to pin eOTP.

(see Figure 15). The CS1615/16 cyclically

NTC

of the system (and hence LED current I

) if the temperature

LED

exceeds 95 °C. The large time constant for this filter ensures that the dim scaling does not happen spontaneously and is not noticeable (suppress spurious glitches). The eOTP tracking circuit is designed to function accurately with external capacitance up to 470pF.

The tracking range of this resistance ADC is approximately

15.5k to 4M. The series resistor R

is used to adjust the

resistance of the NTC to fall within the ADC tracking range, allowing the entire dynamic range of the ADC to be well used. The CS1615/ 16 recognizes a resistance (R

S+RNTC

20.3k which corresponds to a temperature of 95°C, as the beginning of an overtemperature dimming event and starts reducing the power dissipation. The output current is scaled until the series resistance (R

S+RNTC

) value reaches 16.6k (125°C). Beyond this temperature, the IC shuts down until the resistance (R

S+RNTC

) rises above 19.23k. This is not a latched protection state, and the ADC keeps tracking the temperature in this state in order to clear the fault state once the temperature drops below 110°C.

When exiting reset, the chip enters startup and the ADC quickly (<5ms) tracks the external temperature to check if it is below the 110°C reference code before the controller is powered up. If this check fails, the chip will wait until this condition becomes true before initializing the rest of the system.

For example, a 14k (±1% tolerance) series resistor is required to allow measurements of up to 130°C to be within the eOTP tracking range when a 100k NTC with a Beta of 4275. If the temperature exceeds 95°C, thermistor R

6.3k and series resistor R

resistance of 20.3k. The eOTP pin initiates protective dimming

is 14k, so the eOTP pin has a total

is approximately

NTC

action by reducing the power dissipation. At 125°C the thermistor

has 2.6k plus a series resistor RS equal to 14k present

NTC

a resistance of 16.6k at the eOTP pin reaching the point where a thermal shutdown fault intervenes. The CS1615/16 will continue to monitor pin eOTP and once the series resistor R plus the thermistor R

rises above 19.23k the device will

NTC

resume power conversion (see Figure 16).

) equal to

The total resistance on the eOTP pin gives an indication of the temperature and is used in a digital feedback loop to adjust current I

CONNECT

into the NTC and series resistor RS to maintain a constant reference voltage V I

CONNECT

is generated from a controlled current source with a full-scale current of 80A. When the loop is in equilibrium, the voltage on the eOTP pin fluctuates around reference voltage V current I

CONNECT(th)

CONNECT

. A resistance ADC is used to generate

. The ADC output is filtered to suppress noise and compared against a reference that corresponds to 125°C. A second low-pass filter with a time constant of two seconds filters the ADC output and is used to scale down the internal dim level

DS961F1 11

CONNECT(th)

of 1.25V. Current

If the external overtemperature protection feature is not required, connect the eOTP pin to GND using a 50k-to-500k resistor to disable the eOTP feature.

6. PACKAGE DRAWING

4&"5*/(1-"/&

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16-PIN TSSOP (173 MIL BODY)

CS1615/16

mm inch

Dimension MIN NOM MAX MIN NOM MAX

A - - - - 1.20 - - - - 0.047

A1 0.05 - - 0.15 0.002 - - 0.006

b 0.19 - - 0.30 0.007 - - 0.012

C 0.09 - - 0.20 0.004 - - 0.008

D 4.90 5.00 5.10 0.193 0.197 0.201

E 6.40 BSC 0.252 BSC

E1 4.30 4.40 4.50 0.169 0.173 0.177

e 0.65 BSC 0.026 BSC

L 0.45 0.60 0.75 0.018 0.024 0.030

Θ 0°- -8°0°- -8°

aaa 0.10 0.004

bbb 0.10 0.004

ddd 0.20 0.008

1. Controlling dimensions are in millimeters.

2. Dimensioning and tolerances per ASME Y14.5 M.

3. This drawing conforms to JEDEC outline MO-153, variation AB.

4. Recommended reflow profile is per JEDEC/IPC J-STD-020.

12 DS961F1

CS1615/16

16-PIN SOICN (150 MIL BODY)

Dimension MIN NOM MAX MIN NOM MAX

A - - - - 1.75 - - - - 0.069

A1 0.10 - - 0.25 0.004 - - 0.010

b 0.31 - - 0.51 0.012 - - 0.020

c 0.10 - - 0.25 0.004 - - 0.010

D 9.90 BSC 0.390 BSC

E 6.00 BSC 0.236 BSC

E1 3.90 BSC 0.154 BSC

e 1.27 BSC 0.050 BSC

L 0.40 - - 1.27 0.016 - - 0.050

Θ 0°- -8°0°- -8°

aaa 0.10 0.004

bbb 0.25 0.010

ddd 0.25 0.010

Notes: 1. Controlling dimensions are in millimeters.

2. Dimensions and tolerances per ASME Y14.5 M.

3. This drawing conforms to JEDEC outline MS-012, variation AC for standard 16 SOICN narrow body.

4. Recommended reflow profile is per JEDEC/IPC J-STD-020.

mm inch

DS961F1 13

CS1615/16

7. ORDERING INFORMATION

Ordering Number Container AC Line Voltage Temperature Package

CS1615-FSZ Bulk

CS1615-FSZR Tape & Reel

CS1616-FSZ Bulk

CS1616-FSZR Tape & Reel

CS1615-FZZ Bulk

CS1615-FZZR Tape & Reel

CS1616-FZZ Bulk

CS1616-FZZR Tape & Reel

120VAC -40 °C to +125 °C 16-lead SOICN, Lead (Pb) Free

230VAC -40 °C to +125 °C 16-lead SOICN, Lead (Pb) Free

120VAC -40 °C to +125 °C 16-lead TSSOP, Lead (Pb) Free

230VAC -40 °C to +125 °C 16-lead TSSOP, Lead (Pb) Free

8. ENVIRONMENTAL, MANUFACTURING, & HANDLING INFORMATION

Part Number Peak Reflow Temp MSL Rating

CS1615-FSZ 260 °C 3 7 Days

CS1616-FSZ 260 °C 3 7 Days

CS1615-FZZ 260 °C 3 7 Days

CS1616-FZZ 260 °C 3 7 Days

Max Floor Life

a.MSL (Moisture Sensitivity Level) as specified by IPC/JEDEC J-STD-020.

b.Stored at 30°C, 60% relative humidity.

14 DS961F1

REVISION HISTORY

Revision Date Changes

T1 JUN 2012 Initial release.

PP1 JUL 2012 Corrected typographical errors.

PP2 SEP 2012 Clarified context and corrected typographical errors.

PP3 OCT 2012 Clarified context.

PP4 JAN 2013 Buck-boost content added, and clarified context.

PP5 APR 2013 Context clarification.

F1 JUN 2013 Final release

CS1615/16

DS961F1 15

CS1615/16

Contacting Cirrus Logic Support

For all product questions and inquiries contact a Cirrus Logic Sales Representative. To find the one nearest to you go to www.cirrus.com

IMPORTANT NOTICE

Cirrus Logic, Inc. and its subsidiaries ("Cirrus") believe that the information contained in this document is accurate and reliable. However, the information is subject to change without notice and is provided "AS IS" without warranty of any kind (express or implied). Customers are advised to obtain the latest version of relevant information to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied at the time of order acknowledgment, including those pertaining to warranty, indemnification, and limitation of liability. No responsibility is assumed by Cirrus for the use of this information, including use of this information as the basis for manufacture or sale of any items, or for infringement of patents or other rights of third parties. This document is the property of Cirrus and by furnishing this information, Cirrus grants no license, express or implied under any patents, mask work rights, copyrights, trademarks, trade secrets or other intellectual property rights. Cirrus owns the copyrights associated with the information contained herein and gives consent for copies to be made of the information only for use within your organization with respect to Cirrus integrated circuits or other products of Cirrus. This consent does not extend to other copying such as copying for general distribution, advertising or promotional purposes, or for creating any work for resale.

CERTAIN APPLICATIONS USING SEMICONDUCTOR PRODUCTS MAY INVOLVE POTENTIAL RISKS OF DEATH, PERSONAL INJURY, OR SEVERE PROPERTY OR ENVIRONMENTAL DAMAGE ("CRITICAL APPLICATIONS"). CIRRUS PRODUCTS ARE NOT DESIGNED, AUTHORIZED OR WARRANTED FOR USE IN PRODUCTS SURGICALLY IMPLANTED INTO THE BODY, AUTOMOTIVE SAFETY OR SECURITY DEVICES, LIFE SUPPORT PRODUCTS OR OTHER CRITICAL APPLICATIONS. INCLUSION OF CIRRUS PRODUCTS IN SUCH APPLICATIONS IS UNDERSTOOD TO BE FULLY AT THE CUSTOMER'S RISK AND CIRRUS DISCLAIMS AND MAKES NO WARRANTY, EXPRESS, STATUTORY OR IMPLIED, INCLUDING THE IMPLIED WARRANTIES OF MERCHANTABILITY AND FITNESS FOR PARTICULAR PURPOSE, WITH REGARD TO ANY CIRRUS PRODUCT THAT IS USED IN SUCH A MANNER. IF THE CUSTOMER OR CUSTOMER'S CUSTOMER USES OR PERMITS THE USE OF CIRRUS PRODUCTS IN CRITICAL APPLICATIONS, CUSTOMER AGREES, BY SUCH USE, TO FULLY INDEMNIFY CIRRUS, ITS OFFICERS, DIRECTORS, EMPLOYEES, DISTRIBUTORS AND OTHER AGENTS FROM ANY AND ALL LIABILITY, INCLUDING ATTORNEYS' FEES AND COSTS, THAT MAY RESULT FROM OR ARISE IN CONNECTION WITH THESE USES.

Use of the formulas, equations, calculations, graphs, and/or other design guide information is at your sole discretion and does not guarantee any specific results or performance. The formulas, equations, graphs, and/or other design guide information are provided as a reference guide only and are intended to assist but not to be solely relied upon for design work, design calculations, or other purposes. Cirrus Logic makes no representations or warranties concerning the formulas, equations, graphs, and/or other design guide information.

Cirrus Logic, Cirrus, the Cirrus Logic logo designs, EXL Core, and the EXL Core logo design are trademarks of Cirrus Logic, Inc. All other brand and product names in this document may be trademarks or service marks of their respective owners.

16 DS961F1

Cirrus Logic CS1616 User Manual

Specifications and Main Features

Frequently Asked Questions

User Manual

Features

1. INTRODUCTION

2. PIN DESCRIPTION

3. CHARACTERISTICS AND SPECIFICATIONS

3.1 Electrical Characteristics

3.2 Thermal Resistance

3.3 Absolute Maximum Ratings

4. TYPICAL PERFORMANCE PLOTS

5. GENERAL DESCRIPTION

5.1 Overview

5.2 IC Startup

5.3 IC Operation

5.3.1 Dimmer Detection

5.3.2 Switch Overpower Protection

5.4 Voltage Clamp Circuit

5.4.1 Clamp Overpower Protection

5.5 Dimmer Angle Extraction and the Dim Mapping Algorithm

5.6 Dual-mode Flyback/Buck-boost

5.6.1 Primary-Side Current Control

5.6.2 Output Current Regulation

5.6.3 Input Current Shaping

5.6.4 Max Primary-side Switching Current

5.6.5 Auxiliary Winding Configuration

5.6.6 Output Open Circuit Protection

5.6.7 Overcurrent Protection

5.6.8 Open Loop Protection

5.7 Overtemperature Protection

5.7.1 Internal Overtemperature Protection

5.7.2 External Overtemperature Protection

6. PACKAGE DRAWING

7. ORDERING INFORMATION

8. ENVIRONMENTAL, MANUFACTURING, & HANDLING INFORMATION

REVISION HISTORY