ATMEL U209B User Manual

查询U209B 供应商

Phase-Control IC – Tacho Applications

Description

The integrated circuit U209B is designed as a phase­control circuit in bipolar technology with an internal
frequency-voltage converter. Furthermore, it has an
internal open-loop amplifier which means it can be used
for motor speed control with tacho feedback.

Features

 Internal frequency-to-voltage converter

The U209B is a 14-pin shrink version of the U211B with
reduced features. Using the U209B, the designer is able
to realize sophisticated as well as economic motor control
systems.

 Triggering pulse typ. 155 mA

U209B

 Externally controlled integrated amplifier
 Automatic soft start with minimized “dead time”
 Voltage and current synchronization
 Retriggering

Block Diagram

14(16) 1(1)

Voltage / Current

detector

10(10)

9(9)

+

–

Control
amplifier

Automatic

retriggering

Phase

control unit



= f (V11)

 Internal supply-voltage monitoring
 Temperature-compensated reference source
 Current requirement ≤ 3 mA

Output

pulse

Supply
voltage

limitation
Reference

voltage

Voltage

monitoring

4(4)

5(5)

6(6)

3(3)

2(2)

13(15)

–V

GND

S

Frequency-

Soft start

–V

S

11(11) 12(12) 8(8) 7(7)

Figure 1. Block diagram (Pins in brackets refer to SO16)

to-voltage

converter

U209B

Ordering Information

Extended Type Number Package Remarks

U209B-x DIP14 Tube

U209B-xFP SO16 Tube

U209B-xFPG3 SO16 Taped and reeled

Rev. A3, 11-Jan-01 1 (11)

U209B

L

=

M

V

230 V ~

N

M

F

2

C

3

Supply

F

25 V

22

1

C

S

–V

2

voltage

16 V

2.2

10

C

GND

voltage

limitation

Reference

13

Voltage

monitoring

U209B

converter

to voltage

Frequency

220 nF

4

C

5

C

Speed sensor

R

1 k 

1 nF

5

1

1

R

TIC

236N



2 W

18 k

IN4007 D

13

R

4

Output

220 

pulse

680 k

2

3.3 nF

R

6

5

)

11

Automatic

retriggering



4

R

470 k

Phase

= f (V



control unit

Soft start

s

–V

8

C

11 12 8 7

F

3

2.2

C

220 nF

7

R

16 V



22 k

R

3



220 k

14 1

9



R

47 k

detector

Voltage / Current

R

Set speed

voltage

12

R

100 k 

11

10

R



100 k



56 k

Control

amplifier

10

9

C

–

+

9

F

2.2 /16 V

Figure 2. Block diagram with typical circuitry for speed regulation

7

C

F

16 V

2.2



8

R

Actual

2 M

speed

voltage



6

R

68 k

6

C

100 nF

Rev. A3, 11-Jan-012 (11)

Description

Mains Supply

The U209B is designed with voltage limiting and can
therefore be supplied directly from the mains. The supply
voltage between Pin 2 (+ pol/) and Pin 3 builds up
across D
series resistance can be approximated using:

Further information regarding the design of the mains
supply can be found in the chapter “Design Calculations
for Mains Supply”. The reference voltage source on Pin
13 of typ. –8.9 V is derived from the supply voltage and
represents the reference level of the control unit.

Operation using an externally stabilised DC voltage is not
recommended.

If the supply cannot be taken directly from the mains
because the power dissipation in R
then the circuit shown in the following figure 3 should be
employed.

and R1 and is smoothed by C

1

1



VM–V

R

2I

S

S

~

24 V~

12345

U209B

. The value of the

1

would be too large,

1

U209B

When the potential on Pin 6 reaches the nominal value
predetermined at Pin 11, a trigger pulse is generated
whose width tp is determined by the value of C
of C2 and hence the pulse width can be evaluated by
assuming 8 s/nF).

The current sensor on Pin 1 ensures that no pulse is gener­ated (for operation with inductive loads) in a new half
cycle as long as the current from the previous half cycle
is still flowing in the opposite direction to the supply
voltage at that instant. This makes sure that “Gaps” in the
load current are prevented.

The control signal on Pin 11 can be in the range 0 V to
–7 V (reference point Pin 2).

If V

= –7 V, the phase angle is at maximum = 

11

the current flow angle is a minimum. The minimum phase
angle 

is when V

min

11

= V

pin2

.

Voltage Monitoring

As the voltage is built up, uncontrolled output pulses are
avoided by internal voltage surveillance. At the same
time, all latches in the circuit (phase control, soft start) are
reset and the soft-start capacitor is short circuited. Used
with a switching hysteresis of 300 mV, this system guar­antees defined start-up behaviour each time the supply
voltage is switched on or after short interruptions of the
mains supply.

Soft Start

(the value

2

, i.e.,

max

As soon as the supply voltage builds up (t1), the integrated
soft start is initiated. Figure 4 shows the behaviour of the

R

1

C

1

voltage across the soft-start capacitor which is identical

Figure 3. Supply voltage for high current requirements

with the voltage on the phase control input on Pin 11. This
behaviour guarantees a gentle start-up for the motor and
automatically ensures the optimum run-up time.

Phase Control

The function of the phase control is largely identical to
that of the well known integrated circuit U2008B. The
phase angle of the trigger pulse is derived by comparing
the ramp voltage. This is mains-synchronized by the volt­age detector with the set value on the control input Pin 4.
The slope of the ramp is determined by C
current. The charging current can be varied using R
Pin 5. The maximum phase angle 
justed using R2.

and its charging

2

can also be ad-

max

on

2

is first charged up to the starting voltage V

3

typically 30 A current (t2). By then reducing the
charging current to approx. 4 A, the slope of the charging
function is substantially reduced so that the rotational
speed of the motor only slowly increases. The charging
current then increases as the voltage across C
giving a progressively rising charging function which
accelerates the motor with increasing rotational speed.
The charging function determines the acceleration up to
the set-point. The charging current can have a maximum
value of 50 A.

with

o

increases

3

C

Rev. A3, 11-Jan-01 3 (11)

U209B

V

C3

V

12

V

0

t

1

t

2

Figure 4. Soft start

t

3

t

tot

t

t1 = build-up of supply voltage
t2 = charging of C3 to starting voltage
t1 + t2 = dead time
t3 = run-up time
t

= total start-up time to required speed

tot

Frequency-to-Voltage Converter

The internal frequency-to-voltage converter
(f/V-converter) generates a DC signal on Pin 9 which is
proportional to the rotational speed using an AC signal
from a tacho generator or a light beam whose frequency
is in turn dependent on the rotational speed. The high
impedance input with a switch-on threshold of typ.
–100 mV gives very reliable operation even when
relatively simple tacho generators are employed. The
tacho frequency is given by:

n

f =

n = revolutions per minute

p = number of pulses per revolution

The converter is based on the charge pumping principle.
With each negative half wave of the input signal, a
quantity of charge determined by C
amplified and then integrated by C
output on Pin 9. The conversion constant is determined
by C5, its charging voltage of Vch, R
internally adjusted charge amplification Gi.

k = Gi  C5  R

 V

6

The analog output voltage is given by

V

= k  f

where: V

o

= 6.7 V

ch

G

= 8.3

i

p[Hz]

60

is internally

5

at the converter

6

(Pin 9) and the

6

ch

The values of C

and C6 must be such that for the highest

5

possible input frequency, the maximum output voltage V
does not exceed 6 V. The R
C

is charging up. To obtain good linearity of the

5

on Pin 8 is approx. 6 kΩ while

i

f/V converter the time constant resulting from Ri and C
should be considerably less (1/5) than the time span of the
negative half cycle for the highest possible input
frequency. The amount of remaining ripple on the output
voltage on Pin 9 is dependent on C5, C

and the internal

6

charge amplification.

V



O

The ripple ∆V

Gi Vch C

C

can be reduced by using larger values of

o

5

6

C6, however, the maximum conversion speed will then
also be reduced.

The value of this capacitor should be chosen to fit the
particular control loop where it is going to be used.

Control Amplifier

The integrated control amplifier with differential input
compares the set value (Pin 10) with the instantaneous
value on Pin 9 and generates a regulating voltage on the
output Pin 11 (together with external circuitry on Pin 12)
which always tries to hold the real voltage at the value of
the set voltages. The amplifier has a transmittance of typi­cally 110 A/V and a bipolar current source output on Pin
11 which operates with typically ±100 A. The
amplification and frequency response are determined by
R7, C7, C
power divider, C4, C5, R6, C6, R7, C7, C

and R8 (can be left out). For operation as a

8

and R8 can be

8

left out. Pin 9 should be connected with Pin 11 and Pin 7
with Pin 2. The phase angle of the triggering pulse can be
adjusted using the voltage on Pin 10. An internal limiting
circuit prevents the voltage on Pin 11 from becoming
more negative than V

13

+ 1 V.

Pulse-Output Stage

The pulse-output stage is short-circuit protected and can
typically deliver currents of 125 mA. For the design of
smaller triggering currents, the function I

GT

= f (R

GT

) can

be taken from figure 14.

Automatic Retriggering

The automatic retriggering prevents half cycles without
current flow, even if the triacs are turned off earlier e.g.,
due to not exactly centered collector (brush lifter) or in the
event of unsuccessful triggering. If necessary, another
triggering pulse is generated after a time lapse of
tPP = 4.5 tP and this is repeated until either the triac fires
or the half cycle finishes.

0

5

Rev. A3, 11-Jan-014 (11)

U209B

General Hints and Explanation of Terms

To ensure safe and trouble-free operation, the following
points should be taken into consideration when circuits
are being constructed or in the design of printed circuit
boards.

 The connecting lines from C

be as short as possible, and the connection to Pin 2
should not carry any additional high current such as
the load current. When selecting C2, a low tempera­ture coefficient is desirable.

 The common (earth) connections of the set-point

generator, the tacho-generator and the final inter­ference suppression capacitor C
should not carry load current.

 The tacho generator should be mounted without

influence by strong stray fields from the motor.

to Pin 6 and Pin 2 should

2

of the f/V converter

4

V

Mains
Supply

Trigger
Pulse

Load
Voltage

Load
Current

V

GT

V

L

I

L

/2  3/2 2

t

p

t

= 4.5 t

pp

p





Figure 5. Explanation of terms in phase relationship

Design Calculations for Mains Supply

The following equations can be used for the evaluation of the series resistor R

R

P

(R1max)

1max

 0.85

(V



V

Mmin–VSmax

2I

tot

Mmax–VSmin

2R

1

R

 0.85

1min

2

)

VM–V

2I

Smax

Smin

where:
V

= Mains voltage 230 V

M

V

= Supply voltage on Pin 3

S

I

= Total DC current requirement of the circuit

tot

= IS + Ip + I

I

= Current requirement of the IC in mA

Smax

I

= Average current requirement of the triggering pulse

p

I

= Current requirement of other peripheral components

x

x

R1 can be easily evaluated from figures 15 to 17

Rev. A3, 11-Jan-01 5 (11)

for worst case conditions:

1

U209B

Absolute Maximum Ratings

Reference point Pin 2, unless otherwise specified

Parameters Symbol Value Unit

Current requirement Pin 3

t ≤ 10 s

Synchronization current Pin 1

Pin 14
t < 10 s Pin 1
t < 10 s Pin 14

f/V converter:
Input current Pin 7

t < 10 s

Phase control: Pin 11
Input voltage

Input current
Soft start:
Input voltage Pin 12 –V
Pulse output:
Reverse voltage Pin 4 V

Amplifier

Input voltage Pin 10 –V
Pin 8 open Pin 9 –V

Reference voltage source

Output current Pin 13 I
Power dissipation T

T

amb
amb

= 45°C
= 80°C

Storage temperature range T
Junction temperature T
Ambient temperature range T

I

I

–I

S

–i

S

syncI

syncV

±i

i

±i

v

I

eff

±i

i

–V

±I

I

R

o

P

tot

stg

j

amb

30

100

5

5
35
35

3
13

I

0 to 7

500

I

I
I

|V13| to 0 V

V

to 5 V

S

|VS|

|V13| to 0 V

mA
mA
mA
mA
mA
mA

mA
mA

V



7.5 mA

570
320

mW
mW

–40 to +125 °C

125 °C

–10 to +100 °C

Thermal Resistance

Parameters Symbol Maximum Unit

Junction ambient DIP14

SO16: on p.c. board
SO16: on ceramic substrate

Electrical Characteristics

–V

= 13.0 V, T

S

Parameters Test Conditions / Pin Symbol Min. Typ. Max. Unit

Supply voltage for mains
operations
Supply voltage limitation –I

DC supply current –VS = 13.0 V Pin 3 –I
Reference voltage source –IL = 10 A Pin 13

Temperature coefficient Pin 13 TC

= 25°C, reference point Pin 2, unless otherwise specified

amb

Pin 3 –V

= 3 mA Pin 3

S

–IS = 30 mA

–IL = 5 mA

–V

V

R

thJA

R

thJA

R

thJA

S

S

S

Ref

VRef

140
180
100

13.0 V

14.6

14.7

Limit

16.6

16.8

K/W
K/W
K/W

1.1 2.5 3.0 mA

8.6

8.3

8.9 9.2

9.1

0.5 mV/K

Rev. A3, 11-Jan-016 (11)

V

V
V

V
V

U209B

UnitMax.Typ.Min.SymbolTest Conditions / PinParameters

Voltage monitoring Pin 3

Turn-on threshold –V
Turn-off threshold –V

TON

TOFF

9.9 10.9 V

Phase-control currents

Current synchronization Pin 1 ±I
Voltage synchronization Pin 14 ±I

syncl

syncV

Voltage limitation ±IL = 5 mA Pin 1, 14 ±V

l

0.35 2.0 mA

0.35 2.0 mA

1.4 1.6 1.8 V

Reference ramp, figure 6
Charge current I

= f (R

6

),

5

I

6

1 20 A

R5 = 1 K ... 820 k Pin 6

Rϕ – reference voltage  ≥ = 180 ° Pin 5, 3 Vϕ
Temperature coefficient Pin 5 TCϕ

Ref

Ref

1.06 1.13 1.18 V

Output pulse

Output pulse current R
Reverse current Pin 4 I
Output pulse width Pin 5, 2 t

= 0, V

V

= 1.2 V Pin 4 I

GT

O

OR

100 155 190 mA

p

Automatic retriggering

Repetition rate Pin 4 t

pp

3 4.5 6 t

Amplifier

Common-mode voltage

Pin 9, 10 V

ICR

(V13–1V) (V2–1V) V
range
Input bias current Pin 10 I

Input offset voltage Pin 9, 10 V
Output current Pin 11 –I

Short circuit forward

I11 = f (V

) Pin 11 Y

9/10

+I

IB

IO

O
O

f

75
88

transmittance

Frequency-to-voltage converter

Input bias current Pin 7 I
Input voltage limitation ±I

1 mA Pin 7 +V

I =

Turn-on threshold Pin 7 –V
Turn-off threshold Pin 7 –V
Discharge current Figure 2 Pin 8 I
Charge transfer voltage Pin 8 V
Charge transfer gain I9 / I

8

Conversion factor C

= 1 nF, R

8

Pin 8/9 G

= 100 k k 5.5 mV/Hz

9

Operating range f/V output Ref. point Pin 13 Pin 9 V

IB

–V

TOFF
dis

I

I

TON

ch

i

O

660

7.25

20 50 mV

6.50 6.70 6.90 V

7.5 8.3 9.0

Linearity ± 1 %
Soft start Pin 12
f/v–converter non-active figures 8 and 9
Starting current V
Final current V12 = –0.5 V I

12

= V

, V7 = V

13

2

I

O
O

20 30 50 A

50 85 130 A
f/v–converter active figures 7 and 10
Starting current V
Final current V12 = –0.5 V I
Discharge current Restart pulse –I

12

= V

13

I

O
O

O

2 4 6 A

30 55 80 A

0.5 3 10 mA

11.2 13 V

0.5 mV/K

0.01 3.0 A
8 s/nF

0.01 1 mA

10 mV

110
120

145
165

A
A

1000 A/V

0.6 2 A
750

8.05

mV

V

100 150 mV

0.5 mA

0 – 6 V

p

Rev. A3, 11-Jan-01 7 (11)

U209B

240

100

500

200

10nF 4.7nF

 °

160

120

Phase Angle ( )

80

0

0 0.2 0.4 0.6 0.8

R ( M )

Figure 6. Ramp control

100

80

Reference Point Pin 13

60



12

I ( A)

40

Reference Point Pin 2

2.2nF

C /t=1.5nF



1.0

10

8

6

12

V ( V )

4

2

0

Reference Point Pin 13

t=f

(C3)

Figure 9. Soft-start voltage (f/V -converter non-active)

10

8

Reference Point Pin 13

6

12

V ( V )

4

20

0

02468

V12 ( V )

Figure 7. Soft-start charge current (f/V-converter active)

80

60



12

I ( A)

40

20

Reference Point Pin 16

0

02468

V12 ( V )

Figure 8. Soft-start charge current (f/V-converter non-active)

2

10

0

t=f

(C3)

Figure 10. Soft-start voltage (f/V -converter active)

250

Reference Point Pin 2



0

8

I ( A )

–250

10

–500

–10 –8 –6 –4 –2

V8 ( V )

02

4

Figure 11. f/V-converter voltage limitation

Rev. A3, 11-Jan-018 (11)

U209B

100

50

6

10

8

Reference Point Pin 13

6

12

V ( V )

4

40

30



1

R ( k )

20

Mains Supply
230 V

2

10

0

t=f

(C3)

Motor Standstill ( Dead Time )
Motor in Action

Figure 12. Soft start function

0

04812

I

( mA )

tot

Figure 15. Determination of R

1

16

6

100

50



0

12

I ( A )

–50

Control Amplifier

P ( W )

(R1)

5

4

3

2

Mains Supply
230 V

Reference Point

–100

for I12 = –4V

–300 –200 –100 0 200

V

10–11

100

( V )

Figure 13. Amplifier output characteristic

80

300

1

0

036912

I

( mA )

tot

Figure 16. Power dissipation of R

1

according to current consumption

5

Mains Supply

4

230 V

15

60

GT

I ( mA )

40

1.4V

V

= 0.8V

GT

20

0

0 200 400 600 800

1000

RGT (  )

3

(R1)

P ( W )

2

1

0

0102030

R

( k )

1

40

Figure 14. Pulse output

Figure 17. Power dissipation of R

1

Rev. A3, 11-Jan-01 9 (11)

U209B

Package Information

Package DIP14

Dimensions in mm

20.0 max

7.77

7.47

4.8 max

Package SO16

Dimensions in mm

3.3

0.5 min

1.64

0.58

1.44

0.48

15.24

14 8

17

10.0

9.85

2.54

technical drawings
according to DIN
specifications

6.4 max

0.36 max

9.8

8.2

5.2

4.8

3.7

1.4

0.4

1.27

8.89

16 9

18

0.25

0.10

3.8

6.15

5.85

technical drawings
according to DIN
specifications

0.2

Rev. A3, 11-Jan-0110 (11)

U209B

Ozone Depleting Substances Policy Statement

It is the policy of Atmel Germany GmbH to

1. Meet all present and future national and international statutory requirements.

2. Regularly and continuously improve the performance of our products, processes, distribution and operating systems
with respect to their impact on the health and safety of our employees and the public, as well as their impact on
the environment.

It is particular concern to control or eliminate releases of those substances into the atmosphere which are known as
ozone depleting substances (ODSs).

The Montreal Protocol (1987) and its London Amendments ( 1990) intend to severely restrict the use of ODSs and forbid
their use within the next ten years. Various national and international initiatives are pressing for an earlier ban on these
substances.

Atmel Germany GmbH has been able to use its policy of continuous improvements to eliminate the use of ODSs listed
in the following documents.

1. Annex A, B and list of transitional substances of the Montreal Protocol and the London Amendments respectively

2. Class I and II ozone depleting substances in the Clean Air Act Amendments of 1990 by the Environmental
Protection Agency (EPA) in the USA

3. Council Decision 88/540/EEC and 91/690/EEC Annex A, B and C (transitional substances) respectively.

Atmel Germany GmbH can certify that our semiconductors are not manufactured with ozone depleting substances
and do not contain such substances.

We reserve the right to make changes to improve technical design and may do so without further notice .

Parameters can vary in different applications. All operating parameters must be validated for each customer

application by the customer. Should the buyer use Atmel Wireless & Microcontrollers products for any unintended

or unauthorized application, the buyer shall indemnify Atmel Wireless & Microcontrollers against all claims,

costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death

associated with such unintended or unauthorized use.

Data sheets can also be retrieved from the Internet: http://www.atmel–wm.com

Atmel Germany GmbH, P.O.B. 3535, D-74025 Heilbronn, Germany

Telephone: [phone], Fax number: 49 (0)7131 67 2423

Rev. A3, 11-Jan-01 11 (11)