This document describes the features and the system integration of
TOBY-L4 series multi-mode cellular modules.
The modules are a complete and cost efficient LTE-FDD, LTE-TDD, DCHSPA+, (E)GPRS multi-mode and multi-band solution with uCPU
embedded Linux programming capability. The modules offer up to
301.5 Mb/s download and up to 51.0 Mb/s upload data rates with
Category 6 LTE-Advanced carrier aggregation technology in the
compact TOBY form factor.
www.u-blox.com
UBX-16024839 - R04
TOBY-L4 series
LTE Advanced (Cat 6) modules
with 3G and 2G fallback
System Integration Manual
TOBY-L4 series - System Integration Manual
Document Information
Title
TOBY-L4 series
Subtitle
LTE Advanced (Cat 6) modules
with 3G and 2G fallback
Document type
System Integration Manual
Document number
UBX-16024839
Revision, date
R04
27-Feb-2018
Disclosure restriction
Product Status
Corresponding content status
Functional Sample
Draft
For functional testing. Revised and supplementary data will be published later.
In Development /
Prototype
Objective Specification
Target values. Revised and supplementary data will be published later.
Engineering Sample
Advance Information
Data based on early testing. Revised and supplementary data will be published later.
Initial Production
Early Prod. Information
Data from product verification. Revised and supplementary data may be published later.
Mass Production /
End of Life
Production Information
Final product specification.
Name
Type number
Modem version
Application version
PCN reference
Product status
TOBY-L4006
TOBY-L4006-00A-00
TBD
TBD
TBD
Functional Sample
TOBY-L4006-50A-00
40.24
A00.02
UBX-18007908
Engineering Sample
TOBY-L4106
TOBY-L4106-00A-00
TBD
TBD
TBD
Functional Sample
TOBY-L4106-50A-00
40.24
A00.02
UBX-18007908
Engineering Sample
TOBY-L4206
TOBY-L4206-00A-00
TBD
TBD
TBD
Functional Sample
TOBY-L4206-50A-00
TBD
TBD
TBD
Functional Sample
TOBY-L4906
TOBY-L4906-00A-00
TBD
TBD
TBD
Functional Sample
TOBY-L4906-50A-00
40.19
A00.02
UBX-17058711
Engineering Sample
This document applies to the following products:
u-blox reserves all rights to this document and the information contained herein. Products, names, logos and designs described herein may in
whole or in part be subject to intellectual property rights. Reproduction, use, modification or disclosure to third parties of this document or
any part thereof without the express permission of u-blox is strictly prohibited.
The information contained herein is provided “as is” and u-blox assumes no liability for the use of the information. No warranty, either express
or implied, is given, including but not limited, with respect to the accuracy, correctness, reliability and fitness for a particular purpose of the
information. This document may be revised by u-blox at any time. For most recent documents, please visit www.u-blox.com.
u-blox® is a registered trademark of u-blox Holding AG in the EU and other countries. Microsoft and Windows are either registered trademarks
or trademarks of Microsoft Corporation in the United States and/or other countries. All other registered trademarks or trademarks mentioned
in this document are property of their respective owners.
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TOBY-L4 series - System Integration Manual
Preface
u-blox Technical Documentation
As part of our commitment to customer support, u-blox maintains an extensive volume of technical documentation
for our products. In addition to our product-specific technical data sheets, the following manuals are available to
assist u-blox customers in product design and development.
AT Commands Manual: This document provides the description of the AT commands supported by the
u-blox cellular modules.
System Integration Manual: This document provides the description of u-blox cellular modules’ system from
the hardware and the software point of view, it provides hardware design guidelines for the optimal
integration of the cellular modules in the application device and it provides information on how to set up
production and final product tests on application devices integrating the cellular modules.
Application Note: These documents provide guidelines and information on specific hardware and/or
software topics on u-blox cellular modules. See Related documents for a list of Application Notes related to
your Cellular Module.
How to use this Manual
The TOBY-L4 series System Integration Manual provides the necessary information to successfully design and
configure the u-blox cellular modules.
This manual has a modular structure. It is not necessary to read it from the beginning to the end.
The following symbols are used to highlight important information within the manual:
An index finger points out key information pertaining to module integration and performance.
A warning symbol indicates actions that could negatively impact or damage the module.
Questions
If you have any questions about u-blox Cellular Integration:
Read this manual carefully.
Contact our information service on the homepage http://www.u-blox.com/
Technical Support
Worldwide Web
Our website (http://www.u-blox.com/) is a rich pool of information. Product information, technical documents can
be accessed 24h a day.
By E-mail
Contact the closest Technical Support office by email. Use our service pool email addresses rather than any personal
email address of our staff. This makes sure that your request is processed as soon as possible. You will find the
contact details at the end of the document.
Helpful Information when Contacting Technical Support
When contacting Technical Support, have the following information ready:
Module type (TOBY-L4106) and firmware version
Module configuration
Clear description of your question or the problem
A short description of the application
Your complete contact details
The TOBY-L4 series modules support multi-band LTE-FDD, LTE-TDD, DC-HSPA+, and (E)GPRS radio access
technologies (see Table 1) in the very small TOBY 248-pin LGA form-factor (35.6 x 24.8 mm), which is easy to
integrate in compact designs.
TOBY-L4 series modules are form-factor compatible with the other u-blox cellular module families (including SARA,
LISA, LARA, and TOBY form-factors): this allows customers to take maximum advantage of their hardware and
software investments, and provides very short time-to-market.
With LTE-Advanced carrier aggregation category 6 data rates up to 301.5 Mbit/s (downlink) / 51.0 Mbit/s (uplink),
the modules are ideal for applications requiring the highest data-rates and high-speed internet access. Reduced
cost variants supporting LTE Cat 4 or LTE Cat 1 will be available for lower speed or “pure” telematics devices.
TOBY-L4 series include the following LTE Cat 6 modules with 3G and 2G fallback:
TOBY-L4006 modules, mainly designed for operation in North America
TOBY-L4106 modules, mainly designed for operation in Europe
TOBY-L4206 modules, mainly designed for operation in Asia-Pacific and South America
TOBY-L4906 modules, mainly designed for operation in China
TOBY-L4 series modules include the following product versions:
The “00” product versions, integrating the u-blox uCPU on-chip processor to allow customers to run their
dedicated applications on an embedded Linux distribution based on Yocto, with RIL-Core connectivity APIs
The “50” product versions, which can be controlled by an external application processor through standard
and u-blox proprietary AT commands described in the u-blox AT Commands Manual [2]
TOBY-L4 series modules are the ideal product for the development of all kinds of automotive devices, such as
smart antennas and in-dash telematics / infotainment devices, supporting a comprehensive set of HW interfaces
(including RGMII/RMII for Ethernet and analog audio) over a very extended temperature range that allow the
establishment of an emergency call up to +95 °C, complemented by a set of state-of-the art security features.
TOBY-L4 series modules are also the perfect choice for consumer fixed-wireless terminals, mobile routers and
gateways, applications requiring video streaming and many other industrial (M2M) applications.
TOBY-L4 series modules are manufactured in ISO/TS 16949 certified sites, with the highest production standards
and the highest quality and reliability. Each module is fully tested and inspected during production. The modules
are qualified according to the automotive requirements as for systems installed in vehicles.
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TOBY-L4 series - System Integration Manual
Model
Region
Bands
Interfaces
Features
Grade
LTE FDD bands LTE TDD bands UMTS FDD bands GSM bands UART USB 2.0 device/host* USB 3.0 device** SPI
RGMII / RMII eMMC SDIO DDC (I
2
C)
SIM
GPIO ADC Antenna supervisor CA / MIMO / Rx Diversity Analog audio Digital Audio uCPU for customer applications GNSS via modem Wi-Fi via modem Network indication Jamming detection Embedded TCP/UDP stack Embedded HTTP,
FTP, SSL
FOTA Dual stack IPv4/IPv6 Standard Professional Automotive
TOBY-L4006-00
North
America
2,4,5
7,12
13,29
2
4,5
850
1900
4 1 1 2 1 1 1 2 2
14
2
●
● ● ● ● ●
● ● ● ● ●
●
●
TOBY-L4006-50
North
America
2,4,5
7,12
13,29
2
4,5
850
1900
1 1 2 9
●
●
● ●
● ●
●
TOBY-L4106-00
EMEA
1,3
7,8
20
38
1,8
900
1800
4 1 1 2 1 1 1 2 2
14
2
● ● ● ● ●
● ● ● ● ●
●
●
●
TOBY-L4106-50
EMEA
1,3
7,8
20
38
1,8
900
1800
1 1 2 9
●
●
●
●
● ●
●
TOBY-L4206-00
APAC,
South
America
1,3,5
7,8,9
19,28
1
5,8
Quad
4 1 1 2 1 1 1 2 2
14
2
●
● ● ●
●
● ● ● ● ●
●
● ●
TOBY-L4206-50
APAC,
South
America
1,3,5
7,8,9
19,28
1
5,8
Quad
1 1 2 9
●
●
●
●
● ●
●
TOBY-L4906-00
China
1,3
39
40,41
1,8
900
1800
4 1 1 2 1 1 1 2 2
14
2
●
● ● ●
●
● ● ● ● ●
●
● ●
TOBY-L4906-50
China
1,3
39
40,41
1,8
900
1800
1 1 2 9
●
●
●
●
● ●
●
* USB 2.0 host role not supported by the "50" product versions
** USB 3.0 interface supported by future firmware versions
Table 1 summarizes the main features and interfaces of the TOBY-L4 series modules.
Table 1: TOBY-L4 series main features summary
TOBY-L4 series modules provide multi-band 4G / 3G / 2G multi-mode radio access technologies, based on the
3GPP Release 10 protocol stack, with the main characteristics summarized in Table 2 and Table 3.
UBX-16024839 - R04 System description
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LTE
3G
2G
LTE-Advanced Carrier Aggregation
Frequency Division Duplex (LTE FDD)
Time Division Duplex (LTE TDD)
Down-Link CA / MIMO / Rx diversity
Dual-Cell High Speed Packet Access
Frequency Division Duplex (UMTS FDD)
Down-Link Rx diversity
Enhanced Data rate GSM Evolution (EDGE)
Time Division Multiple Access (TDMA)
DL Advanced Rx Performance Phase 1
LTE FDD Power Class
Class 3 (23 dBm)
LTE TDD Power Class
Class 3 (23 dBm)
UMTS FDD Power Class
Class 3 (24 dBm)
GMSK Power Class
Class 4 (33 dBm) for GSM/E-GSM bands
Class 1 (30 dBm) for DCS/PCS bands
8-PSK Power Class
Class E2 (27 dBm) for GSM/E-GSM bands
Class E2 (26 dBm) for DCS/PCS bands
Data rate
LTE category 6:
up to 301.5 Mbit/s DL
up to 51.0 Mbit/s UL
Data rate
FDD UE categories:
DL cat.24, up to 42.2 Mbit/s
UL cat.6, up to 5.76 Mbit/s
Table 2: TOBY-L4 series LTE, 3G and 2G characteristics summary
TOBY-L4 series - System Integration Manual
Table 3: TOBY-L4 series supported bands2 and Carrier Aggregation combinations summary
Down-Link Rx diversity not supported on this band
TOBY-L4 series modules support all the E-UTRA channel bandwidths for each operating band according to 3GPP TS 36.521-1 [13].
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TOBY-L4 series - System Integration Manual
Cellular
Base-band
Processor
Memory
Power Management Unit
26 MHz
32.768 kHz
ANT1
RF
Transceiver
ANT2
V_INT (I/O)
V_BCKP (RTC)
VCC (Supply)
2 x SIM
USB 2.0 / 3.0
2 x ADC
Power on
External reset
PAs
LNAsFilters
Filters
Duplexer
Filters
PAs
LNAsFilters
Filters
Duplexer
Filters
LNAsFiltersFilters
LNAsFiltersFilters
Switch
Switch
2 x DDC (I2C)
SDIO
4 x UART
Analog audio
Antenna detection
Host Select
2 x SPI
RGMII
eMCC
2 x Digital audio (I2S)
GPIOs
1.2 Architecture
Figure 1 summarizes the internal architecture of the TOBY-L4 series modules.
Figure 1: TOBY-L4 series modules simplified block diagram
TOBY-L4 series modules internally consist of the RF, Baseband and Power Management sections described herein
with more details than the simplified block diagrams of Figure 1.
RF section
The RF section is composed of an RF transceiver, PAs, LNAs, crystal oscillator, filters, duplexers and RF switches.
The Tx signal is pre-amplified by the RF transceiver, then output to the primary antenna input/output port (ANT1)
of the module via power amplifier (PA), SAW band pass filters band, specific duplexer and antenna switch.
Dual receiving paths are implemented according to Carrier Aggregation, MIMO, and Receiver Diversity radio
technologies supported by the modules as LTE category 6 and HSDPA category 24 User Equipments: incoming
signals are received through the primary (ANT1) and the secondary (ANT2) antenna input ports which are
connected to the RF transceiver via specific antenna switch, diplexer, duplexer, LNA, SAW band pass filters.
RF transceiver performs modulation, up-conversion of the baseband I/O signals for Tx, down-conversion and
demodulation of the dual RF signals for Rx. The RF transceiver contains:
Single chain high linearity receivers with integrated LNAs for multi-band multi-mode CA operation,
Highly linear RF demodulator / modulator capable GMSK, 8-PSK, QPSK, 16-QAM, 64-QAM
RF synthesizer,
VCO.
Power Amplifiers (PA) amplify the Tx signal modulated by the RF transceiver
RF switches connect the primary (ANT1) and secondary (ANT2) antenna ports to the suitable Tx / Rx path
SAW duplexers and band pass filters separate the Tx and Rx signal paths and provide RF filtering
26 MHz voltage-controlled temperature-controlled crystal oscillator (VC-TCXO) generates the clock reference
in active mode or connected mode.
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TOBY-L4 series - System Integration Manual
Baseband and power management section
The Baseband and Power Management section is composed of the following main elements:
A mixed signal ASIC, which integrates
o Microprocessor for control functions
o DSP core for cellular Layer 1 and digital processing of Rx and Tx signal paths
o Memory interface controller
o Dedicated peripheral blocks for control of the USB, SIM and generic digital interfaces
o Interfaces to the RF transceiver ASIC
Memory system, which includes NAND flash and LPDDR2 RAM
Voltage regulators to derive all the subsystem supply voltages from the module supply input VCC
Voltage source for external use: V_INT
Hardware power on
Hardware reset
Low power idle mode support
32.768 kHz crystal oscillator to provide the clock reference in the low power idle mode, which can be set by
enabling the power saving configuration.
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TOBY-L4 series - System Integration Manual
Function
Pin Name
Pin No
I/O
Description
Remarks
Power
VCC
70,71,72
I
Module supply input
VCC supply circuit affects the RF performance and
compliance of the device integrating the module with
applicable required certification schemes.
See section 1.5.1 for functional description / requirements.
See section 2.2.1 for external circuit design-in.
GND pins are internally connected each other.
External ground connection affects the RF and thermal
performance of the device.
See section 1.5.1 for functional description.
See section 2.2.1 for external circuit design-in.
V_BCKP
3
I/O
RTC back-up supply
If the VCC voltage is below the operating range, the RTC
block can be externally supplied through the V_BCKP pin.
See section 1.5.2 for functional description.
See section 2.2.2 for external circuit design-in.
V_INT
5 O Generic digital
interfaces supply
output
V_INT = 1.8 V (typical) generated by internal DC/DC
regulator when the module is switched on.
Test-Point for diagnostic access is recommended.
See section 1.5.3 for functional description.
See section 2.2.3 for external circuit design-in.
System
PWR_ON
20 I Power-on input
Internal 35 k pull-up resistor to internal 1.3 V supply rail.
Test-Point for diagnostic access is recommended.
See section 1.6.1 for functional description.
See section 2.3.1 for external circuit design-in.
RESET_N
23 I External reset input
Internal 100 k pull-up resistor to V_INT.
Test-Point for diagnostic access is recommended.
See section 1.6.3 for functional description.
See section 2.3.2 for external circuit design-in.
HOST_SELECT0
26
I/O / I GPIO /
External Interrupt
1.8 V GPIO or External Interrupt configurable by uCPU API.
See sections 1.6.4, 1.13 for functional description.
See sections 2.3.3, 2.10 for external circuit design-in.
HOST_SELECT1
62
I/O / I GPIO /
External Interrupt
1.8 V GPIO or External Interrupt configurable by uCPU API.
See sections 1.6.4, 1.13 for functional description.
See sections 2.3.3, 2.10 for external circuit design-in.
Antennas
ANT1
81
I/O
Primary antenna
Main Tx / Rx antenna interface.
50 nominal characteristic impedance.
Antenna circuit affects the RF performance and application
device compliance with required certification schemes.
See section 1.7.1 for functional description / requirements.
See section 2.4 for external circuit design-in.
ANT2
87 I Secondary antenna
Rx only for Down-Link CA, MIMO and Rx diversity.
50 nominal characteristic impedance.
Antenna circuit affects the RF performance and application
device compliance with required certification schemes.
See section 1.7.1 for functional description / requirements.
See section 2.4 for external circuit design-in.
ANT_DET
75 I Antenna detection
ADC for antenna presence detection function.
See section 1.7.2 for functional description.
See section 2.4.2 for external circuit design-in.
1.3 Pin-out
Table 4 lists the pin-out of the TOBY-L4 series modules, with pins grouped by function.
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TOBY-L4 series - System Integration Manual
Function
Pin Name
Pin No
I/O
Description
Remarks
SIM0
VSIM
59 O SIM0 supply output
VSIM = 1.8 V / 3 V output as per the connected SIM type.
See section 1.8 for functional description.
See section 2.5 for external circuit design-in.
SIM_IO
57
I/O
SIM0 data
Data input/output for 1.8 V / 3 V SIM.
Internal 4.7 k pull-up to VSIM.
See section 1.8 for functional description.
See section 2.5 for external circuit design-in.
SIM_CLK
56 O SIM0 clock
3.9 MHz clock output for 1.8 V / 3 V SIM.
See section 1.8 for functional description.
See section 2.5 for external circuit design-in.
SIM_RST
58 O SIM0 reset
Reset output for 1.8 V / 3 V SIM.
See section 1.8 for functional description.
See section 2.5 for external circuit design-in.
SIM1
VSIM1
172 O SIM1 supply output
VSIM1 = 1.8 V / 3 V output as per the connected SIM type.
See section 1.8 for functional description.
See section 2.5 for external circuit design-in.
SIM1_IO
178
I/O
SIM1 data
Data input/output for 1.8 V / 3 V SIM.
Internal 4.7 k pull-up to VSIM1.
See section 1.8 for functional description.
See section 2.5 for external circuit design-in.
SIM1_CLK
182 O SIM1 clock
3.9 MHz clock output for 1.8 V / 3 V SIM.
See section 1.8 for functional description.
See section 2.5 for external circuit design-in.
SIM1_RST
177 O SIM1 reset
Reset output for 1.8 V / 3 V SIM.
See section 1.8 for functional description.
See section 2.5 for external circuit design-in.
USB
VUSB_DET
4 I USB detect input
VBUS (5 V typical) generated by the host must be connected
to this pin to enable the module USB device interface.
Test-Point for diagnostic / FW update access is
recommended.
See section 1.9.1 for functional description.
See section 2.6.1 for external circuit design-in.
USB_D–
27
I/O
USB High-Speed 2.0
diff. transceiver (–)
90 nominal differential impedance (Z0).
30 nominal common mode impedance (Z
CM
).
Pull-up or pull-down resistors and external series resistors as
required by the USB 2.0 specifications [3] are part of the
USB pin driver and need not be provided externally.
Test-Point for diagnostic / FW update access is recommended.
See section 1.9.1 for functional description.
See section 2.6.1 for external circuit design-in.
USB_D+
28
I/O
USB High-Speed 2.0
diff. transceiver (+)
90 nominal differential impedance (Z0).
30 nominal common mode impedance (Z
CM
).
Pull-up or pull-down resistors and external series resistors as
required by the USB 2.0 specifications [3] are part of the
USB pin driver and need not be provided externally.
Test-Point for diagnostic / FW update access is recommended.
See section 1.9.1 for functional description.
See section 2.6.1 for external circuit design-in.
USB_ID
168 I USB device
identification
Pin for ID resistance measurement.
See section 1.9.1 for functional description.
See section 2.6.1 for external circuit design-in.
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Function
Pin Name
Pin No
I/O
Description
Remarks
USB_SSTX+
175 O USB Super-Speed 3.0
diff. transmitter (+)
90 nominal differential characteristic impedance.
Internal series 100 nF capacitor for AC coupling.
Compliant with USB Revision 3.0 specification [4].
See section 1.9.1 for functional description.
See section 2.6.1 for external circuit design-in.
USB_SSTX–
176 O USB Super-Speed 3.0
diff. transmitter (–)
90 nominal differential characteristic impedance.
Internal series 100 nF capacitor for AC coupling.
Compliant with USB Revision 3.0 specification [4].
See section 1.9.1 for functional description.
See section 2.6.1 for external circuit design-in.
USB_SSRX+
170 I USB Super-Speed 3.0
diff. receiver (+)
90 nominal differential characteristic impedance.
Compliant with USB Revision 3.0 specification [4].
See section 1.9.1 for functional description.
See section 2.6.1 for external circuit design-in.
USB_SSRX–
171 I USB Super-Speed 3.0
diff. receiver (–)
90 nominal differential characteristic impedance.
Compliant with USB Revision 3.0 specification [4].
See section 1.9.1 for functional description.
See section 2.6.1 for external circuit design-in.
UART0
RXD
17 O UART0 data output
1.8 V output, Circuit 104 (RXD) in ITU-T V.24.
Test-Point for diagnostic access recommended.
See section 1.9.2 for functional description.
See section 2.6.2 for external circuit design-in.
TXD
16 I UART0 data input
1.8 V input, Circuit 103 (TXD) in ITU-T V.24.
Internal active pull-up to V_INT.
Test-Point for diagnostic access recommended.
See section 1.9.2 for functional description.
See section 2.6.2 for external circuit design-in.
CTS
15 O UART0 clear to send
output
1.8 V output, Circuit 106 (CTS) in ITU-T V.24.
See section 1.9.2 for functional description.
See section 2.6.2 for external circuit design-in.
RTS
14 I UART0 ready to
send input
1.8 V input, Circuit 105 (RTS) in ITU-T V.24.
Internal active pull-up to V_INT.
See section 1.9.2 for functional description.
See section 2.6.2 for external circuit design-in.
DSR
10
I/O / I GPIO /
External Interrupt
1.8 V GPIO or External Interrupt configurable by uCPU API.
See sections 1.9.2, 1.13 for functional description.
See sections 2.6.1, 2.10 for external circuit design-in.
RI
11
O /
I/O /
I
UART0 ring indicator /
GPIO /
External Interrupt
1.8 V output, Circuit 125 (RI) in ITU-T V.24.
Configurable as GPIO or External Interrupt.
See sections 1.9.2, 1.13 for functional description.
See sections 2.6.1, 2.10 for external circuit design-in.
DTR
13
I/O / I GPIO /
External Interrupt
1.8 V GPIO or External Interrupt configurable by uCPU API.
See sections 1.9.2, 1.13 for functional description.
See sections 2.6.1, 2.10 for external circuit design-in.
DCD
12
I/O / I GPIO /
External Interrupt
1.8 V GPIO or External Interrupt configurable by uCPU API.
See sections 1.9.2, 1.13 for functional description.
See sections 2.6.1, 2.10 for external circuit design-in.
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Function
Pin Name
Pin No
I/O
Description
Remarks
UART1
RXD1
160
O / O UART1 data output /
SPI1 MOSI
1.8 V output, Circuit 104 (RXD) in ITU-T V.24,
alternatively configurable as SPI1 MOSI by uCPU API.
See section 1.9.2 / 1.9.3 for functional description.
See section 2.6.2 / 2.6.3 for external circuit design-in.
TXD1
159
I / I UART1 data input /
SPI1 MISO
1.8 V input, Circuit 103 (TXD) in ITU-T V.24,
alternatively configurable as SPI1 MISO by uCPU API.
Internal pull-up to V_INT enabled when UART1 data input.
See section 1.9.2 / 1.9.3 for functional description.
See section 2.6.2 / 2.6.3 for external circuit design-in.
CTS1
195
O / O UART1 CTS output /
SPI1 Chip Select
1.8 V output, Circuit 106 (CTS) in ITU-T V.24,
alternatively configurable as SPI1 Chip Select by uCPU API.
See section 1.9.2 / 1.9.3 for functional description.
See section 2.6.2 / 2.6.3 for external circuit design-in.
RTS1
193
I / O UART1 RTS input /
SPI1 Clock
1.8 V input, Circuit 105 (RTS) in ITU-T V.24,
alternatively configurable as SPI1 Clock by uCPU API.
Internal pull-up to V_INT enabled when UART1 RTS input.
See section 1.9.2 / 1.9.3 for functional description.
See section 2.6.2 / 2.6.3 for external circuit design-in.
UART2
RXD2
162 O UART2 data output
1.8 V output, Circuit 104 (RXD) in ITU-T V.24.
See section 1.9.2 for functional description.
See section 2.6.2 for external circuit design-in.
TXD2
161 I UART2 data input
1.8 V input, Circuit 103 (TXD) in ITU-T V.24.
Internal active pull-up to V_INT.
See section 1.9.2 for functional description.
See section 2.6.2 for external circuit design-in.
UART3
RXD3
19 O UART3 data output
1.8 V output, Circuit 104 (RXD) in ITU-T V.24.
See section 1.9.2 for functional description.
See section 2.6.2 for external circuit design-in.
TXD3
18 I UART3 data input
1.8 V input, Circuit 103 (TXD) in ITU-T V.24.
Internal active pull-up to V_INT.
See section 1.9.2 for functional description.
See section 2.6.2 for external circuit design-in.
SPI0
SPI_MOSI
174 O SPI0 Master Output
Slave Input
1.8 V, SPI0 data output.
See section 1.9.3 for functional description.
See section 2.6.3 for external circuit design-in.
SPI_MISO
169 I SPI0 Master Input
Slave Output
1.8 V, SPI0 data input.
See section 1.9.3 for functional description.
See section 2.6.3 for external circuit design-in.
SPI_SCLK
179 O SPI0 Shift Clock
1.8 V, SPI0 clock.
See section 1.9.3 for functional description.
See section 2.6.3 for external circuit design-in.
SPI_CS
173 O SPI0 Chip Select 0
1.8 V, SPI0 chip select 0.
See section 1.9.3 for functional description.
See section 2.6.3 for external circuit design-in.
I2C0
SCL
54 O I2C0 clock
1.8 V open drain.
External pull-up required.
See section 1.9.4 for functional description.
See section 2.6.4 for external circuit design-in.
SDA
55
I/O
I2C0 data
1.8 V open drain.
External pull-up required.
See section 1.9.4 for functional description.
See section 2.6.4 for external circuit design-in.
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Function
Pin Name
Pin No
I/O
Description
Remarks
I2C1
SCL1
54 O I2C1 clock
1.8 V open drain.
External pull-up required.
See section 1.9.4 for functional description.
See section 2.6.4 for external circuit design-in.
SDA1
55
I/O
I2C1 data
1.8 V open drain.
External pull-up required.
See section 1.9.4 for functional description.
See section 2.6.4 for external circuit design-in.
SDIO
SDIO_D0
66
I/O
SDIO serial data [0]
SDIO interface for communication with Wi-Fi / Bluetooth.
See section 1.9.5 for functional description.
See section 2.6.5 for external circuit design-in.
SDIO_D1
68
I/O
SDIO serial data [1]
SDIO interface for communication with Wi-Fi / Bluetooth.
See section 1.9.5 for functional description.
See section 2.6.5 for external circuit design-in.
SDIO_D2
63
I/O
SDIO serial data [2]
SDIO interface for communication with Wi-Fi / Bluetooth.
See section 1.9.5 for functional description.
See section 2.6.5 for external circuit design-in.
SDIO_D3
67
I/O
SDIO serial data [3]
SDIO interface for communication with Wi-Fi / Bluetooth.
See section 1.9.5 for functional description.
See section 2.6.5 for external circuit design-in.
SDIO_CLK
64 O SDIO serial clock
SDIO interface for communication with Wi-Fi / Bluetooth.
See section 1.9.5 for functional description.
See section 2.6.5 for external circuit design-in.
SDIO_CMD
65
I/O
SDIO command
SDIO interface for communication with Wi-Fi / Bluetooth.
See section 1.9.5 for functional description.
See section 2.6.5 for external circuit design-in.
Ethernet
V_ETH
221 O Ethernet Interface
supply output
Ethernet (RGMII / RMII) interface supply output.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_TX_CLK
29
O
Ethernet
Transmission Clock
RGMII: Transmit reference clock (TXC).
RMII: Reference clock (REF_CLK).
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_TX_CTL
33 O Ethernet Transmit
Control
RGMII: Control signal for the transmit data (TXEN on TXC
rising edge; TXEN xor TXER on TXC falling edge).
RMII: Control signal for the transmit data (TX_EN).
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_TXD0
37 O Ethernet Transmit
Data [0]
RGMII: Tx data bit 0 / 4 on TXC rising / falling edges.
RMII: Tx data bit 0 in sync with REF_CLK.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_TXD1
36 O Ethernet Transmit
Data [1]
RGMII: Tx data bit 1 / 5 on TXC rising / falling edges.
RMII: Tx data bit 1 in sync with REF_CLK.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_TXD2
35 O Ethernet Transmit
Data [2]
RGMII: Tx data bit 2 / 6 on TXC rising / falling edges.
RMII: Not used.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_TXD3
34 O Ethernet Transmit
Data [3]
RGMII: Tx data bit 3 / 7 on TXC rising / falling edges.
RMII: Not used.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
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Function
Pin Name
Pin No
I/O
Description
Remarks
ETH_RX_CLK
43 I Ethernet Receive
Clock
RGMII: Receive reference clock (RXC).
RMII: Not used.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_RX_CTL
42 I Ethernet Receive
Control
RGMII: Control signal for receive data (RXDV on RXC rising
edge; RXDV xor RXER on RXC falling edge).
RMII: Control signal for receive data, contains carrier sense
(CRS) and data valid (RX_DV) information.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_RXD0
38 I Ethernet Receive
Data [0]
RGMII: Rx data bit 0 / 4 on RXC rising / falling edges.
RMII: Rx data bit 0 in sync with REF_CLK.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_RXD1
39 I Ethernet Receive
Data [1]
RGMII: Rx data bit 1 / 5 on RXC rising / falling edges.
RMII: Rx data bit 1 in sync with REF_CLK.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_RXD2
40 I Ethernet Receive
Data [2]
RGMII: Rx data bit 2 / 6 on RXC rising / falling edges.
RMII: Not used.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_RXD3
41 I Ethernet Receive
Data [3]
RGMII: Rx data bit 3 / 7 on RXC rising / falling edges.
RMII: Not used.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_INTR
220 I Ethernet Interrupt
Input
Input for the detection of an interrupt event in the PHY.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_MDIO
222
I/O
Ethernet
Management Data
Input Output
Ethernet management data input / output.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
ETH_MDC
223 O Ethernet
Management Data
Clock
Ethernet management data clock output.
See section 1.9.6 for functional description.
See section 2.6.6 for external circuit design-in.
eMMC
V_MMC
210 O Multi-Media Card
Interface supply
output
Embedded Multi-Media / SD Card memory supply.
See section 1.10 for functional description.
See section 2.7 for external circuit design-in.
MMC_D0
214
I/O
Multi-Media Card
Data [0]
Embedded Multi-Media / SD Card memory data [0].
See section 1.10 for functional description.
See section 2.7 for external circuit design-in.
MMC_D1
212
I/O
Multi-Media Card
Data [1]
Embedded Multi-Media / SD Card memory data [1].
See section 1.10 for functional description.
See section 2.7 for external circuit design-in.
MMC_D2
217
I/O
Multi-Media Card
Data [2]
Embedded Multi-Media / SD Card memory data [2].
See section 1.10 for functional description.
See section 2.7 for external circuit design-in.
MMC_D3
213
I/O
Multi-Media Card
Data [3]
Embedded Multi-Media / SD Card memory data [3].
See section 1.10 for functional description.
See section 2.7 for external circuit design-in.
MMC_CMD
215
I/O
Multi-Media Card
Command
Embedded Multi-Media / SD Card memory command.
See section 1.10 for functional description.
See section 2.7 for external circuit design-in.
MMC_CLK
216 O Multi-Media Card
Clock
Embedded Multi-Media / SD Card memory clock.
See section 1.10 for functional description.
See section 2.7 for external circuit design-in.
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Function
Pin Name
Pin No
I/O
Description
Remarks
MMC_RST_N
211 O Multi-Media Card
Reset
Embedded Multi-Media / SD Card memory reset.
See section 1.10 for functional description.
See section 2.7 for external circuit design-in.
MMC_CD_N
218 I Multi-Media Card
Detect
Embedded Multi-Media / SD Card detect.
See section 1.10 for functional description.
See section 2.7 for external circuit design-in.
I2S0
I2S_TXD
51
O
I2S0 transmit data
I2S transmit data output.
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
I2S_RXD
53
I
I2S0 receive data
I2S receive data input.
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
I2S_CLK
52
I/O
I2S0 clock
I2S serial clock.
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
I2S_WA
50
I/O
I2S0 word alignment
I2S word alignment.
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
I2S1
I2S1_TXD
206
O
I2S1 transmit data
I2S transmit data output.
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
I2S1_RXD
207
I
I2S1 receive data
I2S receive data input.
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
I2S1_CLK
208
I/O
I2S1 clock
I2S serial clock.
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
I2S1_WA
205
I/O
I2S1 word alignment
I2S word alignment.
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
Analog
audio
MIC_BIAS
231 O Microphone supply
output
Supply output for external microphones.
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
MIC_GND
230 I Microphone analog
reference
Local ground for the external microphone.
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
MIC1_P
237
I
MIC1 differential
analog audio input (+)
MIC1 differential analog audio signal input (positive).
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
MIC1_N
236
I
MIC1 differential
analog audio input (–)
MIC1 differential analog audio signal input (negative).
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
MIC2_P
234
I
MIC2 differential
analog audio input (+)
MIC2 differential analog audio signal input (positive).
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
MIC2_N
233
I
MIC2 differential
analog audio input (–)
MIC2 differential analog audio signal input (negative).
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
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Function
Pin Name
Pin No
I/O
Description
Remarks
SPK_P
227 O Differential analog
audio output (+)
Differential analog audio signal output (positive).
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
SPK_N
228 O Differential analog
audio output (–)
Differential analog audio signal output (negative).
See sections 1.11 for functional description.
See sections 2.8 for external circuit design-in.
ADC
ADC1
240 I ADC input
See section 1.12 for functional description.
See section 2.9 for external circuit design-in.
ADC2
239 I ADC input
See section 1.12 for functional description.
See section 2.9 for external circuit design-in.
GPIO
GPIO1
21
I/O
GPIO
1.8 V GPIO with alternatively configurable functions.
See section 1.13 for functional description.
See section 2.10 for external circuit design-in.
GPIO2
22
I/O
GPIO
1.8 V GPIO with alternatively configurable functions.
See section 1.13 for functional description.
See section 2.10 for external circuit design-in.
GPIO3
24
I/O
GPIO
1.8 V GPIO with alternatively configurable functions.
Configurable as External Interrupt by uCPU API.
See section 1.13 for functional description.
See section 2.10 for external circuit design-in.
GPIO4
25
I/O
GPIO
1.8 V GPIO with alternatively configurable functions.
Configurable as SPI0 Chip Select 1 by uCPU API.
See sections 1.13, 1.9.3 for functional description.
See sections 2.10, 2.6.3 for external circuit design-in.
GPIO5
60
I/O
GPIO
1.8 V GPIO with alternatively configurable functions.
See section 1.13 for functional description.
See section 2.10 for external circuit design-in.
GPIO6
61
I/O
GPIO
1.8 V GPIO with alternatively configurable functions.
See section 1.13 for functional description.
See section 2.10 for external circuit design-in.
GPIO7
248
I/O
GPIO
1.8 V GPIO with alternatively configurable functions.
See section 1.13 for functional description.
See section 2.10 for external circuit design-in.
GPIO8
247
I/O
GPIO
1.8 V GPIO with alternatively configurable functions.
See section 1.13 for functional description.
See section 2.10 for external circuit design-in.
Reserved
RSVD
6
N/A
Reserved pin
This pin must be connected to ground.
See sections 1.14 and 2.11
Table 4: TOBY-L4 series module pin definition, grouped by function
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General Status
Operating Mode
Definition
Power-down
Not-powered mode
VCC supply not present or below operating range: module is switched off.
Power-off mode
VCC supply within operating range and module is switched off.
Normal Operation
Idle mode
Module processor core runs with 32 kHz reference generated by the internal oscillator.
Active mode
Module processor core runs with 26 MHz reference generated by the internal oscillator.
Connected mode
RF Tx/Rx data connection enabled and processor core runs with 26 MHz reference.
Mode
Description
Transition between operating modes
Not-powered
Module is switched off.
Application interfaces are not accessible.
When VCC supply is removed, the modules enter not-powered mode.
When in not-powered mode, the modules do not switch on by
applying VCC supply, or by using the PWR_ON pin.
When in not-powered mode, the modules go to power-off mode by
applying VCC supply.
Power-off
Module is switched off: normal shutdown by an
appropriate power-off event (see 1.6.2).
Application interfaces are not accessible.
When the modules are switched off by an appropriate power-off event
(see 1.6.2), the modules enter power-off mode from active mode.
When in power-off mode, the modules can be switched on by means
of the PWR_ON pin (see 1.6.1).
When in power-off mode, the modules enter not-powered mode by
removing VCC supply.
Idle
Module is switched on with application
interfaces temporarily disabled or suspended to
reduce the current consumption (see 1.5.1.5)
due to power saving configuration enabled by
AT+UPSV command or uCPU API
The modules automatically switch from the active mode to low power
idle mode whenever possible if power saving is enabled.
The modules wake up from low power idle mode to active mode due
to any necessary network related activity, external wake-up through
the operating interfaces, or wake-up by means of dedicated uCPU API.
Active
Module is switched on with application
interfaces enabled or not suspended: the
module is ready to communicate with an
external device by means of the application
interfaces unless power saving configuration is
enabled by AT+UPSV command or uCPU API.
When the modules are switched on by an appropriate power-on event
(see 1.6.1), the module enter active mode from power-off mode.
If power saving configuration is enabled by the AT+UPSV command or
uCPU API, the module automatically switches from active to idle mode
whenever possible and the module wakes up from idle to active mode
in the events listed above (see idle mode to active mode transition
description above).
When a RF Tx/Rx data or voice connection is initiated or when RF Tx/Rx
is required due to a connection previously initiated, the module
switches from active to connected mode.
Connected
RF Tx/Rx data connection is in progress.
The module is prepared to accept data signals
from an external device unless power saving
configuration is enabled by AT+UPSV command
or uCPU API.
When a data or voice connection is initiated, the module enters
connected mode from active mode.
Connected mode is suspended if Tx/Rx data or voice is not in progress.
In such case, the module automatically switches from connected to
active mode and then, if power saving configuration is enabled by the
AT+UPSV command or uCPU API, the module automatically switches
to idle mode whenever possible. Vice-versa, the module wakes up from
idle to active mode and then connected mode if RF Tx/Rx is necessary.
When a data connection is terminated, the module returns to the
active mode.
1.4 Operating modes
TOBY-L4 series modules have several operating modes. The operating modes are defined in Table 5 and described
in detail in Table 6, providing general guidelines for operation.
Table 5: TOBY-L4 series modules operating modes definition
Table 6: TOBY-L4 series modules operating modes descriptions
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If power saving is enabled
and there is no activity for
a defined time interval
Any wake up event described
in the module operating
modes summary table above
Incoming/outgoing call or
other dedicated device
network communication
No RF Tx/Rx in progress,
Call terminated,
Communication dropped
Remove VCC
Switch ON:
• PWR_ON
Not
powered
Power off
ActiveConnectedIdle
Switch OFF:
• AT+CPWROFF
• uCPU API
• PWR_ON
Apply VCC
Figure 2 describes the transition between the various operating modes.
Figure 2: TOBY-L4 series modules operating modes transitions
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72
VCC
71
VCC
70
VCC
TOBY-L4 series
Power
Management
Unit
Memory
Baseband
Processor
Transceiver
RF PMU
Cellular
Power Amplifiers
1.5 Supply interfaces
1.5.1 Module supply input (VCC)
The modules must be supplied via the three VCC pins that represent the module power supply input.
The VCC pins are internally connected to the RF power amplifier and to the integrated Power Management Unit:
all supply voltages needed by the module are generated from the VCC supply by integrated voltage regulators,
including the Real Time Clock supply, V_INT generic digital interfaces supply, VSIM SIM card supply, V_ETH RGMII
interface supply, V_MMC eMMC interface supply, and any other internal rail.
During operation, the current drawn by the TOBY-L4 series modules through the VCC pins can vary by several
orders of magnitude. This ranges from the pulse of current consumption during GSM transmitting bursts at
maximum power level in connected mode (as described in section 1.5.1.2) to the low current consumption during
low power idle mode with power saving enabled (as described in section 1.5.1.5).
Figure 3 provides a simplified block diagram of the TOBY-L4 series modules’ internal VCC supply routing.
RF performance is guaranteed when VCC PA voltage is
inside the normal operating range limits.
RF performance may be affected when VCC PA voltage is
outside the normal operating range limits, though the
module is still fully functional until the VCC voltage is inside
the extended operating range limits.
VCC voltage during
normal operation
Within VCC extended operating range:
3.00 V min. / 4.50 V max.
VCC voltage must be above the extended operating range
minimum limit to switch-on the module.
The module may switch-off when the VCC voltage drops
below the extended operating range minimum limit.
Operation above VCC extended operating range is not
recommended and may affect device reliability.
VCC average current
Support with adequate margin the highest averaged
VCC current consumption value in connected mode
conditions
The maximum average current consumption can be
greater than the specified value according to the actual
antenna mismatching, temperature and supply voltage.
Sections 1.5.1.2, 1.5.1.3 and 1.5.1.4 describe the current
consumption profiles in 2G, 3G and LTE connected modes.
VCC peak current
Support with margin the highest peak VCC current
consumption value in connected mode conditions
The specified maximum peak of current consumption
occurs during the GSM single transmit slot in 850/900
MHz connected mode, in case of a mismatched antenna.
Supply voltage drop values greater than recommended
during 2G TDMA transmission slots directly affect the RF
compliance with the applicable certification schemes.
Figure 5 describes supply voltage drop during 2G Tx slots.
VCC voltage ripple
during 2G/3G/LTE Tx
Noise in the supply must be minimized
High supply voltage ripple values during LTE/3G/2G RF
transmissions in connected mode directly affect the RF
compliance with applicable certification schemes.
Figure 5 describes supply voltage ripple during RF Tx.
VCC under/over-shoot
at start/end of Tx slots
Absent or at least minimized
Supply voltage under-shoot or over-shoot at the start or
the end of 2G TDMA transmission slots directly affect the
RF compliance with the applicable certification schemes.
Figure 5 describes supply voltage under/over-shoot
1.5.1.1 VCC supply requirements
Table 7 summarizes the requirements for the VCC modules supply. See section 2.2.1 for suggestions on how to
properly design a VCC supply circuit compliant with the requirements listed in Table 7.
The supply circuit affects the RF compliance of the device integrating TOBY-L4 series modules
with applicable required certification schemes as well as antenna circuit design. Compliance is
guaranteed if the requirements summarized in Table 7 are fulfilled.
Table 7: Summary of VCC modules supply requirements
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Time [ms]
RX
slot
unused
slot
unused
slot
TX
slot
unused
slot
unused
slot
MON
slot
unused
slot
RX
slot
unused
slot
unused
slot
TX
slot
unused
slot
unused
slot
MON
slot
unused
slot
GSM frame
4.615 ms
(1 frame = 8 slots)
Current [A]
200 mA
60-120 mA
1900 mA
Peak current depends
on TX power and
actual antenna load
GSM frame
4.615 ms
(1 frame = 8 slots)
60-120 mA
10-40 mA
0.0
1.5
1.0
0.5
2.0
2.5
Time [ms]
undershoot
overshoot
ripple
drop
Voltage [mV]
3.8 V
(typ)
RX
slot
unused
slot
unused
slot
TX
slot
unused
slot
unused
slot
MON
slot
unused
slot
RX
slot
unused
slot
unused
slot
TX
slot
unused
slot
unused
slot
MON
slot
unused
slot
GSM frame
4.615 ms
(1 frame = 8 slots)
GSM frame
4.615 ms
(1 frame = 8 slots)
1.5.1.2 VCC current consumption in 2G connected mode
When a GSM call is established, the VCC module current consumption is determined by the current consumption
profile typical of the GSM transmitting and receiving bursts.
The peak of current consumption during a transmission slot is strictly dependent on the RF transmitted power,
which is regulated by the network (the current base station). The transmitted power in the transmit slot is also the
more relevant factor for determining the average current consumption.
If the module is transmitting in 2G single-slot mode in the 850 or 900 MHz bands, at the maximum RF power level
(approximately 2 W or 33 dBm in the allocated transmit slot/burst) the current consumption can reach an upper
peak for 576.9 µs (width of the transmit slot/burst) with a periodicity of 4.615 ms (width of 1 frame = 8 slots/burst),
so with a 1/8 duty cycle according to GSM TDMA (Time Division Multiple Access).
If the module is transmitting in 2G single-slot mode in the 1800 or 1900 MHz bands, the current consumption
figures are considerably lower than the one in the low bands, due to the 3GPP transmitter output power
specifications.
During a GSM call, current consumption is not so significantly high in receiving or in monitor bursts and is low in
the inactive unused bursts.
Figure 4 shows an example of the module current consumption profile versus time in 2G single-slot mode.
Figure 4: VCC current consumption profile versus time during a 2G single-slot call (1 TX slot, 1 RX slot)
Figure 5 illustrates VCC voltage profile versus time during a 2G single-slot call, according to the relative VCC current
consumption profile illustrated in Figure 4.
Figure 5: VCC voltage profile versus time during a 2G single-slot call (1 TX slot, 1 RX slot)
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Time [ms]
RX
slot
unused
slot
TX
slot
TX
slot
TX
slot
TX
slot
MON
slot
unused
slot
RX
slot
unused
slot
TX
slot
TX
slot
TX
slot
TX
slot
MON
slot
unused
slot
GSM frame
4.615 ms
(1 frame = 8 slots)
Current [A]
200mA
60-130mA
Peak current depends
on TX power and
actual antenna load
GSM frame
4.615 ms
(1 frame = 8 slots)
1600 mA
0.0
1.5
1.0
0.5
2.0
2.5
When a GPRS connection is established, more than one slot can be used to transmit and/or more than one slot
can be used to receive. The transmitted power depends on the network conditions, which set the peak current
consumption, but following the 3GPP specifications, the maximum Tx RF power is reduced if more than one slot
is used to transmit, so the maximum peak of current is not as high as can be the case with a 2G single-slot call.
If the module transmits in GPRS class 12 in the 850 or 900 MHz bands, at the maximum RF power control level,
the current consumption can reach a quite high peak but lower than the one achievable in 2G single-slot mode.
This happens for 2.307 ms (width of the 4 transmit slots/bursts) with a periodicity of 4.615 ms (width of 1 frame
= 8 slots/bursts), so with a 1/2 duty cycle, according to 2G TDMA.
If the module is in GPRS connected mode in the 1800 or 1900 MHz bands, the current consumption figures are
quite less high than the one in the low bands, due to 3GPP transmitter output power specifications.
Figure 6 reports the current consumption profiles in GPRS class 12 connected mode, in the 850 or 900 MHz bands,
with 4 slots used to transmit and 1 slot used to receive.
It must be noted that the actual current consumption of the module in 2G connected mode depends also on the
specific concurrent activities performed by the integrated CPU, beside the actual Tx power and antenna load.
Figure 6: VCC current consumption profile during a 2G GPRS/EDGE multi-slot connection (4 TX slots, 1 RX slot)
For EDGE connections, the VCC current consumption profile is very similar to the GPRS current profile, so the
image shown in Figure 6, representing the current consumption profile in GPRS class 12 connected mode, is valid
for the EDGE class 12 connected mode as well.
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Time
[ms]
3G frame
10 ms
(1 frame = 15 slots)
Current [mA]
Current consumption value
depends on TX power and
actual antenna load
170 mA
1 slot
666 µs
850 mA
0
300
200
100
500
400
600
700
1.5.1.3 VCC current consumption in 3G connected mode
During a 3G connection, the module can transmit and receive continuously due to the Frequency Division Duplex
(FDD) mode of operation with the Wideband Code Division Multiple Access (WCDMA).
The current consumption depends on output RF power, which is always regulated by the network (the current
base station) sending power control commands to the module. These power control commands are logically
divided into a slot of 666 µs, so the rate of power change can reach a maximum rate of 1.5 kHz.
There are no high current peaks as in the 2G connection, since transmission and reception are continuously
enabled due to FDD WCDMA implemented in the 3G that differs from the TDMA implemented in the 2G case.
In the worst case scenario, corresponding to a continuous transmission and reception at maximum output power
(approximately 250 mW or 24 dBm), the average current drawn by the module at the VCC pins is considerable.
At the lowest output RF power (approximately 0.01 µW or –50 dBm), the current drawn by the internal power
amplifier is strongly reduced. The total current drawn by the module at the VCC pins is due to baseband processing
and transceiver activity.
Figure 7 shows an example of the current consumption profile of the module in 3G WCDMA/DC-HSPA+
continuous transmission mode.
It must be noted that the actual current consumption of the module in 3G connected mode depends also on the
specific concurrent activities performed by the integrated CPU, beside the actual Tx power and antenna load.
Figure 7: VCC current consumption profile versus time during a 3G connection (TX and RX continuously enabled)
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Time
[ms]
Current [mA]
Current consumption value
depends on TX power and
actual antenna load
1 Slot
1 Resource Block
(0.5 ms)
1 LTE Radio Frame
(10 ms)
0
300
200
100
500
400
600
700
800
900
1.5.1.4 VCC current consumption in LTE connected mode
During an LTE connection, the module can transmit and receive continuously due to the Frequency Division Duplex
(FDD) mode of operation used in LTE radio access technology.
The current consumption depends on output RF power, which is always regulated by the network (the current
base station) sending power control commands to the module. These power control commands are logically
divided into a slot of 0.5 ms (time length of one Resource Block), thus the rate of power change can reach a
maximum rate of 2 kHz.
The current consumption profile is similar to that in 3G radio access technology. Unlike the 2G connection mode,
which uses the TDMA mode of operation, there are no high current peaks since transmission and reception are
continuously enabled in FDD.
In the worst case scenario, corresponding to a continuous transmission and reception at maximum output power
(approximately 250 mW or 24 dBm), the average current drawn by the module at the VCC pins is considerable.
At the lowest output RF power (approximately 0.1 µW or –40 dBm), the current drawn by the internal power
amplifier is greatly reduced and the total current drawn by the module at the VCC pins is due to baseband
processing and transceiver activity.
Figure 8 shows an example of the module current consumption profile versus time in LTE connected mode.
It must be noted that the actual current consumption of the module in LTE connected mode depends also on the
specific concurrent activities performed by the integrated CPU, beside the actual Tx power and antenna load.
Figure 8: VCC current consumption profile versus time during LTE connection (TX and RX continuously enabled)
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~50 ms
IDLE MODEACTIVE MODEIDLE MODE
Active Mode
Enabled
Idle Mode
Enabled
2G case: 0.44-2.09 s
3G case: 0.61-5.09 s
LTE case: 0.27-2.51 s
IDLE MODE
~50 ms
ACTIVE MODE
Time [s]
Current [mA]
Time [ms]
Current [mA]
RX
Enabled
0
100
0
100
1.5.1.5 VCC current consumption in cyclic idle/active mode (power saving enabled)
The power saving configuration is disabled by default, but it can be enabled using the AT+UPSV command (see
the u-blox AT Commands Manual [2]) or the dedicated uCPU API. When power saving is enabled, the module
automatically enters the low power idle mode whenever possible, reducing current consumption.
During low power idle mode, the module processor runs with 32 kHz reference clock frequency.
When the power saving configuration is enabled and the module is registered or attached to a network , the
module automatically enters the low power idle mode whenever possible, but it must periodically monitor the
paging channel of the current base station (paging block reception), in accordance with the 2G/3G/LTE system
requirements, even if connected mode is not enabled by the application. When the module monitors the paging
channel, it wakes up to the active mode to enable the reception of the paging block. In between, the module
switches to low power idle mode. This is known as discontinuous reception (DRX).
The module processor core is activated during the paging block reception, and automatically switches its reference
clock frequency from 32 kHz to the 26 MHz used in active mode.
The time period between two paging block receptions is defined by the network. This is the paging period
parameter, fixed by the base station through the broadcast channel sent to all users on the same serving cell:
For 2G radio access technology, the paging period can vary from 470.8 ms (DRX = 2, length of 2 x 51 2G
frames = 2 x 51 x 4.615 ms) up to 2118.4 ms (DRX = 9, length of 9 x 51 2G frames = 9 x 51 x 4.615 ms)
For 3G radio access technology, the paging period can vary from 640 ms (DRX = 6, i.e. length of 2
6
3G frames
= 64 x 10 ms) up to 5120 ms (DRX = 9, length of 29 3G frames = 512 x 10 ms).
For LTE radio access technology, the paging period can vary from 320 ms (DRX = 5, i.e. length of 2
5
LTE frames
= 32 x 10 ms) up to 2560 ms (DRX = 8, length of 28 LTE frames = 256 x 10 ms).
Figure 9 illustrates a typical example of the module current consumption profile when power saving is enabled.
The module is registered with the network, automatically enters the low power idle mode and periodically wakes
up to active mode to monitor the paging channel for the paging block reception.
Figure 9: VCC current consumption profile with power saving enabled and module registered with the network: the module is in
low-power idle mode and periodically wakes up to active mode to monitor the paging channel for paging block reception
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ACTIVE MODE
2G case: 0.44-2.09 s
3G case: 0.61-5.09 s
LTE case: 0.32-2.56 s
Paging period
Time [s]
Current [mA]
Time [ms]
Current [mA]
RX
Enabled
0
100
0
100
1.5.1.6 VCC current consumption in fixed active mode (power saving disabled)
When power saving is disabled, the module does not automatically enter the low power idle mode whenever
possible: the module remains in active mode. Power saving configuration is by default disabled. It can also be
disabled using the AT+UPSV command (see the u-blox AT Commands Manual [2]) or the dedicated uCPU API.
The module processor core is activated during idle mode, and the 26 MHz reference clock frequency is used. It
would draw more current during the paging period than that in the power saving mode.
Figure 10 illustrates a typical example of the module current consumption profile when power saving is disabled.
In such a case, the module is registered with the network and while active mode is maintained, the receiver is
periodically activated to monitor the paging channel for paging block reception.
It must be noted that the actual current consumption of the module in active mode depends on the specific
concurrent activities performed by the integrated CPU.
Figure 10: VCC current consumption profile with power saving disabled and module registered with the network: active mode is
always held and the receiver is periodically activated to monitor the paging channel for paging block reception
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Baseband
Processor
70
VCC
71
VCC
72
VCC
5
V_INT
Switching
Step-Down
Power
Management
TOBY-L4 series
Digital I/O
1.5.2 RTC back-up supply (V_BCKP)
When the VCC module supply input voltage is within the valid operating range, the internal Power Management
Unit (PMU) supplies the Real Time Clock (RTC) through the rail available at the V_BCKP pin.
The RTC provides the module time reference (date and time) that is used to set the wake-up interval during the
low power idle mode periods, and is able to make the programmable alarm functions available.
If the VCC module supply input voltage is under the minimum operating limit (e.g. during the not powered mode),
the RTC can be externally supplied through the V_BCKP pin. This lets the time reference (date and time) run until
the V_BCKP voltage is within its valid range, even when the main supply is not provided to the module.
Consider that the module cannot switch on if a valid voltage is not present on VCC even when the RTC is supplied
through V_BCKP (meaning that VCC is mandatory to switch on the module).
The RTC has a very low current consumption, but is highly temperature dependent.
If V_BCKP is left unconnected and the module main supply is not applied to the VCC pins, the RTC is supplied
from a small bypass capacitor mounted inside the module. However, this small capacitor is not able to provide a
long buffering time: within a few milliseconds the voltage on V_BCKP will drop below the valid range. This has
no impact on cellular connectivity, as all the module functionalities do not rely on date and time settings.
1.5.3 Generic digital interfaces supply output (V_INT)
The V_INT output pin of the TOBY-L4 series modules is connected to an internal 1.8 V supply. This supply is
internally generated by a switching step-down regulator integrated in the Power Management Unit and it is
internally used to source the generic digital I/O interfaces of the cellular module, as illustrated in Figure 11. The
output of this regulator is enabled when the module is switched on and it is disabled when the module is switched
off.
Figure 11: TOBY-L4 series generic digital interfaces supply output (V_INT) simplified block diagram
The switching regulator operates in Pulse Width Modulation (PWM) mode for greater efficiency at high output
loads and it automatically switches to Pulse Frequency Modulation (PFM) power save mode for greater efficiency
at low output loads.
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Baseband
Processor
20
PWR_ON
TOBY-L4 series
Power-on
Power
Management
Power-on
35k
1.3 V
1.6 System function interfaces
1.6.1 Module power-on
TOBY-L4 series modules can be switched on in the following way:
Low pulse on the PWR_ON pin, which is normally set high by an internal pull-up, for a valid time period, when
the applied VCC voltage is stable at its nominal value within the valid operating range.
As illustrated in Figure 12, the TOBY-L4 series PWR_ON input is equipped with an internal active pull-up resistor
to an internal 1.3 V supply rail: the PWR_ON input voltage thresholds are different from the other generic digital
interfaces, and the line should be driven by an open drain, by an open collector or by a contact switch, without
an external pull-up resistor.
Detailed electrical characteristics and specifications are described in TOBY-L4 seriesData Sheet [1].
Figure 12: TOBY-L4 series PWR_ON input description
TOBY-L4 series modules do not switch on by applying the VCC supply only: a low pulse must be forced on
the PWR_ON pin when the VCC voltage is stable at its nominal value within the valid operating range.
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VCC
PWR_ON
V_INT
RESET_N
Internal Reset
System State
Digital Pins State
Internal Reset → Operationa l Opera tional
Tristate / Floating
OFF
ON
Internal Reset
Start of interface
configuration
Module interfaces
are configured
The module starts
the switch-on routine
Figure 13 shows the module power-on sequence, describing the following phases:
The VCC module supply is stable at its nominal value within the normal operating range
The PWR_ON input pin is set low for a valid time period, representing the switch-on event.
All the generic digital pins of the modules are tri-stated until the switch-on of their supply source (V_INT): any
external signal connected to the generic digital pins must be tri-stated or set low at least until the activation
of the V_INT supply output to avoid latch-up of circuits and allow a clean boot of the module.
The V_INT generic digital interfaces supply output is enabled by the integrated power management unit.
The RESET_N line rises suddenly to the high logic level due to internal pull-up to V_INT.
The internal reset signal is held low by the integrated power management unit: the baseband processor core
and all the digital pins of the modules are held in reset state.
When the internal reset signal is released, any digital pin is set in the correct sequence from the reset state to
the default operational configured state. The duration of this pins’ configuration phase differs within the
generic digital interfaces and the USB interface due to host / device enumeration timings (see section 1.9.1).
The module is fully ready to operate after all interfaces are configured.
Figure 13: TOBY-L4 series power-on sequence description
The Internal Reset signal is not available on a module pin, but the host application can monitor the V_INTBefore the switch-on of the generic digital interface supply source (V_INT) of the module, no voltage driven Before the TOBY-L4 series module is fully ready to operate, the host application processor should not send The duration of the TOBY-L4 series modules’ switch-on routine can vary depending on the application /
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pin to sense the start of the TOBY-L4 series module power-on sequence.
by an external application should be applied to any generic digital interface of the module.
any AT command over the AT communication interface (USB) of the module.
network settings and any concurrent module activities.
TOBY-L4 series - System Integration Manual
3
4
3
4
1.6.2 Module power-off
TOBY-L4 series can be properly switched off by:
AT+CPWROFF command
uCPU application
(see the u-blox AT Commands Manual [2])
Low pulse on the PWR_ON pin, which is normally set high by an internal pull-up, for a valid time period (see
the TOBY-L4 seriesData Sheet [1]), module normal switch-off: the internal switch-off sequence of the module
starts when the external application releases the PWR_ON line from the low logic level, after that it has been
set low for an appropriate time period.
The methods listed above represent the appropriate normal switch-off events, triggering an appropriate normal
switch-off procedure of the module: the current parameter settings are saved in the module’s non-volatile memory
and a clean network detach is performed.
An abrupt under-voltage shutdown occurs on TOBY-L4 series modules when the VCC module supply is removed.
If this occurs, it is not possible to perform the storing of the current parameter settings in the module’s non-volatile
memory or to perform a clean network detach.
It is highly recommended to avoid an abrupt removal of the VCC supply during TOBY-L4 series modules
normal operations: the switch-off procedure must be started by an appropriate switch-off event (see above),
and then a suitable VCC supply must be held at least until the end of the modules’ internal switch-off
sequence, which occurs when the generic digital interfaces supply output (V_INT) is switched off by the
module.
An abrupt emergency shutdown procedure is triggered on TOBY-L4 series modules when a long enough low pulse
is set at the PWR_ON input pin (see the TOBY-L4 seriesData Sheet [1], module emergency switch-off). In this
case, storage of the current parameter settings in the module’s non-volatile memory and the clean network detach
are not performed.
This abrupt emergency shutdown procedure is intended only for use for emergency, e.g. if the module does not
provide a reply to a specific AT command after a time period longer than the one defined in the u-blox AT Commands Manual [2], or if shutdown via a normal switch-off procedure fails.
An over-temperature shutdown occurs on TOBY-L4 series modules when the temperature measured within the
cellular module reaches a critical range.
Not supported by "00" product version
Not supported by "50" product version
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VCC
PWR_ON
RESET_N
V_INT
Internal Reset
System State
BB Pads State
OFF
Tristate / Floating
ON
Operational ->Tristate
Operational
The module starts
the switch-off routine
VCC
can be removed
Figure 14 describes the TOBY-L4 series modules’ switch-off sequence started by means of the PWR_ON input pin, allowing storage of current parameter settings in the module’s non-volatile memory and a clean network detach,
with the following phases
A low pulse with the appropriate time duration is applied at the PWR_ON input pin, which is normally set
high by an internal pull-up: the module starts the switch-off routine when the PWR_ON signal is released
from the low logical level.
At the end of the switch-off routine, all the digital pins are tri-stated and all the internal voltage regulators are
turned off, including the generic digital interfaces supply (V_INT).
Then, the module remains in power-off mode as long as a switch-on event does not occur (i.e. applying a
suitable low level pulse to the PWR_ON input pin), and enters not-powered mode if the supply is removed
from the VCC pins.
Figure 14: TOBY-L4 series power-off sequence description
The Internal Reset signal is not available on a module pin, but the application can monitor the V_INT pin to
sense the end of the power-off sequence.
The VCC supply can be removed only after the end of the module internal switch-off routine, i.e. only after
that the V_INT voltage level has gone low.
The duration of each phase in the TOBY-L4 series modules’ switch-off routines can largely vary depending
on the application / network settings and the concurrent module activities.
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5
6
Baseband
Processor
23
RESET_N
TOBY-L4 series
5
V_INT
Reset
100k
5
6
1.6.3 Module reset
TOBY-L4 series modules can be properly reset (rebooted) by:
AT+CFUN command
uCPU application
(see the u-blox AT Commands Manual [2])
The methods listed above represent appropriate reset (reboot) events, triggering an appropriate “internal” or
“software” reset of the module: the current parameter settings are saved in the module’s non-volatile memory
and a clean network detach is performed.
An abrupt hardware reset occurs on TOBY-L4 series modules when a low level is applied on the RESET_N input
pin. In this case, the current parameter settings are not saved in the module’s non-volatile memory and a clean
network detach is not performed.
It is highly recommended to avoid an abrupt hardware reset of the module by forcing a low level on the
RESET_N input during modules normal operation: the RESET_N line should be set low only if reset via AT
commands or if the uCPU application fails.
As illustrated in Figure 15, the RESET_N input pins are equipped with an internal pull-up to the V_INT supply.
Figure 15: TOBY-L4 series RESET_N input equivalent circuit description
1.6.4 Module / host configuration selection
Host Select pins are not supported by the "50" product version.
TOBY-L4 series modules include two 1.8 V digital pins (HOST_SELECT0, HOST_SELECT1), which can be
configured for External Interrupt detection or as GPIO by means of the uCPU API.
Not supported by "00" product version
Not supported by "50" product version
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Item
Requirements
Remarks
Impedance
50 nominal characteristic impedance
The impedance of the antenna RF connection must match the 50
impedance of the ANT1 port.
Frequency Range
See the TOBY-L4 seriesData Sheet [1]
The required frequency range of the antenna connected to the ANT1
port depends on the operating bands of the used cellular module and
the used mobile network.
Return Loss
S11 < -10 dB (VSWR < 2:1) recommended
S11 < -6 dB (VSWR < 3:1) acceptable
The Return loss or the S11, as the VSWR, refers to the amount of
reflected power, measuring how well the antenna RF connection
matches the 50 characteristic impedance of the ANT1 port.
The impedance of the antenna termination must match as much as
possible the 50 nominal impedance of the ANT1 port over the
operating frequency range, reducing as much as possible the amount
of reflected power.
Efficiency
> -1.5 dB ( > 70% ) recommended
> -3.0 dB ( > 50% ) acceptable
The radiation efficiency is the ratio of the radiated power to the power
delivered to antenna input: the efficiency is a measure of how well an
antenna receives or transmits.
The radiation efficiency of the antenna connected to the ANT1 port
needs to be enough high over the operating frequency range to
comply with the Over-The-Air (OTA) radiated performance
requirements, as Total Radiated Power (TRP) and the Total Isotropic
Sensitivity (TIS), specified by applicable related certification schemes.
Maximum Gain
According to radiation exposure limits
The power gain of an antenna is the radiation efficiency multiplied by
the directivity: the gain describes how much power is transmitted in
the direction of peak radiation to that of an isotropic source.
The maximum gain of the antenna connected to ANT1 port must not
exceed the herein stated value to comply with regulatory agencies’
radiation exposure limits.
Input Power
> 33 dBm ( > 2 W )
The antenna connected to the ANT1 port must support with adequate
margin the maximum power transmitted by the modules.
1.7 Antenna interfaces
1.7.1 Antenna RF interfaces (ANT1 / ANT2)
TOBY-L4 series modules provide two RF interfaces for connecting the external antennas:
The ANT1 represents the primary RF input/output for transmission and reception of LTE/3G/2G RF signals.
The ANT1 pin has a nominal characteristic impedance of 50 and must be connected to the primary Tx / Rx
antenna through a 50 transmission line to allow clean RF transmission and reception.
The ANT2 represents the secondary RF input for the reception of the RF signals for CA, MIMO and Rx diversity
configurations supported by TOBY-L4 series modules as a required feature for LTE category 6 UEs.
The ANT2 pin has a nominal characteristic impedance of 50 and must be connected to the secondary Rx
antenna through a 50 transmission line to allow for clean RF reception.
1.7.1.1 Antenna RF interfaces requirements
Table 8, Table 9 and Table 10 summarize the requirements for the antennas’ RF interfaces (ANT1 / ANT2). See
section 2.4.1 for suggestions on how to correctly design antennas circuits which are compliant with these
requirements.
The antenna circuits affect the RF compliance of the device integrating TOBY-L4 series modules
with the applicable required certification schemes (for more details see section 4). Compliance is
guaranteed if the antenna RF interfaces (ANT1 / ANT2) requirements summarized in Table 8, Table
9 and Table 10 are fulfilled.
The impedance of the antenna RF connection must match the 50
impedance of the ANT2 port.
Frequency Range
See the TOBY-L4 seriesData Sheet [1]
The required frequency range of the antennas connected to ANT2
port depends on the operating bands of the used cellular module and
the used mobile network.
Return Loss
S11 < -10 dB (VSWR < 2:1) recommended
S11 < -6 dB (VSWR < 3:1) acceptable
The Return loss or the S11, as the VSWR, refers to the amount of
reflected power, measuring how well the antenna RF connection
matches the 50 characteristic impedance of the ANT2 port.
The impedance of the antenna termination must match as much as
possible the 50 nominal impedance of the ANT2 port over the
operating frequency range, reducing as much as possible the amount
of reflected power.
Efficiency
> -1.5 dB ( > 70% ) recommended
> -3.0 dB ( > 50% ) acceptable
The radiation efficiency is the ratio of the radiated power to the power
delivered to antenna input: the efficiency is a measure of how well an
antenna receives or transmits.
The radiation efficiency of the antenna connected to the ANT2 port
needs to be enough high over the operating frequency range to
comply with the Over-The-Air (OTA) radiated performance
requirements, as the TIS, specified by applicable related certification
schemes.
The radiation efficiency imbalance is the ratio of the primary (ANT1)
antenna efficiency to the secondary (ANT2) antenna efficiency: the
efficiency imbalance is a measure of how much better an antenna
receives or transmits compared to the other antenna.
The radiation efficiency of the secondary antenna needs to be roughly
the same as the radiation efficiency of the primary antenna for good
RF performance.
Envelope
Correlation
Coefficient
< 0.4 recommended
< 0.5 acceptable
The Envelope Correlation Coefficient (ECC) between the primary
(ANT1) and the secondary (ANT2) antenna is an indicator of 3D
radiation pattern similarity between the two antennas: low ECC results
from antenna patterns with radiation lobes in different directions.
The ECC between the primary and secondary antennas needs to be
low enough to comply with the radiated performance requirements
specified by related certification schemes.
Isolation
> 15 dB recommended
> 10 dB acceptable
The antenna to antenna isolation is the loss between the primary
(ANT1) and the secondary (ANT2) antenna: high isolation results from
low coupled antennas.
The isolation between primary and secondary antenna needs to be
high for good RF performance.
TOBY-L4 series - System Integration Manual
Table 10: Summary of primary (ANT1) and secondary (ANT2) antennas relationship requirements
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7
8
1.7.2 Antenna detection interface (ANT_DET)
The antenna detection is based on ADC measurement. The ANT_DET pin is an Analog to Digital Converter (ADC)
provided to sense the antenna presence.
The antenna detection function provided by ANT_DET pin is an optional feature that can be implemented if the
application requires it.
The ANT_DET pin generates a DC current and measures the resulting DC voltage, thus determining the resistance
from the antenna connector provided on the application board to GND. So the requirements to achieve antenna
detection functionality are the following:
an RF antenna assembly with a built-in resistor (diagnostic circuit) must be used
an antenna detection circuit must be implemented on the application board
See section 2.4.2 for the antenna detection circuit on the application board and the diagnostic circuit in the
antenna assembly design-in guidelines.
1.8 SIM interfaces
1.8.1 SIM interfaces
TOBY-L4 series modules provide two SIM interfaces for the direct connection of two external SIM cards/chips,
which can be used alternatively (only one SIM at a time can be used for network access):
SIM0 interface (VSIM, SIM_IO, SIM_CLK, SIM_RST pins), which is enabled by default
SIM1 interface (VSIM1, SIM1_IO, SIM1_CLK, SIM1_RST pins), which can be alternatively enabled by
dedicated AT command7 (see the u-blox AT Commands Manual [2]), or by means of the uCPU application8.
Both 1.8 V and 3 V SIM types are supported by the SIM interfaces. Activation and deactivation with an automatic
voltage switch from 1.8 V to 3 V is implemented according to ISO-IEC 7816-3 specifications.
High-speed SIM/ME interface and the PPS procedure for baud-rate selection is implemented according to the
values proposed by the SIM card/chip.
Both the VSIM supply output and the VSIM1 supply output provide internal short circuit protection to limit the
start-up current and protect the SIM from short circuits.
1.8.2 SIM detection interface
The GPIO5 pin of TOBY-L4 series modules can be configured to detect the mechanical / physical presence of an
external SIM card connected to the SIM0 interface. The pin can sense SIM card presence as intended to be properly
connected to the mechanical switch of a SIM card holder as described in section 2.5:
Low logic level at GPIO5 input pin is recognized as SIM card not present
High logic level at GPIO5 input pin is recognized as SIM card present
The SIM card detection function provided by GPIO5 pin is an optional feature that can be implemented / used or
not according to the application requirements: an Unsolicited Result Code (URC) is generated each time that there
is a change of status.
The optional function “SIM card hot insertion/removal” can be additionally configured on the GPIO5 pin, in order
to enable / disable the SIM0 interface upon detection of external SIM card physical insertion / removal.
Not supported by the "00" product version
Not supported by the "50" product version
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9
10
11
12
9
10
11
12
1.9 Data communication interfaces
TOBY-L4 series modules provide the following serial communication interfaces:
USB interface (see section 1.9.1):
USB Super-Speed 3.0 compliant interface
USB High-Speed 2.0 compliant interface, with the module acting as a USB device or host
AT command
Data communication
Ethernet-over-USB virtual channel (CDC-NCM)
FW upgrades
Trace log capture (diagnostic purposes)
Auxiliary channel to tune internal audio parameters using a dedicated external tool
Linux console for uCPU API development and debug
Communication with external processor / device by means of uCPU API
Up to four UART interfaces (see section 1.9.2):
UART0 interface, providing:
Communication with external serial devices by means of uCPU API
Trace log capture (diagnostic purposes)
Ring Indicator functionality
UART1 interface
, providing:
Communication with external serial devices by means of uCPU API
UART2 interface, providing:
Communication with external serial devices by means of uCPU API
UART3 interface, providing:
Linux console for uCPU API development and debug
Up to two SPI interfaces
11
(see section 1.9.3):
SPI0 interface, with the module acting as SPI master, providing:
Communication with external SPI slave devices by means of uCPU API
SPI1 interface
12
, with the module acting as SPI master, providing:
Communication with external SPI slave devices by means of uCPU API
Two DDC I
2
C bus compatible interfaces11 (see section 1.9.4):
I2C0 interface, with the module acting as I
Communication with u-blox GNSS positioning chips / modules
Communication with external I
I2C1 interface, with the module acting as I
Communication with external I
SDIO interface
11
, with the module acting as SDIO host, providing (see section 1.9.5):
Communication with compatible u-blox short range radio modules by means of uCPU API
Communication with external SDIO devices by means of uCPU API
RGMII / RMII interface
Ethernet connection enabled by means of uCPU API, through the external Ethernet PHY
11
, with the module acting as Ethernet MAC, providing (see section 1.9.6):
, with the module acting as a USB device:
11
11
11
11
11
2
C master, providing:
2
C slave devices by means of uCPU API
2
2
C master, providing:
C slave devices by means of uCPU API
11
, providing:
Supported by future FW versions
Not supported by the "00" product version
Not supported by the "50" product version
UART1 and SPI1 interfaces can be used alternatively, in mutually exclusive way, by means of uCPU API
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13
14
13
14
1.9.1 USB interface
The USB Super-Speed 3.0 compliant interface will be supported by future firmware versions. The USB High-Speed 2.0 host role is not supported by the "50" product versions.
TOBY-L4 series modules include a USB Super-Speed 3.0 compliant interface, supporting up to 5 Gbit/s data rate,
and also including a USB High-Speed 2.0 compliant interface, supporting up to 480 Mbit/s data rate.
The USB High-Speed 2.0 compliant interface consists of the following pins:
USB_D+/USB_D–, USB High-Speed differential transceiver data lines as per USB 2.0 specification [3]
VUSB_DET input pin, which senses the VBUS USB supply presence (nominally 5 V at the source) to detect the
host connection and enable the USB 2.0 interface with the module acting as a USB device.
Neither the USB interface, nor the whole module is supplied by the VUSB_DET input pin, which senses the
VBUS USB supply voltage presence and absorbs few microamperes.
USB_ID pin, available for USB ID resistance measurement:
if the USB_ID pin is externally connected to GND, then the module acts as a USB host
if the USB_ID pin is externally left unconnected (floating), then the module acts as a USB device
The USB High-Speed 2.0 compliant interface, with the module acting as a USB device, provides:
AT command
Data communication
Ethernet-over-USB virtual channel
Trace log capture (diagnostic purposes)
Auxiliary channel to tune internal audio parameters using a dedicated external tool
Linux console for uCPU applications development and debug
FW upgrades
The module, acting as a USB device, identifies itself by its VID (Vendor ID) and PID (Product ID) combination,
included in the USB device descriptor according to the USB 2.0 specifications [3].
If the module, acting as a USB device, is connected to the USB host before the module is switched on, or if the
module is reset (rebooted) with the USB connected to the host, the VID and PID are automatically updated during
the boot of the module. First, the VID and PID are the following:
VID = 0x8087
PID = 0x0801
This VID and PID combination identifies a USB profile where no USB function described above is available: the AT
commands must not be sent to the module over the USB profile identified by this VID and PID combination.
Then, after a time period (depending on the host / device enumeration timings), the VID and PID are updated to
the one where the normal operative functions (AT, Data, Ethernet-over-USB, Trace, Linux console) are available.
VID and PID for normal operative functions are the following:
VID = 0x1546
PID = 0x1010
The USB High-Speed 2.0 compliant interface, with the module acting as USB host (OTG), provides:
Communication with external device by means of the uCPU application
Not supported by the "00" product version
Not supported by the "50" product version
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D0D1 D2 D3D4 D5D6D7
Start of 1-Byte
transfer
Start Bit
(Always 0)
Possible Start of
next transfer
Stop Bit
(Always 1)
t
bit
= 1/(Baudrate)
Normal Transfer, 8N1
The USB Super-Speed 3.0 compliant interface as per USB 3.0 specifications [4], with the module acting as a USB
device, consists of the following additional pins:
USB_SSTX+/USB_SSTX–, USB Super-Speed differential transmitter data lines
USB_SSRX+/USB_SSRX–, USB Super-Speed differential receiver data lines
USB drivers are available for Windows operating system platforms. TOBY-L4 series modules are compatible with
standard Linux/Android USB kernel drivers.
1.9.2 UART interfaces
UART interfaces are not supported by the "50" product version, except for trace logging (diagnostic
purposes) and Ring Indicator functionality over the UART0 interface.
1.9.2.1 UART0 interface
The UART0 Universal Asynchronous Receiver/Transmitter serial interface has CMOS compatible signal levels
(0 V for ON / active state and 1.8 V for OFF / idle state), providing:
Communication with external devices by means of the uCPU API, over the following pins:
o RXD module output and TXD module input data lines
o CTS module output and RTS module input hardware flow control lines
Trace logging (diagnostic purpose), over the following pins:
o RXD module output and TXD module input data lines
Ring Indicator functionality, over the following pin:
oRI module output line
The UART0 interface can operate at 9.6 kbit/s, 19.2 kbit/s, 38.4 kbit/s, 57.6 kbit/s, 115.2 kbit/s, 230.4 kbit/s, 460.8
kbit/s, 921.6 kbit/s, 3 Mbit/s, 3.25 Mbit/s and 6.5 Mbit/s baud rates, with 8N1 frame format (illustrated in Figure
16), and with hardware flow control output (CTS line) driven to the OFF state when the module is not prepared
to accept data by the UART0 interface.
Figure 16: Description of UART 8N1 frame format (8 data bits, no parity, 1 stop bit)
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1s
time [s]
151050
RI ON
RI OFF
Call incomes
1s
time [s]
151050
RI ON
RI OFF
Call incomes
SMS arrives
time [s]
0
RI ON
RI OFF
1s
time [s]
0
RI ON
RI OFF
1s
The RI line can notify an incoming call: the RI line is switched from the OFF state to the ON state with a 4:1 duty
cycle and a 5 s period (ON for 1 s, OFF for 4 s, see Figure 17), until the DTE attached to the module sends the ATA
string and the module accepts the incoming data call. The RING string sent by the module (DCE) to the serial port
at constant time intervals is not correlated with the switch of the RI line to the ON state.
Figure 17: RI behavior during an incoming call
The RI output line can notify an SMS arrival. When the SMS arrives, the RI line switches from OFF to ON for 1 s
(see Figure 18), if the feature is enabled by the AT+CNMI command (see the u-blox AT Commands Manual [2]).
Figure 18: RI behavior at SMS arrival
This behavior allows the DTE to stay in power saving mode until the DCE related event requests service.
For SMS arrival, if several events coincidently occur or in quick succession, each event independently triggers the
RI line, although the line will not be deactivated between each event. As a result, the RI line may stay to ON for
more than 1 s, if an incoming call is answered within less than 1 s (with ATA or if auto-answering is set to ATS0=1)
then the RI line is set to OFF earlier, so that:
RI line monitoring cannot be used by the DTE to determine the number of received SMSs. For multiple events (incoming call plus SMS received), the RI line cannot be used to discriminate the two
events, but the DTE must rely on subsequent URCs and interrogate the DCE with the suitable commands.
The RI line can additionally notify URCs and/or incoming data, if the feature is enabled by the specific AT+URING
command (for more details, see the u-blox AT Commands Manual [2]): the RI line is asserted when one of the
configured events occur and it remains asserted for 1 s unless another configured event will happen, with the
same behavior illustrated in Figure 18.
The DTR, DSR, DCD and RI pins can be alternatively configured for External Interrupt detection or as GPIO by
means of the uCPU API. The RI pin can be alternatively configured as GPIO by an AT command.
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1.9.2.2 UART1 interface
The UART1 Universal Asynchronous Receiver/Transmitter serial interface, with CMOS compatible signal levels (0 V
for ON / active state and 1.8 V for OFF / idle state), can operate as a
serial interface for communication with external devices by means of the uCPU API, with the following pins:
o RXD1 module output and TXD1 module input data lines
o CTS1 module output and RTS1 module input hardware flow control lines
The UART1 interface can operate at 9.6 kbit/s, 19.2 kbit/s, 38.4 kbit/s, 57.6 kbit/s, 115.2 kbit/s, 230.4 kbit/s, 460.8
kbit/s, 921.6 kbit/s, 3 Mbit/s, 3.25 Mbit/s and 6.5 Mbit/s baud rates, with 8N1 frame format (illustrated in Figure
16), and with hardware flow control output (CTS1 line) driven to the OFF state when the module is not prepared
to accept data by the UART1 interface.
The UART1 interface can be alternatively, in mutually exclusive way, configured as SPI1 interface by means of the
uCPU API, for communication with external devices with the following pins:
o RXD1 pin, alternatively configured as SPI1 Master Output Slave Input (module output)
o TXD1 pin, alternatively configured as SPI1 Master Input Slave Output (module input)
o CTS1 pin, alternatively configured as SPI1 Chip Select (module output)
o RTS1 pin, alternatively configured as SPI1 Clock (module output)
1.9.2.3 UART2 interface
The UART2 Universal Asynchronous Receiver/Transmitter serial interface, with CMOS compatible signal levels (0 V
for ON / active state and 1.8 V for OFF / idle state), can operate as a
serial interface for communication with external devices by means of the uCPU API, with the following pins:
oRXD2 module output and TXD2 module input data lines
The UART2 interface can operate at 9.6 kbit/s, 19.2 kbit/s, 38.4 kbit/s, 57.6 kbit/s, 115.2 kbit/s, 230.4 kbit/s, 460.8
kbit/s, 921.6 kbit/s, 3 Mbit/s, 3.25 Mbit/s and 6.5 Mbit/s baud rates, with 8N1 frame format (illustrated in Figure
16).
1.9.2.4 UART3 interface
The UART3 Universal Asynchronous Receiver/Transmitter serial interface, with CMOS compatible signal levels (0 V
for ON / active state and 1.8 V for OFF / idle state), can operate as
Linux console for uCPU API development and debug, with the following pins:
oRXD3 module output and TXD3 module input data lines
The UART3 interface can operate at 9.6 kbit/s, 19.2 kbit/s, 38.4 kbit/s, 57.6 kbit/s, 115.2 kbit/s, 230.4 kbit/s, 460.8
kbit/s, 921.6 kbit/s, 3 Mbit/s, 3.25 Mbit/s and 6.5 Mbit/s baud rates, with 8N1 frame format (illustrated in Figure
16).
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1.9.3 SPI interfaces
SPI interfaces are not supported by the "50" product version.
1.9.3.1 SPI0 interface
The SPI0 1.8 V Serial Peripheral Interface supports communication with an external SPI slave devices, with the
module acting as SPI master, by means of the uCPU API, with the following pins:
The SPI0 Serial Clock signal can be configured to different operating frequencies: 26 MHz (maximum frequency),
and 26 / n MHz, where n is 2, 3, 4, etc.
1.9.3.2 SPI1 interface
The SPI1 1.8 V Serial Peripheral Interface supports communication with an external SPI slave devices, with the
module acting as SPI master, by means of the uCPU API, with the following UART1 pins configured as alternative
functions, in a mutually exclusive way:
RXD1 pin, alternatively configured as SPI1 Master OutputSlave Input (module output)
TXD1 pin, alternatively configured as SPI1 Master Input Slave Output (module input)
RTS1 pin, alternatively configured as SPI1 Serial Clock (module output)
CTS1 pin, alternatively configured as SPI1 Chip Select (module output)
The SPI1 Serial Clock signal can be configured at various operating frequencies: 26 MHz (maximum frequency),
and 26 / n MHz, where n is 2, 3, 4, etc.
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1.9.4 DDC (I
DDC (I
2
C) interfaces
2
C) interfaces are not supported by the "50" product version.
1.9.4.1 I2C0 interface
The SDA and SCL pins represent the I2C0 1.8 V I2C bus compatible Display Data Channel (DDC) interface, with
the module acting as I2C master, available for
communication with u-blox GNSS chips / modules
communication with other external I
2
C devices by means of the uCPU API
The I2C0 interface pins of the module are open drain outputs conforming to the I2C bus specifications [6],
supporting up to 100 kbit/s data rate in Standard mode, and up to 400 kbit/s data rate in Fast mode. External
pull-up resistors to suitable 1.8 V supply (e.g. V_INT) are required for operations.
u-blox has implemented special features to ease the design effort required for the integration of a u-blox cellular
module with a u-blox GNSS receiver.
Combining a u-blox cellular module with a u-blox GNSS receiver allows designers to have full access to the
positioning receiver directly via the cellular module: it relays control messages to the GNSS receiver via a dedicated
DDC (I2C) interface. An interface connected to the positioning receiver is not necessary: the cellular module allows
full control of the GNSS receiver.
The modules provide embedded GNSS aiding that is a set of specific features developed by u-blox to improve the
cellular / GNSS system power consumption and the GNSS performance, decreasing the Time-To-First-Fix (TTFF),
thus allowing to calculate the position in a shorter time with higher accuracy.
1.9.4.2 I2C1 interface
The SDA and SCL pins represent the I2C1 I2C bus compatible Display Data Channel (DDC) interface, with the
module acting as the I2C master, available for
communication with other external I
2
C devices by means of uCPU API
The I2C1 interface pins of the module are open drain outputs conforming to the I2C bus specifications [6],
supporting up to 100 kbit/s data rate in Standard mode, and up to 400 kbit/s data rate in Fast mode. External
pull-up resistors to a suitable 1.8 V supply (e.g. V_INT) are required for operations.
1.9.5 SDIO interface
SDIO interface is not supported by the "50" product version.
TOBY-L4 series modules include a 4-bit Secure Digital Input Output interface (SDIO_D0, SDIO_D1, SDIO_D2,
SDIO_D3, SDIO_CLK, SDIO_CMD), where the module acts as an SDIO host controller designed to
communicate with compatible u-blox short range radio communication modules by means of the uCPU API
communicate with external SDIO devices by means of the uCPU API
The SDIO interface supports up to 832 Mbit/s data rate with SD 3.0 SDR104 mode at 208 MHz clock frequency.
Combining a u-blox cellular module with a u-blox short range communication module gives designers full access
to the Wi-Fi module directly via the cellular module, so that a second interface connected to the Wi-Fi module is
not necessary. The cellular module allows a full control of the Wi-Fi module, because Wi-Fi control messages are
relayed to the Wi-Fi module via the dedicated SDIO interface.
u-blox has implemented special features in the cellular modules to ease the design effort for the integration of a
u-blox cellular module with a u-blox short range Wi-Fi module to provide Router functionality.
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1.9.6 RGMII interface
RGMII interface is not supported by the "50" product version.
TOBY-L4 series modules include an Ethernet Media Access Control (MAC) block supporting up to 1 Gbit/s data
rate via a Reduced Gigabit Media-Independent Interface compliant with the RGMII Version 1.3 specification [7]
and the RMII Revision 1.2 specification [8].
The module represents an Ethernet MAC controller, which can be connected to an external Ethernet physical
transceiver (PHY) chip for communication with a remote processor over Ethernet.
The following signals are provided for communication and management of an external Ethernet PHY:
ETH_TX_CTL RGMII Transmit Control output, driven on both edges of the Transmit clock (TXC)
RMII Transmit Enable (TXEN) output, synchronous with Reference Clock (REF_CLK)
ETH_TXD0 RGMII / RMII Transmit Data [0], from MAC to PHY (module output)
ETH_TXD1 RGMII / RMII Transmit Data [1], from MAC to PHY (module output)
ETH_TXD2 RGMII Transmit Data [2], from MAC to PHY (module output)
ETH_TXD3 RGMII Transmit Data [3], from MAC to PHY (module output)
ETH_RX_CLK RGMII Receive reference Clock (RXC) input
ETH_RX_CTL RGMII Receive Control input, sampled on both edges of the Receive clock (RXC)
RMII Carrier Sense (CRS) / Receive Data Valid (RX_DV) input
ETH_RXD0 RGMII / RMII Receive Data [0], from PHY to MAC (module input)
ETH_RXD1 RGMII / RMII Receive Data [1], from PHY to MAC (module input)
ETH_RXD2 RGMII Receive Data [2], from PHY to MAC (module input)
ETH_RXD3 RGMII Receive Data [3], from PHY to MAC (module input)
ETH_INTR Ethernet Interrupt Input, from PHY to MAC (module input)
When this signal is high, it indicates an interrupt event in the PHY
ETH_MDIO Management Data Input Output, bidirectional signal (module input/output)
ETH_MDC Management Data Clock, from MAC to PHY (module output)
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1.10 eMMC interface
The eMMC interface is not supported by the "50" product version.
TOBY-L4 series modules include a 4-bit embedded Multi-Media Card interface compliant with the JESD84-B451
Embedded Multimedia Card (eMMC) Electrical Standard 4.51 [9].
The following signals are provided for connection and management of an external eMMC / SD memory by means
of the uCPU API:
V_MMC Interface supply output (module output)
MMC_D0 Multi-Media Card Data [0], bidirectional signal (module input/output)
MMC_D1 Multi-Media Card Data [1], bidirectional signal (module input/output)
MMC_D2 Multi-Media Card Data [2], bidirectional signal (module input/output)
MMC_D3 Multi-Media Card Data [3], bidirectional signal (module input/output)
MMC_CMD Multi-Media Card Command, bidirectional signal (module input/output)
MMC_CLK Multi-Media Card Clock (module output)
MMC_RST_N Multi-Media Card Reset (module output)
MMC_CD_N Multi-Media Card Detect (module input)
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15
15
1.11 Audio interfaces
1.11.1 Analog audio interfaces
TOBY-L4 series modules provide the following analog audio interfaces:
Analog audio inputs (analog audio uplink path)
First differential analog audio input (MIC1_P, MIC1_N), which can be connected to the output of an
external analog audio device, or an external microphone for voice call or eCall purposes.
The MIC1_P / MIC1_N pins are internally directly connected to a differential input (positive/negative) of
the Audio Front-End, consisting of a Low Noise Amplifier integrated in a dedicated IC, without any
internal series capacitor for DC blocking. The LNA is internally followed by an integrated sigma-delta
ADC connecting the analog Audio Front-End to the digital audio processing system.
Second differential analog audio input (MIC2_P, MIC2_N), which can be connected to the output of an
external analog audio device, or an external microphone for voice call or eCall purposes.
The MIC2_P / MIC2_N pins are internally directly connected to a differential input (positive/negative) of
the Audio Front-End, consisting of a Low Noise Amplifier integrated in a dedicated IC, without any
internal series capacitor for DC blocking. The LNA is internally followed by an integrated sigma-delta
ADC connecting the analog Audio Front-End to the digital audio processing system.
Supply output for external microphones (MIC_BIAS), which can provide the bias / supply for external
microphones by means of a simple circuit implemented on the application board.
The MIC_BIAS pin is internally connected to the output of a low noise LDO linear regulator integrated
in a dedicated IC, with appropriate internal bypass capacitor provided to guarantee stable operation of
the linear regulator.
Local ground for the external microphone (MIC_GND)
The MIC_GND pin is internally connected to ground as a sense line, representing a clean ground
reference for the analog audio input.
Analog audio output (analog audio downlink path):
Differential analog audio output (SPK_P, SPK_N), which can be connected to the input of an external
analog audio device, or an external speaker.
The SPK_P / SPK_N pins are internally directly connected to a differential output (positive/negative) of
the Audio Front-End, consisting of a low power audio amplifier integrated in a dedicated IC, without
any internal series capacitor for DC blocking. The low power audio amplifier is internally preceded by an
integrated DAC connecting the analog Audio Front-End to the digital audio processing system.
:
The first differential analog audio input (MIC1_P, MIC1_N) and the second differential analog audio input (MIC2_P, MIC2_N) interfaces can
be used alternatively, in mutually exclusive way.
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1.11.2 Digital audio interface
TOBY-L4 series modules include two 4-wire I2S digital audio interfaces:
I2S0 digital audio interface, consisting of the following pins:
I2S_TXD data output
I2S_RXD data input
I2S_CLK bit clock input/output
I2S_WA world alignment / synchronization signal input/output
I2S1 digital audio interface consisting of the following pins:
I2S1_TXD data output
I2S1_RXD data input
I2S1_CLK bit clock input/output
I2S1_WA world alignment / synchronization signal input/output
The second digital audio interface (I2S1) will be supported by future firmware versions.
Both I2S0 and I2S1 digital audio interfaces are suitable to transfer digital audio data with an external compatible
digital audio device, as an audio codec or as an audio digital signal processor.
The I2S interfaces can be alternatively set in different modes:
PCM mode (short synchronization signal): I
synchronization, and then is set low for 16 clock cycles according to the 17 or 18 clock cycles frame length.
Normal I
2
S mode (long synchronization signal): I2S word alignment is set high / low with a 50% duty cycle
(high for 16 clock cycles / low for 16 clock cycles, according to the 32 clock cycles frame length).
The I2S interface can be alternatively set in 2 different roles:
Master mode
Slave mode
The sample rate of transmitted/received words, which corresponds to the I2S word alignment / synchronization
signal frequency (<I2S_sample_rate>), can be alternatively set to:
The modules support I2S transmit and I2S receive data 16-bit words long, linear. Data is transmitted and read in 2’s
complement notation. The MSB is transmitted and read first.
I2S clock signal frequency depends on the frame length, the sample rate and the selected mode of operation:
17 x <I2S_sample_rate> or 18 x <I2S_sample_rate> in PCM mode (short synchronization signal)
16 x 2 x <I2S_sample_rate> in Normal I2S mode (long synchronization signal)
2
S word alignment signal is set high for 1 or 2 clock cycles for the
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Function
Description
Configurable GPIOs
External Interrupt
External Interrupt detection (module input)
GPIO3, HOST_SELECT0, HOST_SELECT1, DTR,
DSR, DCD, RI
SPI Chip Select
SPI0 Chip Select 1 (module output)
GPIO4
GNSS supply enable
Enable/disable the supply of u-blox GNSS receiver connected to the
cellular module over the I2C0 interface
GPIO2
GNSS data ready
Sense when u-blox GNSS receiver connected to the module is ready
for sending data over the I2C0 interface
GPIO3
GNSS RTC sharing
RTC synchronization signal to the u-blox GNSS receiver connected
to the cellular module over the I2C0 interface
GPIO4
SIM card detection
External SIM card physical presence detection
GPIO5
SIM card hot
insertion/removal
Enable / disable SIM interface upon detection of external SIM card
physical insertion / removal
GPIO5
Wi-Fi enable
Switch-on/off the external u-blox Wi-Fi module connected to the
cellular module over the SDIO interface
GPIO1
Wake-up
Wake-up the module from Suspend to RAM state
GPIO3
Core dump
Indicates core dump sent over Ethernet RGMII / RMII interface
The ADC pins are not supported by the "50" product version.
TOBY-L4 series modules include Analog to Digital Converter inputs (ADC1, ADC2), which can be handled by
means of the dedicated uCPU API.
1.13 General Purpose Input/Output
TOBY-L4 series modules "00" product versions include 14 pins (GPIO1, GPIO2, GPIO3, GPIO4, GPIO5, GPIO6,
GPIO7, GPIO8, HOST_SELECT0, HOST_SELECT1, DTR, DSR, DCD, and RI) that can be configured by the uCPU
application as general purpose input/output or to provide custom functions as summarized in Table 11.
UART0 Ring Indicator functionality (Circuit 125 in ITU-T V.24)
RI
SIM card detection
External SIM card physical presence detection
GPIO5
SIM card hot
insertion/removal
Enable / disable SIM interface upon detection of external SIM card
physical insertion / removal
GPIO5
Input
Input to sense high or low digital level
GPIO1, GPIO2, GPIO3, GPIO4, GPIO5, GPIO6,
GPIO7, GPIO8, RI
Output
Output to set the high or the low digital level
GPIO1, GPIO2, GPIO3, GPIO4, GPIO5, GPIO6,
GPIO7, GPIO8, RI
Pin disabled
Output tri-stated with an internal active pull-down enabled
GPIO1, GPIO2, GPIO3, GPIO4, GPIO5, GPIO6,
GPIO7, GPIO8, RI
TOBY-L4 series modules "50" product versions include 9 pins (GPIO1, GPIO2, GPIO3, GPIO4, GPIO5, GPIO6,
GPIO7, GPIO8, and RI) that can be configured by AT commands as general purpose input/output or to provide
custom functions as summarized in Table 12.
TOBY-L4 series modules have pins reserved for future use, marked as RSVD: they can all be left unconnected on
the application board, except
the RSVD pin number 6 that must be externally connected to ground
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2 Design-in
2.1 Overview
For optimal integration of the modules in the application PCB, follow the design guidelines stated in this section.
Every application circuit must be properly designed to guarantee the correct functionality of the relative interface,
but a number of points require greater attention during the design of the application device.
The following list provides a rank of importance in the application design, starting with the most significant:
1. Module antenna connection:
Antenna circuit directly affects the RF compliance of the device integrating a TOBY-L4 series module with
applicable certification schemes. Very carefully follow the suggestions provided in section 2.4 for the schematic
and layout design.
2. Module supply:
The supply circuit affects the RF compliance of the device integrating a TOBY-L4 series module with applicable
required certification schemes as well as the antenna circuit design. Very carefully follow the suggestions
provided in section 2.2.1 for the schematic and layout design.
3. USB interface:
Accurate design is required to guarantee USB functionality. Carefully follow the suggestions provided in
section 2.6.1 for the schematic and layout design.
4. SIM interface:
Accurate design is required to guarantee SIM card functionality reducing the risk of RF coupling. Carefully
follow the suggestions provided in section 2.5 for the schematic and layout design.
5. System functions:
Accurate design is required to guarantee well defined voltage level during operation at Reset and Power-on
inputs. Carefully follow the suggestions provided in section 2.3 for the schematic and layout design.
6. Analog audio:
Accurate design is required to obtain clear and high quality audio reducing the risk of noise from audio lines
due to both supply burst noise coupling and RF detection. Carefully follow the suggestions provided in section
2.8.1 for the schematic and layout design.
7. SDIO, RGMII, eMMC interfaces:
Accurate design is required to guarantee SDIO, RGMII, eMMC interfaces functionality. Carefully follow the
suggestions provided in section 2.6.5, 2.6.6, 2.7 for the schematic and layout design.
8. ADC interfaces:
Accurate design is required to guarantee ADC interfaces functionality. Carefully follow the suggestions
provided in section 2.9 for the schematic and layout design.
9. Other digital interfaces: (UART, SPI, I
Accurate design is required to guarantee correct functionality and reduce the risk of digital data frequency
harmonics coupling. Follow the suggestions provided in sections 2.6.1, 2.6.3, 2.6.4, 2.8.2, 2.3.3, 2.10, 2.11.
10. Other supplies: V_BCKP RTC supply and V_INT generic digital interfaces supply.
Correct design is required to guarantee functionality. Follow the suggestions provided in 2.2.2 and 2.2.3.
It is recommended to also follow the specific design guidelines provided by each manufacturer of any
external part selected for the application board that integrates the u-blox cellular modules.
2
C, I2S, Host Select, GPIOs, and Reserved pins).
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TOBY-L4 series - System Integration Manual
Main Supply
Available?
Battery
Li-Ion 3.7 V
Linear LDO
Regulator
Main Supply
Voltage > 5V?
Switching Step-Down
Regulator
No, portable device
No, less than 5 V
Yes, greater than 5 V
Yes, always available
2.2 Supply interfaces
2.2.1 Module supply (VCC)
2.2.1.1 General guidelines for VCC supply circuit selection and design
All the available VCC pins must be connected to the external supply minimizing the power loss due to series
resistance.
GND pins are internally connected. Application design shall connect all the available pads to solid ground on the
application board, since a good (low impedance) connection to external ground can minimize power loss and
improve RF and thermal performance.
TOBY-L4 series modules must be sourced through the VCC pins with a suitable DC power supply that should meet
the following prerequisites to comply with the modules’VCC requirements summarized in Table 7.
The suitable DC power supply can be selected according to the application requirements (see Figure 19) between
the different possible supply sources types, which most common ones are the following:
The switching step-down regulator is the typical choice when the available primary supply source has a nominal
voltage much higher (e.g. greater than 5 V) than the operating supply voltage of TOBY-L4 series. The use of
switching step-down provides the best power efficiency for the overall application and minimizes current drawn
from the main supply source. See sections 2.2.1.2, 2.2.1.6, 2.2.1.10, 2.2.1.11 for specific design-in.
The use of an LDO linear regulator becomes convenient for a primary supply with a relatively low voltage (e.g. less
or equal than 5 V). In this case the typical 90% efficiency of the switching regulator diminishes the benefit of
voltage step-down and no true advantage is gained in input current savings. On the opposite side, linear regulators
are not recommended for high voltage step-down as they dissipate a considerable amount of energy in thermal
power. See sections 2.2.1.3, 2.2.1.6, 2.2.1.10, 2.2.1.11 for specific design-in.
If TOBY-L4 series modules are deployed in a mobile unit where no permanent primary supply source is available,
then a battery will be required to provide VCC. A standard 3-cell Li-Ion or Li-Pol battery pack directly connected to
VCC is the usual choice for battery-powered devices. During charging, batteries with Ni-MH chemistry typically
reach a maximum voltage that is above the maximum rating for VCC, and should therefore be avoided. See
sections 2.2.1.4, 2.2.1.6, 2.2.1.10, 2.2.1.11 for specific design-in.
Keep in mind that the use of rechargeable batteries requires the implementation of a suitable charger circuit which
is not included in the modules. The charger circuit must be designed to prevent over-voltage on VCC pins, and it
should be selected according to the application requirements: a DC/DC switching charger is the typical choice
when the charging source has an high nominal voltage (e.g. ~12 V), whereas a linear charger is the typical choice
when the charging source has a relatively low nominal voltage (~5 V). If both a permanent primary supply /
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TOBY-L4 series - System Integration Manual
charging source (e.g. ~12 V) and a rechargeable back-up battery (e.g. 3.7 V Li-Pol) are available at the same time
as possible supply source, then a suitable charger / regulator with integrated power path management function
can be selected to supply the module while simultaneously and independently charging the battery. See sections
2.2.1.7, 2.2.1.8, and 2.2.1.4, 2.2.1.6, 2.2.1.10, 2.2.1.11 for specific design-in.
An appropriate primary (not rechargeable) battery can be selected taking into account the maximum current
specified in the TOBY-L4 series Data Sheet [1] during connected mode, considering that primary cells might have
weak power capability. See sections 2.2.1.5, and 2.2.1.6, 2.2.1.10, 2.2.1.11 for specific design-in.
The usage of more than one DC supply at the same time should be evaluated carefully: depending on the supply
source characteristics, different DC supply systems can result as mutually exclusive.
The usage of a regulator or a battery not able to support the highest peak of VCC current consumption specified
in the TOBY-L4 series Data Sheet [1] is generally not recommended. However, if the selected regulator or battery
is not able to support the highest peak current of the module, it must be able to support with adequate margin
at least the highest averaged current consumption value specified in the TOBY-L4 series Data Sheet [1]. The
additional energy required by the module during a 2G Tx slot can be provided by an appropriate bypass tank
capacitor or a super-capacitor with very large capacitance and very low ESR placed close to the module VCC pins.
Depending on the actual capability of the selected regulator or battery, the required capacitance can be
considerably larger than 1 mF and the required ESR can be in the range of few tens of m. Carefully evaluate the
super-capacitor characteristics since aging and temperature may affect the actual characteristics.
The following sections highlight some design aspects for each of the supplies listed above providing application
circuit design-in compliant with the module VCC requirements summarized in Table 7.
2.2.1.2 Guidelines for VCC supply circuit design using a switching regulator
The use of a switching regulator is suggested when the difference from the available supply rail source to the VCC
value is high, since switching regulators provide good efficiency transforming a 12 V or greater voltage supply to
the typical 3.8 V value of the VCC supply.
The characteristics of the switching regulator connected to VCC pins should meet the following prerequisites to
comply with the module VCC requirements summarized in Table 7:
Power capability: the switching regulator with its output circuit must be capable of providing a voltage value
to the VCC pins within the specified operating range and must be capable of delivering to VCC pins the
maximum peak / pulse current consumption during Tx burst at maximum Tx power specified in the TOBY-L4 seriesData Sheet [1].
Low output ripple: the switching regulator together with its output circuit must be capable of providing a
clean (low noise) VCC voltage profile.
High switching frequency: for best performance and for smaller applications it is recommended to select a
switching frequency ≥ 600 kHz (since L-C output filter is typically smaller for high switching frequency). The
use of a switching regulator with a variable switching frequency or with a switching frequency lower than 600
kHz must be evaluated carefully since this can produce noise in the VCC voltage profile and therefore
negatively impact LTE/3G/2G modulation spectrum performance. An additional L-C low-pass filter between
the switching regulator output to VCC supply pins can mitigate the ripple at the input of the module, but adds
extra voltage drop due to resistive losses on series inductors.
PWM mode operation: it is preferable to select regulators with Pulse Width Modulation (PWM) mode. While
in connected mode, the Pulse Frequency Modulation (PFM) mode and PFM/PWM modes transitions must be
avoided to reduce noise on VCC voltage profile. Switching regulators can be used that are able to switch
between low ripple PWM mode and high ripple PFM mode, provided that the mode transition occurs when
the module changes status from the idle/active modes to connected mode. It is permissible to use a regulator
that switches from the PWM mode to the burst or PFM mode at an appropriate current threshold.
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TOBY-L4 series - System Integration Manual
12V
C5
R3
C4
R2
C2C1
R1
VIN
RUN
VC
RT
PG
SYNC
BD
BOOST
SW
FB
GND
6
7
10
9
5
C6
1
2
3
8
11
4
C7C8
D1
R4
R5
L1
C3
U1
TOBY-L4 series
71
VCC
72
VCC
70
VCC
GND
Reference
Description
Part Number - Manufacturer
C1
10 µF Capacitor Ceramic X7R 5750 15% 50 V
C5750X7R1H106MB - TDK
C2
10 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C103KA01 - Murata
C3
680 pF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71H681KA01 - Murata
C4
22 pF Capacitor Ceramic C0G 0402 5% 25 V
GRM1555C1H220JZ01 - Murata
C5
10 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C103KA01 - Murata
C6
470 nF Capacitor Ceramic X7R 0603 10% 25 V
GRM188R71E474KA12 - Murata
C7
22 µF Capacitor Ceramic X5R 1210 10% 25 V
GRM32ER61E226KE15 - Murata
C8
330 µF Capacitor Tantalum D_SIZE 6.3 V 45 m
T520D337M006ATE045 - KEMET
D1
Schottky Diode 40 V 3 A
MBRA340T3G - ON Semiconductor
L1
10 µH Inductor 744066100 30% 3.6 A
744066100 - Wurth Electronics
R1
470 k Resistor 0402 5% 0.1 W
2322-705-87474-L - Yageo
R2
15 k Resistor 0402 5% 0.1 W
2322-705-87153-L - Yageo
R3
22 k Resistor 0402 5% 0.1 W
2322-705-87223-L - Yageo
R4
390 k Resistor 0402 1% 0.063 W
RC0402FR-07390KL - Yageo
R5
100 k Resistor 0402 5% 0.1 W
2322-705-70104-L - Yageo
U1
Step-Down Regulator MSOP10 3.5 A 2.4 MHz
LT3972IMSE#PBF - Linear Technology
Figure 20 and Table 13 show an example of a high reliability power supply circuit, where the module VCC input
is supplied by a step-down switching regulator capable of delivering maximum current with low output ripple and
with fixed switching frequency in PWM mode operation greater than 1 MHz.
Figure 20: Example of high reliability VCC supply application circuit using a step-down regulator
Table 13: Components for high reliability VCC supply application circuit using a step-down regulator
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TOBY-L4 series - System Integration Manual
TOBY-L4 series
12V
R5
C6C1
VCC
INH
FSW
SYNC
OUT
GND
2
6
3
1
7
8
C3
C2
D1
R1
R2
L1
U1
GND
FB
COMP
5
4
R3
C4
R4
C5
71
VCC
72
VCC
70
VCC
Reference
Description
Part Number - Manufacturer
C1
22 µF Capacitor Ceramic X5R 1210 10% 25 V
GRM32ER61E226KE15 – Murata
C2
100 µF Capacitor Tantalum B_SIZE 20% 6.3V 15m
T520B107M006ATE015 – Kemet
C3
5.6 nF Capacitor Ceramic X7R 0402 10% 50 V
GRM155R71H562KA88 – Murata
C4
6.8 nF Capacitor Ceramic X7R 0402 10% 50 V
GRM155R71H682KA88 – Murata
C5
56 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H560JA01 – Murata
C6
220 nF Capacitor Ceramic X7R 0603 10% 25 V
GRM188R71E224KA88 – Murata
D1
Schottky Diode 25V 2 A
STPS2L25 – STMicroelectronics
L1
5.2 µH Inductor 30% 5.28A 22 m
MSS1038-522NL – Coilcraft
R1
4.7 k Resistor 0402 1% 0.063 W
RC0402FR-074K7L – Yageo
R2
910 Resistor 0402 1% 0.063 W
RC0402FR-07910RL – Yageo
R3
82 Resistor 0402 5% 0.063 W
RC0402JR-0782RL – Yageo
R4
8.2 k Resistor 0402 5% 0.063 W
RC0402JR-078K2L – Yageo
R5
39 k Resistor 0402 5% 0.063 W
RC0402JR-0739KL – Yageo
U1
Step-Down Regulator 8-VFQFPN 3 A 1 MHz
L5987TR – ST Microelectronics
Figure 21 and the components listed in Table 14 show an example of a low-cost power supply circuit, where the
VCC module supply is provided by a step-down switching regulator capable of delivering to VCC pins the specified
maximum peak / pulse current, transforming a 12 V supply input.
Figure 21: Example of low cost VCC supply application circuit using a step-down regulator
Table 14: Components for low cost VCC supply application circuit using a step-down regulator
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TOBY-L4 series - System Integration Manual
5V
C1R1
INOUT
ADJ
GND
1
2
4
5
3
C2R2
R3
U1
SHDN
TOBY-L4 series
71
VCC
72
VCC
70
VCC
GND
C3
Reference
Description
Part Number - Manufacturer
C1, C2
10 µF Capacitor Ceramic X5R 0603 20% 6.3 V
GRM188R60J106ME47 - Murata
C3
330 µF Capacitor Tantalum D_SIZE 6.3 V 45 m
T520D337M006ATE045 - KEMET
R1
47 k Resistor 0402 5% 0.1 W
RC0402JR-0747KL - Yageo Phycomp
R2
9.1 k Resistor 0402 5% 0.1 W
RC0402JR-079K1L - Yageo Phycomp
R3
3.9 k Resistor 0402 5% 0.1 W
RC0402JR-073K9L - Yageo Phycomp
U1
LDO Linear Regulator ADJ 3.0 A
LT1764AEQ#PBF - Linear Technology
2.2.1.3 Guidelines for VCC supply circuit design using a Low Drop-Out linear regulator
The use of a linear regulator is suggested when the difference from the available supply rail source and the VCC
value is low. The linear regulators provide high efficiency when transforming a 5 VDC supply to a voltage value
within the module VCC normal operating range.
The characteristics of the Low Drop-Out (LDO) linear regulator connected to the VCC pins should meet the
following prerequisites to comply with the module VCC requirements summarized in Table 7:
Power capabilities: the LDO linear regulator with its output circuit must be capable of providing a voltage
value to the VCC pins within the specified operating range and must be capable of delivering to the VCC pins
the maximum peak / pulse current consumption during Tx burst at maximum Tx power specified in the TOBY-L4 series Data Sheet [1].
Power dissipation: the power handling capability of the LDO linear regulator must be checked to limit its
junction temperature to the maximum rated operating range (i.e. check the voltage drop from the maximum
input voltage to the minimum output voltage to evaluate the power dissipation of the regulator).
Figure 22 and the components listed in Table 15 show an example of a power supply circuit where the VCC module
supply is provided by an LDO linear regulator capable of delivering the required current with a suitable power
handling capability.
It is recommended to configure the LDO linear regulator to generate a voltage supply value slightly below the
maximum limit of the module VCC normal operating range (e.g. ~4.1 V for the VCC, as in the circuits illustrated
in Figure 22 and Table 15). This reduces the power on the linear regulator and improves the thermal design of the
circuit.
Figure 22: Example of high reliability VCC supply application circuit using an LDO linear regulator
Table 15: Components for high reliability VCC supply application circuit using an LDO linear regulator
UBX-16024839 - R04 Design-in
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TOBY-L4 series - System Integration Manual
5V
C1
INOUT
ADJ
GND
1
2
4
5
3
C2R1
R2
U1
EN
TOBY-L4 series
71
VCC
72
VCC
70
VCC
GND
C3
Reference
Description
Part Number - Manufacturer
C1, C2
10 µF Capacitor Ceramic X5R 0603 20% 6.3 V
GRM188R60J106ME47 - Murata
C3
330 µF Capacitor Tantalum D_SIZE 6.3 V 45 m
T520D337M006ATE045 - KEMET
R1
27 k Resistor 0402 5% 0.1 W
RC0402JR-0727KL - Yageo Phycomp
R2
4.7 k Resistor 0402 5% 0.1 W
RC0402JR-074K7L - Yageo Phycomp
U1
LDO Linear Regulator ADJ 3.0 A
LP38501ATJ-ADJ/NOPB - Texas Instrument
Figure 23 and the components listed in Table 16 show an example of a low-cost power supply circuit, where the
VCC module supply is provided by an LDO linear regulator capable of delivering the specified highest peak / pulse
current, with suitable power handling capability. The regulator illustrated in this example supports a limited input
voltage range and it includes internal circuitry for current and thermal protection.
It is recommended to configure the LDO linear regulator to generate a voltage supply value slightly below the
maximum limit of the module’s VCC normal operating range (e.g. ~4.1 V as in the circuit illustrated in Figure 23
and Table 16). This reduces the power on the linear regulator and improves the whole thermal design of the supply
circuit.
Figure 23: Example of a low cost VCC supply application circuit using an LDO linear regulator
Table 16: Components for a low cost VCC supply application circuit using an LDO linear regulator
UBX-16024839 - R04 Design-in
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TOBY-L4 series - System Integration Manual
2.2.1.4 Guidelines for VCC supply circuit design using a rechargeable Li-Ion or Li-Pol battery
Rechargeable Li-Ion or Li-Pol batteries connected to the VCC pins should meet the following prerequisites to
comply with the module’sVCC requirements as summarized in Table 7:
Maximum pulse and DC discharge current: the rechargeable Li-Ion battery with its related output circuit
connected to the VCC pins must be capable of delivering a pulse current as the maximum peak / pulse current
consumption during Tx burst at the maximum Tx power specified in the TOBY-L4 seriesData Sheet [1] and
must be capable of extensively delivering a DC current as the maximum average current consumption as
specified in the TOBY-L4 seriesData Sheet [1]. The maximum discharge current is not always reported in the
data sheets of batteries, but the maximum DC discharge current is typically almost equal to the battery capacity
in Amp-hours divided by 1 hour.
DC series resistance: the rechargeable Li-Ion battery with its output circuit must be capable of avoiding a
VCC voltage drop below the operating range summarized in Table 7 during transmit bursts.
2.2.1.5 Guidelines for VCC supply circuit design using a primary (disposable) battery
The characteristics of a primary (non-rechargeable) battery connected to the VCC pins should meet the following
prerequisites to comply with the module’sVCC requirements as summarized in Table 7:
Maximum pulse and DC discharge current: the non-rechargeable battery with its related output circuit
connected to the VCC pins must be capable of delivering a pulse current as the maximum peak current
consumption during Tx burst at the maximum Tx power specified in the TOBY-L4 seriesData Sheet [1] and
must be capable of extensively delivering a DC current as the maximum average current consumption as
specified in the TOBY-L4 seriesData Sheet [1]. The maximum discharge current is not always reported in the
data sheets of batteries, but the maximum DC discharge current is typically almost equal to the battery capacity
in Amp-hours divided by 1 hour.
DC series resistance: the non-rechargeable battery with its output circuit must be capable of avoiding a VCC
voltage drop below the operating range as summarized in Table 7 during transmit bursts.
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TOBY-L4 series - System Integration Manual
C2
GND
C3C4
TOBY-L4 series
71
VCC
72
VCC
70
VCC
C1C5C6
3V8
+
Reference
Description
Part Number - Manufacturer
C1
8.2 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H8R2DZ01 - Murata
C2
15 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H150JA01 - Murata
C3
68 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H680JA01 - Murata
C4
10 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C103KA01 - Murata
C5
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C104KA01 - Murata
C6
330 µF Capacitor Tantalum D_SIZE 6.3 V 45 m
T520D337M006ATE045 - KEMET
2.2.1.6 Additional guidelines for VCC supply circuit design
To reduce voltage drops, use a low impedance power source. The series resistance of the power supply lines
(connected to the modules’ VCC and GND pins) on the application board and battery pack should also be
considered and minimized: cabling and routing must be as short as possible to minimize power losses.
Three pins are allocated to the VCC supply. Several pins are designated for GND connection. It is recommended
to correctly connect all of them to supply the module to minimize series resistance losses.
For modules supporting 2G radio access technology, to avoid voltage drop undershoot and overshoot at the start
and end of a transmit burst during a GSM call (when current consumption on the VCC supply can rise up as
specified in the TOBY-L4 seriesData Sheet [1]), place a bypass capacitor with large capacitance (at least 100 µF)
and low ESR near the VCC pins, for example:
To reduce voltage ripple and noise, improving RF performance especially if the application device integrates an
internal antenna, place the following bypass capacitors near the VCC pins:
68 pF capacitor with Self-Resonant Frequency in the 800/900 MHz range (e.g. Murata GRM1555C1H680J)
15 pF capacitor with Self-Resonant Frequency in 1800/1900 MHz range (e.g. Murata GRM1555C1E150J)
8.2 pF capacitor with Self-Resonant Frequency in 2500/2600 MHz range (e.g. Murata GRM1555C1H8R2D)
10 nF capacitor (e.g. Murata GRM155R71C103K) to filter digital logic noise from clocks and data sources
100 nF capacitor (e.g. Murata GRM155R61C104K) to filter digital logic noise from clocks and data sources
A suitable series ferrite bead can be correctly placed on the VCC line for additional noise filtering if required by
the specific application according to the whole application board design.
Figure 24: Suggested schematic for the VCC bypass capacitors to reduce ripple / noise on the supply voltage profile
Table 17: Suggested components to reduce ripple / noise on the VCC
The necessity of each part depends on the specific design, but it is recommended to provide all the bypass The ESD sensitivity rating of the VCC supply pins is 1 kV (HBM as per JESD22-A114). A higher protection
UBX-16024839 - R04 Design-in
Page 60 of 143
capacitors illustrated in Figure 24 / Table 17 if the application device integrates an internal antenna.
level can be required if the line is externally accessible on the application board, e.g. if the accessible battery
connector is directly connected to the supply pins. A higher protection level can be achieved by mounting
an ESD protection (e.g. EPCOS CA05P4S14THSG varistor) close to the accessible point.
TOBY-L4 series - System Integration Manual
C5C8C7C6C9
GND
TOBY-L4 series
71
VCC
72
VCC
70
VCC
+
USB
Supply
C3
R4
θ
U1
IUSB
IAC
IEND
TPRG
SD
VIN
VINSNS
MODE
ISEL
C2C1
5V0
TH
GND
VOUT
VOSNS
VREF
R1
R2
R3
Li-Ion/Li-Pol
Battery Pack
D1
B1
C4
Li-Ion/Li-Polymer
Battery Charger IC
D2
Reference
Description
Part Number - Manufacturer
B1
Li-Ion (or Li-Polymer) battery pack with 470 NTC
Various manufacturer
C1, C4
1 µF Capacitor Ceramic X7R 0603 10% 16 V
GRM188R71C105KA12 - Murata
C2, C6
10 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C103KA01 - Murata
C3
1 nF Capacitor Ceramic X7R 0402 10% 50 V
GRM155R71H102KA01 - Murata
C5
330 µF Capacitor Tantalum D_SIZE 6.3 V 45 m
T520D337M006ATE045 - KEMET
C7
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R61A104KA01 - Murata
C8
68 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H680JA01 - Murata
C9
15 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H150JA01 - Murata
D1, D2
Low Capacitance ESD Protection
CG0402MLE-18G - Bourns
R1, R2
24 k Resistor 0402 5% 0.1 W
RC0402JR-0724KL - Yageo Phycomp
R3
3.3 k Resistor 0402 5% 0.1 W
RC0402JR-073K3L - Yageo Phycomp
R4
1.0 k Resistor 0402 5% 0.1 W
RC0402JR-071K0L - Yageo Phycomp
U1
Single Cell Li-Ion (or Li-Polymer) Battery Charger IC
L6924U - STMicroelectronics
2.2.1.7 Guidelines for the external battery charging circuit
TOBY-L4 series modules do not have an on-board charging circuit. Figure 25 provides an example of a battery
charger design which is suitable for applications that are battery powered with a Li-Ion (or Li-Polymer) cell.
In the application circuit, a rechargeable Li-Ion (or Li-Polymer) battery cell, that features the correct pulse and DC
discharge current capabilities and the correct DC series resistance, is directly connected to the VCC supply input
of the module. Battery charging is completely managed by the STMicroelectronics L6924U Battery Charger IC that,
from a USB power source (5.0 V typ.), charges the battery as a linear charger, in three phases:
Pre-charge constant current (active when the battery is deeply discharged): the battery is charged with a
low current, set to 10% of the fast-charge current.
Fast-charge constant current: the battery is charged with the maximum current, configured by the value of
an external resistor to a value suitable for USB power source (~500 mA).
Constant voltage: when the battery voltage reaches the regulated output voltage (4.2 V), the L6924U starts
to reduce the current until the charge termination is done. The charging process ends when the charging
current reaches the value configured by an external resistor to ~15 mA or when the charging timer reaches
the value configured by an external capacitor to ~9800 s.
Using a battery pack with an internal NTC resistor, the L6924U can monitor the battery temperature to protect
the battery from operating under unsafe thermal conditions.
The L6924U, as a linear charger, is more suitable for applications where the charging source has a relatively low
nominal voltage (~5 V), so that a switching charger is suggested for applications where the charging source has a
relatively high nominal voltage (e.g. ~12 V, see the following section 2.2.1.8 for the specific design-in).
2.2.1.8 Guidelines for external battery charging and power path management circuit
Application devices where both a permanent primary supply / charging source (e.g. ~12 V) and a rechargeable
back-up battery (e.g. 3.7 V Li-Pol) are available at the same time as possible supply source should implement a
suitable charger / regulator with integrated power path management function to supply the module and the whole
device while simultaneously and independently charging the battery.
Figure 26 reports a simplified block diagram circuit showing the working principle of a charger / regulator with an
integrated power path management function. This component allows the system to be powered by a permanent
primary supply source (e.g. ~12 V) using the integrated regulator which simultaneously and independently
recharges the battery (e.g. 3.7 V Li-Pol) that represents the back-up supply source of the system: the power path
management feature permits the battery to supplement the system current requirements when the primary supply
source is not available or cannot deliver the peak system current.
A power management IC should meet the following prerequisites to comply with the module’sVCC requirements
as summarized in Table 7:
High efficiency internal step down converter, compliant with the performances specified in section 2.2.1.2
Low internal resistance in the active path Vout – Vbat, typically lower than 50 m
High efficiency switch mode charger with separate power path control
Figure 26: Charger / regulator with integrated power path management circuit block diagram
Figure 27 and the components listed in Table 19 provide an application circuit example where the MPS MP2617
switching charger / regulator with integrated power path management function provides the supply to the cellular
module while concurrently and autonomously charging a suitable Li-Ion (or Li-Polymer) battery with the correct
pulse and DC discharge current capabilities and the correct DC series resistance according to the rechargeable
battery recommendations as described in section 2.2.1.4.
The MP2617 IC constantly monitors the battery voltage and selects whether to use the external main primary
supply / charging source or the battery as the supply source for the module, and starts a charging phase
accordingly.
The MP2617 IC normally provides a supply voltage to the module regulated from the external main primary source
allowing immediate system operation even under missing or deeply discharged battery: the integrated switching
step-down regulator is capable to provide up to 3 A output current with low output ripple and fixed 1.6 MHz
switching frequency in PWM mode operation. The module load is satisfied in priority, then the integrated switching
charger will take the remaining current to charge the battery.
Additionally, the power path control allows an internal connection from the battery to the module with a low
series internal ON resistance (40 m typical), in order to supplement additional power to the module when the
current demand increases over the external main primary source or when this external source is removed.
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C10C13
GND
C12C11C14
TOBY-L4 series
71
VCC
72
VCC
70
VCC
+
Primary
Source
R3
U1
EN
ILIM
ISET
TMR
AGND
VIN
C2C1
12V
NTC
PGND
SW
SYS
BAT
C4
R1
R2
D1
θ
Li-Ion/Li-Pol
Battery Pack
B1
C5
Li-Ion/Li-Polymer Battery
Charger / Regulator with
Power Path Managment
VCC
C3C6
L1
BST
D2
VLIM
R4
R5
C7 C8
Reference
Description
Part Number - Manufacturer
B1
Li-Ion (or Li-Polymer) battery pack with 10 k NTC
Various manufacturer
C1, C5, C6
22 µF Capacitor Ceramic X5R 1210 10% 25 V
GRM32ER61E226KE15 - Murata
C2, C4, C11
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R61A104KA01 - Murata
C3
1 µF Capacitor Ceramic X7R 0603 10% 25 V
GRM188R71E105KA12 - Murata
C7, C13
68 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H680JA01 - Murata
C8, C14
15 pF Capacitor Ceramic C0G 0402 5% 25 V
GRM1555C1E150JA01 - Murata
C10
330 µF Capacitor Tantalum D_SIZE 6.3 V 45 m
T520D337M006ATE045 - KEMET
C12
10 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C103KA01 - Murata
D1, D2
Low Capacitance ESD Protection
CG0402MLE-18G - Bourns
R1, R3, R5
10 k Resistor 0402 5% 1/16 W
RC0402JR-0710KL - Yageo Phycomp
R2
1.0 k Resistor 0402 5% 0.1 W
RC0402JR-071K0L - Yageo Phycomp
R4
22 k Resistor 0402 5% 1/16 W
RC0402JR-0722KL - Yageo Phycomp
L1
1.2 µH Inductor 6 A 21 m 20%
7447745012 - Wurth
U1
Li-Ion/Li-Polymer Battery DC/DC Charger / Regulator
with integrated Power Path Management function
MP2617 - Monolithic Power Systems (MPS)
Battery charging is managed in three phases:
Pre-charge constant current (active when the battery is deeply discharged): the battery is charged with a
low current, set to 10% of the fast-charge current.
Fast-charge constant current: the battery is charged with the maximum current, configured by the value of
an external resistor to a value suitable for the application.
Constant voltage: when the battery voltage reaches the regulated output voltage (4.2 V), the current is
progressively reduced until the charge termination is done. The charging process ends when the charging
current reaches 10% of the fast-charge current or when the charging timer reaches the value configured by
an external capacitor.
Using a battery pack with an internal NTC resistor, the MP2617 can monitor the battery temperature to protect
the battery from operating under unsafe thermal conditions.
Several parameters, such as the charging current, the charging timings, the input current limit, the input voltage
limit, and the system output voltage, can be easily set according to the specific application requirements to the
actual electrical characteristics of the battery and the external supply / charging source: suitable resistors or
capacitors must be accordingly connected to the related pins of the IC.
Figure 27: Li-Ion (or Li-Polymer) battery charging and power path management application circuit
Table 19: Suggested components for a Li-Ion (or Li-Polymer) battery charging and power path management application circuit
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C3
GND
C2C1C4
TOBY-L4 series
71
VCC
72
VCC
70
VCC
+
VCC Supply Source
GND
GPIO
C5
R1
R3
R2
T2
T1
Application
Processor
Reference
Description
Part Number - Manufacturer
R1
47 k Resistor 0402 5% 0.1 W
RC0402JR-0747KL - Yageo Phycomp
R2
10 k Resistor 0402 5% 0.1 W
RC0402JR-0710KL - Yageo Phycomp
R3
100 k Resistor 0402 5% 0.1 W
RC0402JR-07100KL - Yageo Phycomp
T1
P-Channel MOSFET Low On-Resistance
AO3415 - Alpha & Omega Semiconductor Inc.
T2
NPN BJT Transistor
BC847 - Infineon
C1
330 µF Capacitor Tantalum D_SIZE 6.3 V 45 m
T520D337M006ATE045 - KEMET
C2
10 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C103KA01 - Murata
C3
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R61A104KA01 - Murata
C4
56 pF Capacitor Ceramic C0G 0402 5% 25 V
GRM1555C1E560JA01 - Murata
C5
15 pF Capacitor Ceramic C0G 0402 5% 25 V
GRM1555C1E150JA01 - Murata
2.2.1.9 Guidelines for removing VCC supply
As described in section 1.6.2 and Figure 14, the VCC supply can be removed after the end of the TOBY-L4 series
module’s internal power-off sequence, which must be properly started as described in section 1.6.2.
Removing the VCC power can be useful in order to minimize the current consumption when the TOBY-L4 series
modules are switched off. Then, the modules can be switched on again by re-applying the VCC supply.
If the VCC supply is generated by a switching or an LDO regulator, the application processor may control the input
pin of the regulator which is provided to enable / disable the output of the regulator (as for example, the RUN
input pin for the regulator illustrated in Figure 20, the INH input pin for the regulator illustrated in Figure 21, the
SHDNn input pin for the regulator illustrated in Figure 22, or the EN input pin for the regulator illustrated in Figure
23), in order to apply / remove the VCC supply.
If the regulator that generates the VCC supply does not provide an on / off pin, or for other applications such as
the battery-powered ones, the VCC supply can be switched off using an appropriate external p-channel MOSFET
controlled by the application processor by means of a suitable inverting transistor as shown in Figure 28, given
that the external p-channel MOSFET has provided:
Very low R
(for example, less than 50 m), to minimize voltage drops
DS(ON)
Adequate maximum Drain current (see the TOBY-L4 seriesData Sheet [1] for module consumption figures)
Low leakage current, to minimize the current consumption
Figure 28: Example of application circuit for VCC supply removal
Table 20: Components for VCC supply removal application circuit
It is highly recommended to avoid an abrupt removal of the VCC supply during the TOBY-L4 series module’s
normal operations: the power off procedure must be started as described in section 1.6.2, and then a
suitable VCC supply must be held at least until the end of the modules’ internal power off sequence, which
occurs when the generic digital interfaces supply output (V_INT) is switched off by the module.
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2.2.1.10 Guidelines for VCC supply layout design
A clean connection of the module VCC pins with a DC supply source is required for correct RF performance.
Guidelines are summarized in the following list:
All the available VCC pins must be connected to the DC source.
VCC connection must be as wide as possible and as short as possible.
Any series component with Equivalent Series Resistance (ESR) greater than few milliohms must be avoided.
VCC connection must be routed through a PCB area separated from RF lines / parts, sensitive analog signals
and sensitive functional units: it is good practice to interpose at least one layer of PCB ground between the
VCC track and other signal routing.
Coupling between VCC and digital lines, especially USB, must be avoided.
The tank bypass capacitor with low ESR for current spikes smoothing described in section 2.2.1.6 should be
placed close to the VCC pins. If the main DC source is a switching DC-DC converter, place the large capacitor
close to the DC-DC output and minimize the VCC track length. Otherwise consider using separate capacitors
for the DC-DC converter and module tank capacitor.
The bypass capacitors in the pF range illustrated in Figure 24 and Table 17 should be placed as close as possible
to the VCC pins, where the VCC line narrows close to the module input pins, improving the RF noise rejection
in the band centered on the Self-Resonant Frequency of the pF capacitors. This is highly recommended if the
application device integrates an internal antenna.
Since VCC input provides the supply to the RF Power Amplifiers, any voltage ripple at high frequency may
result in unwanted spurious modulation of the transmitter RF signal. This is more likely to happen with
switching DC-DC converters, in which case it is better to select the highest operating frequency for the
switcher and add a large L-C filter before connecting to the TOBY-L4 series modules in the worst case.
Shielding of switching DC-DC converter circuit, or at least the use of shielded inductors for the switching DC-
DC converter, may be considered since all switching power supplies may potentially generate interfering
signals as a result of high-frequency high-power switching.
If the VCC is protected by a transient voltage suppressor to ensure that the voltage maximum ratings are not
exceeded, place the protecting device along the path from the DC source toward the module, preferably closer
to the DC source (otherwise protection functionality may be compromised).
2.2.1.11 Guidelines for grounding layout design
A clean connection of the module GND pins with the application board solid ground layer is required for correct
RF performance. It significantly reduces EMC issues and provides a thermal heat sink for the module.
Connect each GND pin with the application board solid GND layer. It is strongly recommended that each GND
pad surrounding the VCC pins has one or more dedicated via down to the application board solid ground
layer.
The VCC supply current flows back to the main DC source through GND as the ground current: provide an
adequate return path with a suitable uninterrupted ground plane to the main DC source.
It is recommended to implement one layer of the application board as a ground plane as wide as possible.
If the application board is a multilayer PCB, then all the board layers should be filled with GND plane as much
as possible and each GND area should be connected together with a complete via stack down to the main
ground layer of the board.
If the whole application device is composed of more than one PCB, then it is required to provide a good and
solid ground connection between the GND areas of all the multiple PCBs.
Good grounding of the GND pads also ensures the thermal heat sink. This is critical during connection, when
the real network commands the module to transmit at maximum power: correct grounding helps prevent
module overheating.
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TOBY-L4 series
C1
a.
3
V_BCKP
R2
TOBY-L4 series
C2
(SuperCap)
b.
3
V_BCKP
D3
TOBY-L4 series
B3
c.
3
V_BCKP
Reference
Description
Part Number - Manufacturer
C1
100 µF Tantalum Capacitor
GRM43SR60J107M - Murata
R2
4.7 k Resistor 0402 5% 0.1 W
RC0402JR-074K7L - Yageo Phycomp
C2
70 mF Capacitor
XH414H-IV01E - Seiko Instruments
2.2.2 RTC back-up supply (V_BCKP)
2.2.2.1 Guidelines for V_BCKP circuit design
TOBY-L4 series modules provide the V_BCKP pin, which can be used to:
power the Real Time Clock (RTC) only when the voltage value at VCC main module supply input is too low
The RTC can be supplied from an external back-up battery or capacitor through the V_BCKP pin, when the main
module voltage supply is not applied to the VCC pins. This lets the time reference (date and time) run as long as
the V_BCKP voltage is within its valid range, even when the main supply is not provided to the module.
Figure 29 and Table 21 describe possible application circuits for V_BCKP Real Time Clock (RTC) back-up supply:
a. 100 µF capacitor, to let the RTC run for ~1 minute after the VCC removal
b. 70 mF super-capacitor with a 4.7 k series resistor, to let the RTC run for ~1 hour after the VCC removal
c. Coin non-rechargeable battery with series diode, to let the RTC run for days after the VCC removal
Figure 29: RTC back-up supply (V_BCKP) application circuits using a capacitor, a super-capacitor, or a non-rechargeable battery
Table 21: Example of components for RTC back-up supply (V_BCKP)
The V_BCKP supply output pin provides internal short circuit protection to limit the start-up current and protect
the device in short circuit situations. No additional external short circuit protection is required.
The V_BCKP pin can be left unconnected if the RTC timing is not required when the VCC supply is removed. The internal regulator for V_BCKP is optimized for low leakage current and very light loads. Do not apply
loads which might exceed the limit for the maximum available current from V_BCKP supply, as this can
cause malfunctions in the module. The TOBY-L4 seriesData Sheet [1] describes the detailed electrical
characteristics.
The ESD sensitivity rating of the V_BCKP supply pin is 1 kV (HBM according to JESD22-A114). A higher
protection level can be required if the line is externally accessible on the application board, e.g. if an
accessible back-up battery connector is directly connected to the V_BCKP pin, and it can be achieved by
mounting an ESD protection (e.g. EPCOS CA05P4S14THSG varistor array) close to the accessible point.
2.2.2.2 Guidelines for V_BCKP layout design
The V_BCKP supply requires careful layout: avoid injecting noise on this voltage domain, as it may affect the
stability of the internal circuitry.
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2.2.3 Generic digital interfaces supply output (V_INT)
2.2.3.1 Guidelines for V_INT circuit design
TOBY-L4 series provide the V_INT generic digital interfaces 1.8 V supply output, which can be mainly used to:
Indicate when the module is switched on (as described in sections 1.6.1, 1.6.2)
Pull-up SIM detection signal (see section 2.5 for more details)
Supply voltage translators to connect 1.8 V module generic digital interfaces to 3.0 V devices (e.g. see 2.6.1)
Pull-up DDC (I
Supply a 1.8 V u-blox GNSS receiver (see section 2.6.4 for more details)
Supply an external device as an external 1.8 V audio codec (see section 2.8.2 for more details)
The V_INT supply output pin provides internal short circuit protection to limit the start-up current and protect the
device in short circuit situations. No additional external short circuit protection is required.
2
C) interface signals (see section 2.6.4 for more details)
Do not apply loads which might exceed the limit for the maximum available current from V_INT supply as
this can cause malfunctions in the internal circuitry.
Since the V_INT supply is generated by an internal switching step-down regulator, it is not recommended
to supply sensitive analog circuitry without adequate filtering for digital noise.
V_INT can only be used as an output: do not connect any external supply source on V_INT. The ESD sensitivity rating of the V_INT supply pin is 1 kV (Human Body Model according to JESD22-A114).
A higher protection level could be required if the line is externally accessible and it can be achieved by
mounting an ESD protection (e.g. EPCOS CA05P4S14THSG varistor array) close to the accessible point.
It is recommended to monitor the V_INT pin to sense the end of the internal switch-off sequence of TOBY-
L4 series modules: the VCC supply can be removed only after V_INT goes low
It is recommended to provide direct access to the V_INT pin on the application board by means of an
accessible test point directly connected to the V_INT pin, for diagnostic purposes.
2.2.3.2 Guidelines for V_INT layout design
The V_INT supply output is generated by an integrated switching step-down converter. Because of this, it can be
a source of noise: avoid coupling with sensitive signals.
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TOBY-L4 series
20
PWR_ON
Power-on
push button
ESD
Open
Drain
Output
Application
Processor
TOBY-L4 series
35 k
1.3 V
20
PWR_ON
TP
TP
35 k
1.3 V
Reference
Description
Remarks
ESD
CT0402S14AHSG - EPCOS
Varistor array for ESD protection
2.3 System functions interfaces
2.3.1 Module power-on (PWR_ON)
2.3.1.1 Guidelines for PWR_ON circuit design
TOBY-L4 series PWR_ON input is equipped with an internal active pull-up resistor to an internal 1.3 V supply rail
as illustrated in Figure 30: an external pull-up resistor is not required and should not be provided.
If connecting the PWR_ON input to a push button, the pin will be externally accessible on the application device.
According to EMC/ESD requirements of the application, an additional ESD protection should be provided close to
the accessible point, as illustrated in Figure 30 and Table 22.
The ESD sensitivity rating of the PWR_ON pin is 1 kV (Human Body Model according to JESD22-A114).
A higher protection level can be required if the line is externally accessible on the application board, e.g. if
an accessible push button is directly connected to the PWR_ON pin, and it can be achieved by mounting
an ESD protection (e.g. EPCOS CA05P4S14THSG varistor) close to the accessible point.
An open drain or open collector output is suitable to drive the PWR_ON input from an application processor, as
the pin is equipped with an internal active pull-up resistor, as illustrated in Figure 30.
Figure 30: PWR_ON application circuits using a push button and an open drain output of an application processor
Table 22: Example ESD protection component for the PWR_ON application circuit
It is recommended to provide direct access to the PWR_ON pin on the application board by means of an
accessible test point directly connected to the PWR_ON pin, for diagnostic purposes.
2.3.1.2 Guidelines for PWR_ON layout design
The power-on circuit (PWR_ON) requires careful layout since it is the sensitive input available to switch on the
TOBY-L4 series modules. It is required to ensure that the voltage level is well defined during operation and no
transient noise is coupled on this line, otherwise the module might detect a spurious power-on request.
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TOBY-L4 series
5
V_INT
23
RESET_N
Power-on
push button
ESD
Open
Drain
Output
Application
Processor
TOBY-L4 series
5
V_INT
23
RESET_N
TP
TP
100 k
100 k
Reference
Description
Remarks
ESD
Varistor for ESD protection
CT0402S14AHSG - EPCOS
2.3.2 Module reset (RESET_N)
2.3.2.1 Guidelines for RESET_N circuit design
TOBY-L4 series RESET_N line is equipped with an internal pull-up to the V_INT supply as illustrated in Figure 31.
An external pull-up resistor is not required.
If connecting the RESET_N input to a push button, the pin will be externally accessible on the application device.
According to the EMC/ESD requirements of the application, an additional ESD protection device (e.g. the EPCOS
CA05P4S14THSG varistor) should be provided close to the accessible point on the line connected to this pin, as
illustrated in Figure 31 and Table 23.
The ESD sensitivity rating of the RESET_N pin is 1 kV (HBM according to JESD22-A114). A higher protection
level can be required if the line is externally accessible on the application board, e.g. if an accessible push
button is directly connected to the RESET_N pin, and it can be achieved by mounting an ESD protection
(e.g. EPCOS CA05P4S14THSG varistor) close to the accessible point.
An open drain output is suitable to drive the RESET_N input from an application processor as it is equipped with
an internal pull-up to V_INT supply, as illustrated in Figure 31.
A compatible push-pull output of an application processor can also be used. In any case, take care to set the
correct level in all the possible scenarios to avoid an inappropriate module reset.
Figure 31: RESET_N application circuits using a push button and an open drain output of an application processor
Table 23: Example of ESD protection component for the RESET_N application circuits
If the external reset function is not required by the customer application, the RESET_N input pin can be left
unconnected to external components, but it is recommended to provide direct access on the application
board by means of an accessible test point directly connected to the RESET_N pin.
2.3.2.2 Guidelines for RESET_N layout design
The RESET_N circuit requires careful layout due to the pin function: ensure that the voltage level is well defined
during operation and no transient noise is coupled on this line, otherwise the module might detect a spurious
reset request. It is recommended to keep the connection line to the RESET_N pin as short as possible.
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2.3.3 Module / host configuration selection
Host Select pins are not supported by the "50" product version.
2.3.3.1 Guidelines for HOST_SELECTx circuit design
TOBY-L4 series modules include two 1.8 V digital pins (HOST_SELECT0, HOST_SELECT1), which can be
configured for External Interrupt detection or as GPIO by means of the uCPU API: the pins can be connected to
external devices following the guidelines provided in section 2.10.
Do not apply voltage to the HOST_SELECT0 and HOST_SELECT1 pins before the switch-on of their supply
source (V_INT), to avoid latch-up of circuits and allow a correct boot of the module.
The ESD sensitivity rating of the HOST_SELECT0 and HOST_SELECT1 pins is 1 kV (HBM as per JESD22-
A114). A higher protection level could be required if the lines are externally accessible and it can be achieved
by mounting an ESD protection (e.g. EPCOS CA05P4S14THSG varistor array) close to the accessible points.
If the functionality of the HOST_SELECT0 and HOST_SELECT1 pins is not required, the pins can be left
unconnected on the application board.
2.3.3.2 Guidelines for HOST_SELECTx layout design
The design for the HOST_SELECT0 and HOST_SELECT1 pins functions is generally not critical for layout.
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2.4 Antenna interface
TOBY-L4 series modules provide two RF interfaces for connecting the external antennas:
The ANT1 pin represents the primary RF input/output for LTE/3G/2G RF signals transmission and reception.
The ANT2 pin represents the secondary RF input for MIMO and Rx diversity RF signals reception.
Both the ANT1 and the ANT2 pins have a nominal characteristic impedance of 50 and must be connected to
the related antenna through a 50 transmission line to allow correct transmission / reception of RF signals.
Two antennas (one connected to ANT1 pin and one connected to ANT2 pin) must be used to support the
CA, MIMO and Rx diversity configurations. This is a required feature for LTE category 6 User Equipments
(up to 301.5 Mbit/s Down-Link data rate) according to the 3GPP specifications.
2.4.1 Antenna RF interfaces (ANT1 / ANT2)
2.4.1.1 General guidelines for antenna selection and design
The antenna is the most critical component to be evaluated. Designers must take care of the antennas from all
perspectives at the very start of the design phase when the physical dimensions of the application board are under
analysis/decision, since the RF compliance of the device integrating TOBY-L4 series modules with all the applicable
required certification schemes depends on the antenna radiating performance.
LTE/3G/2G antennas are typically available in the types of linear monopole or PCB antennas such as patches or
ceramic SMT elements.
External antennas (e.g. linear monopole)
o External antennas basically do not imply a physical restriction to the design of the PCB where the TOBY-
L4 series module is mounted.
o The radiation performance mainly depends on the antennas. It is required to select antennas with optimal
radiating performance in the operating bands.
o RF cables should be carefully selected to have minimum insertion losses. Additional insertion loss will be
introduced by low quality or long cable. Large insertion loss reduces both transmit and receive radiation
performance.
o A high quality 50 RF connector provides suitable PCB-to-RF-cable transition. It is recommended to strictly
follow the layout and cable termination guidelines provided by the connector manufacturer.
Integrated antennas (e.g. patch-like antennas):
o Internal integrated antennas imply a physical restriction to the design of the PCB:
An integrated antenna excites RF currents on its counterpoise, typically the PCB ground plane of the device
that becomes part of the antenna: its dimension defines the minimum frequency that can be radiated.
Therefore, the ground plane can be reduced down to a minimum size that should be similar to the quarter
of the wavelength of the minimum frequency that must be radiated, given that the orientation of the
ground plane relative to the antenna element must be considered.
The isolation between the primary and the secondary antennas must be as high as possible and the
correlation between the 3D radiation patterns of the two antennas must be as low as possible. In general,
a separation of at least a quarter wavelength between the two antennas is required to achieve a good
isolation and low pattern correlation.
As a numerical example, the physical restriction to the PCB design can be considered as following:
Frequency = 750 MHz Wavelength = 40 cm Minimum GND plane size = 10 cm
o Radiation performance depends on the whole PCB and antenna system design, including product
mechanical design and usage. Antennas should be selected with optimal radiating performance in the
operating bands according to the mechanical specifications of the PCB and the whole product.
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Min.
250 µm
Min. 400 µm
GND
ANT1
GND clearance
on very close buried layer
below ANT1 pad
GND clearance
on top layer
around ANT1 pad
Min.
250 µm
Min. 400 µm
GND
ANT2
GND clearance
on very close buried layer
below ANT2 pad
GND clearance
on top layer
around ANT2 pad
o It is recommended to select a pair of custom antennas designed by an antennas’ manufacturer if the
required ground plane dimensions are very small (e.g. less than 6.5 cm long and 4 cm wide). The antenna
design process should begin at the start of the whole product design process.
o It is highly recommended to strictly follow the detailed and specific guidelines provided by the antenna
manufacturer regarding correct installation and deployment of the antenna system, including PCB layout
and matching circuitry.
o Further to the custom PCB and product restrictions, antennas may require tuning to obtain the required
performance for compliance with all the applicable required certification schemes. It is recommended to
consult the antenna manufacturer for the design-in guidelines for antenna matching relative to the custom
application.
In both cases, selecting external or internal antennas, these recommendations should be observed:
Select antennas providing optimal return loss (or VSWR) figures over all the operating frequencies.
Select antennas providing optimal efficiency figures over all the operating frequencies.
Select antennas providing similar efficiency for both the primary (ANT1) and the secondary (ANT2) antenna.
Select antennas providing appropriate gain figures (i.e. combined antenna directivity and efficiency figures) so
that the electromagnetic field radiation intensity does not exceed the regulatory limits specified in certain
countries (e.g. by the FCC in the United States).
Select antennas capable of providing a low Envelope Correlation Coefficient between the primary (ANT1) and
the secondary (ANT2) antenna: the 3D antenna radiation patterns should have lobes in different directions.
2.4.1.2 Guidelines for antenna RF interface design
Guidelines for ANT1 / ANT2 pins RF connection design
Correct transition between the ANT1 / ANT2 pads and the application board PCB must be provided, implementing
the following design-in guidelines for the application PCB layout close to the ANT1 / ANT2 pads:
On a multilayer board, the whole layer stack below the RF connection should be free of digital lines.
Increase GND keep-out (i.e. clearance, a void area) around the ANT1 / ANT2 pads, on the top layer of the
application PCB, to at least 250 µm up to the adjacent pads metal definition and up to 400 µm on the area
below the module, to reduce parasitic capacitance to ground, as illustrated in the left example of Figure 32.
Add GND keep-out (i.e. clearance, a void area) on the buried metal layer below the ANT1 / ANT2 pads if the
top-layer to buried layer dielectric thickness is below 200 µm, to reduce parasitic capacitance to ground, as
illustrated in the right example of Figure 32.
Figure 32: GND keep-out area on top layer around ANT1 / ANT2 pads and on very close buried layer below ANT1 / ANT2 pads
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35 µm
35 µm
35 µm
35 µm
270 µm
270 µm
760 µm
L1 Copper
L3 Copper
L2 Copper
L4 Copper
FR-4 dielectric
FR-4 dielectric
FR-4 dielectric
380 µm 500 µm500 µm
35 µm
35 µm
1510 µm
L2 Copper
L1 Copper
FR-4 dielectric
1200 µm 400 µm400 µm
Guidelines for RF transmission line design
Any RF transmission line, such as the ones from the ANT1 and ANT2 pads up to the related antenna connector
or up to the related internal antenna pad, must be designed so that the characteristic impedance is as close as
possible to 50 .
RF transmission lines can be designed as a micro strip (consists of a conducting strip separated from a ground
plane by a dielectric material) or a strip line (consists of a flat strip of metal which is sandwiched between two
parallel ground planes within a dielectric material). The micro strip, implemented as a coplanar waveguide, is the
most common configuration for printed circuit boards.
Figure 33 and Figure 34 provide two examples of suitable 50 coplanar waveguide designs. The first example of
an RF transmission line can be implemented for a 4-layer PCB stack-up herein illustrated, and the second example
of an RF transmission line can be implemented for a 2-layer PCB stack-up herein illustrated.
Figure 33: Example of a 50 coplanar waveguide transmission line design for the described 4-layer board layup
Figure 34: Example of a 50 coplanar waveguide transmission line design for the described 2-layer board layup
If the two examples do not match the application PCB stack-up, the 50 characteristic impedance calculation can
be made using the HFSS commercial finite element method solver for electromagnetic structures from Ansys
Corporation, or using freeware tools like AppCAD from Agilent (www.agilent.com) or TXLine from Applied Wave
Research (www.mwoffice.com), taking care of the approximation formulas used by the tools for the impedance
computation.
To achieve a 50 characteristic impedance, the width of the transmission line must be chosen depending on:
the thickness of the transmission line itself (e.g. 35 µm in the examples of Figure 33 and Figure 34)
the thickness of the dielectric material between the top layer (where the transmission line is routed) and the
inner closer layer implementing the ground plane (e.g. 270 µm in Figure 33, 1510 µm in Figure 34)
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SMA Connector
Primary Antenna
SMA Connector
Secondary Antenna
TOBY-L4
the dielectric constant of the dielectric material (e.g. dielectric constant of the FR-4 dielectric material in Figure
33 and Figure 34)
the gap from the transmission line to the adjacent ground plane on the same layer of the transmission line
(e.g. 500 µm in Figure 33, 400 µm in Figure 34)
If the distance between the transmission line and the adjacent GND area (on the same laye r) does not exceed
5 times the track width of the micro strip, use the “Coplanar Waveguide” model for the 50 calculation.
Additionally to the 50 impedance, the following guidelines are recommended for transmission line design:
Minimize the transmission line length: the insertion loss should be minimized as much as possible, in the order
of a few tenths of a dB.
Add GND keep-out (i.e. clearance, a void area) on buried metal layers below any pad of a component present
on the RF transmission lines, if the top-layer to buried layer dielectric thickness is below 200 µm, to reduce
parasitic capacitance to ground.
The transmission lines width and spacing to GND must be uniform and routed as smoothly as possible: avoid
abrupt changes of width and spacing to GND.
Add GND stitching vias around the transmission lines, as illustrated in Figure 35.
Ensure a solid metal connection of the adjacent metal layer on the PCB stack-up to the main ground layer,
providing enough vias on the adjacent metal layer, as illustrated in Figure 35.
Route RF transmission lines far from any noise source (as switching supplies and digital lines) and from any
sensitive circuit (as USB).
Avoid stubs on the transmission lines.
Avoid signal routing in parallel to the transmission lines or crossing the transmission lines on a buried metal
layer.
Do not route the microstrip lines below discrete components or other mechanics placed on the top layer.
An example of a suitable RF circuit design is illustrated in Figure 35. In this case, the ANT1 and ANT2 pins are
directly connected to SMA connectors by means of suitable 50 transmission lines, designed with a suitable
layout.
Figure 35: Example of the circuit and layout for antenna RF circuits on the application board
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Guidelines for RF termination design
RF terminations must provide a characteristic impedance of 50 as well as the RF transmission lines up to the RF
terminations themselves, to match the characteristic impedance of the ANT1 / ANT2 ports of the modules.
However, real antennas do not have a perfect 50 load on all the supported frequency bands. Therefore, to
reduce as much as possible any performance degradation due to antennas mismatch, the RF terminations must
provide optimal return loss (or VSWR) figures over all the operating frequencies, as summarized in Table 8 and
Table 9.
If external antennas are used, the antenna connectors represent the RF termination on the PCB:
Use suitable 50 connectors providing a correct PCB-to-RF-cable transition.
Strictly follow the connector manufacturer’s recommended layout, for example:
o SMA Pin-Through-Hole connectors require GND keep-out (i.e. clearance, a void area) on all the layers
around the central pin up to the annular pads of the four GND posts, as shown in Figure 35.
o U.FL surface-mounted connectors require no conductive traces (i.e. clearance, a void area) in the area
below the connector between the GND land pads.
Cut out the GND layer under RF connectors and close to buried vias, in order to remove stray capacitance and
thus keep the RF line 50 , e.g. the active pad of U.FL connectors needs to have a GND keep-out (i.e.
clearance, a void area) at least on the first inner layer to reduce parasitic capacitance to ground.
If integrated antennas are used, the RF terminations are represented by the integrated antennas themselves. The
following guidelines should be followed:
Use antennas designed by an antenna manufacturer, providing the best possible return loss (or VSWR).
Provide a ground plane large enough according to the relative integrated antenna requirements. The ground
plane of the application PCB can be reduced down to a minimum size that must be similar to one quarter of
a wavelength of the minimum frequency that must be radiated. As a numerical example,
Frequency = 750 MHz Wavelength = 40 cm Minimum GND plane size = 10 cm
It is highly recommended to strictly follow the detailed and specific guidelines provided by the antenna
manufacturer regarding correct installation and deployment of the antenna system, including PCB layout and
matching circuitry.
Further to the custom PCB and product restrictions, antennas may require a tuning to comply with all the
applicable required certification schemes. It is recommended to consult the antenna manufacturer for the
design-in guidelines for the antenna matching relative to the custom application.
Additionally, these recommendations regarding the antenna system placement must be followed:
Do not place antennas within a closed metal case.
Do not place the antennas in close vicinity to the end user since the emitted radiation in human tissue is limited
by regulatory requirements.
Place the antennas far from sensitive analog systems or employ countermeasures to reduce EMC issues.
Take care of interaction between co-located RF systems since the LTE/3G/2G transmitted power may interact
or disturb the performance of companion systems.
Place the two LTE antennas providing low Envelope Correlation Coefficient (ECC) between the primary (ANT1)
and secondary (ANT2) antenna: the antenna 3D radiation patterns should have lobes in different directions.
The ECC between the primary and secondary antennas needs to be low enough to comply with the radiated
performance requirements specified by related certification schemes, as indicated in Table 10.
Place the two LTE antennas providing enough high isolation (see Table 10) between the primary (ANT1) and
secondary (ANT2) antennas. The isolation depends on the distance between antennas (separation of at least
a quarter wavelength required for good isolation), antenna type (using antennas with different polarization
improves isolation), and the antenna 3D radiation patterns (uncorrelated patterns improve isolation).
GSM / WCDMA / LTE adhesive-mount antenna with cable and SMA(M)
698..960 MHz, 1575.42 MHz, 1710..2700 MHz
105 x 30 x 7.7 mm
Taoglas
MA241.BI.001
Genesis
GSM / WCDMA / LTE MIMO 2-in-1 adhesive-mount combination antenna
waterproof IP67 rated with cable and SMA(M)
698..960 MHz, 1710..2690 MHz
205.8 x 58 x 12.4 mm
Laird Tech.
TRA6927M3PW-001
GSM / WCDMA / LTE screw-mount antenna with N-type(F)
698..960 MHz, 1710..2170 MHz, 2300..2700 MHz
83.8 x Ø 36.5 mm
Laird Tech.
OC69271-FNM
GSM / WCDMA / LTE pole-mount antenna with N-type(M)
698..960 MHz, 1710..2690 MHz
248 x Ø 24.5 mm
Laird Tech.
CMD69273-30NM
GSM / WCDMA / LTE ceiling-mount MIMO antenna with cables & N-type(M)
698..960 MHz, 1710..2700 MHz
43.5 x Ø 218.7 mm
Pulse Electronics
WA700/2700SMA
GSM / WCDMA / LTE clip-mount MIMO antenna with cables and SMA(M)
698..960 MHz,1710..2700 MHz
149 x 127 x 5.1 mm
Examples of antennas
Table 24 lists some examples of possible internal on-board surface-mount antennas.
Table 24: Examples of internal surface-mount antennas
Table 25 lists some examples of possible internal off-board PCB-type antennas with cable and connector.
Table 25: Examples of internal antennas with cable and connector
Table 26 lists some examples of possible external antennas.
Table 26: Examples of external antennas
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Application Board
Antenna Cable
TOBY-L4 series
81
ANT1
75
ANT_DET
R1
C1 D1
C2
J1
Z0= 50 ohmZ0= 50 ohm
Z0= 50 ohm
Primary Antenna Assembly
R2
C4
L3
Radiating
Element
Diagnostic
Circuit
L2
L1
Antenna Cable
87
ANT2
C3
J2
Z0= 50 ohmZ0= 50 ohm
Z0= 50 ohm
Secondary Antenna Assembly
R3
C5
L4
Radiating
Element
Diagnostic
Circuit
Reference
Description
Part Number - Manufacturer
C1
27 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H270J - Murata
C2, C3
33 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H330J - Murata
D1
Very Low Capacitance ESD Protection
PESD0402-140 - Tyco Electronics
L1, L2
68 nH Multilayer Inductor 0402 (SRF ~1 GHz)
LQG15HS68NJ02 - Murata
R1
10 k Resistor 0402 1% 0.063 W
RK73H1ETTP1002F - KOA Speer
J1, J2
SMA Connector 50 Through Hole Jack
SMA6251A1-3GT50G-50 - Amphenol
C4, C5
22 pF Capacitor Ceramic C0G 0402 5% 25 V
GRM1555C1H220J - Murata
L3, L4
68 nH Multilayer Inductor 0402 (SRF ~1 GHz)
LQG15HS68NJ02 - Murata
R2, R3
15 k Resistor for Diagnostic
Various Manufacturers
2.4.2 Antenna detection interface (ANT_DET)
2.4.2.1 Guidelines for ANT_DET circuit design
Figure 36 and Table 27 describe the recommended schematic / components for the antennas detection circuit that
must be provided on the application board and for the diagnostic circuit that must be provided on the antennas’
assembly to achieve primary and secondary antenna detection functionality.
Figure 36: Suggested schematic for the antenna detection circuit on the application board and the diagnostic circuit on the
antennas assembly
Table 27: Suggested components for the antenna detection circuit on the application board and the diagnostic circuit on the
antennas assembly
The antenna detection circuit and diagnostic circuit suggested in Figure 36 and Table 27 are explained here:
When antenna detection is forced by the AT+UANTR command, ANT_DET generates a DC current measuring
the resistance (R2 // R3) from the antenna connectors (J1, J2) provided on the application board to GND.
DC blocking capacitors are needed at the ANT1 / ANT2 pins (C2, C3) and at the antenna radiating element
(C4, C5) to decouple the DC current generated by the ANT_DET pin.
Choke inductors with a Self Resonance Frequency (SRF) in the range of 1 GHz are needed in series at the
ANT_DET pin (L1, L2) and in series at the diagnostic resistor (L3, L4), to avoid a reduction of the RF
performance of the system, improving the RF isolation of the load resistor.
Additional components (R1, C1 and D1 in Figure 36) are needed at the ANT_DET pin as ESD protection.
The ANT1 / ANT2 pins must be connected to the antenna connector by means of a transmission line with a
nominal characteristic impedance as close as possible to 50 .
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The DC impedance at the RF port for some antennas may be a DC open (e.g. linear monopole) or a DC short to
reference GND (e.g. PIFA antenna). For those antennas without the diagnostic circuit of Figure 36, the measured
DC resistance is always at the limits of the measurement range (respectively open or short), and there is no means
to distinguish between a defect on the antenna path with similar characteristics (respectively: removal of linear
antenna or RF cable shorted to GND for a PIFA antenna).
Furthermore, any other DC signal injected to the RF connection from an ANT connector to a radiating element will
alter the measurement and produce invalid results for antenna detection.
It is recommended to use an antenna with a built-in diagnostic resistor in the range from 5 k to 30 k to
assure good antenna detection functionality and avoid a reduction of module RF performance. The choke
inductor should exhibit a parallel Self Resonance Frequency (SRF) in the range of 1 GHz to improve the RF
isolation of the load resistor.
For example:
Consider an antenna with a built-in DC load resistor of 15 k. Using the +UANTR AT command, the module
reports the resistance value evaluated from the antenna connector provided on the application board to GND:
Reported values close to the used diagnostic resistor nominal value (i.e. values from 13 k to 17 k if a 15 k
diagnostic resistor is used) indicate that the antenna is properly connected.
Values close to the measurement range maximum limit (approximately 50 k) or an open-circuit “over range”
report (see the u-blox AT Commands Manual [2]) means that that the antenna is not connected or the RF
cable is broken.
Reported values below the measurement range minimum limit (1 k) indicate a short to GND at the antenna
or along the RF cable.
Measurement inside the valid measurement range and outside the expected range may indicate an incorrect
connection, damaged antenna or wrong value of antenna load resistor for diagnostics.
The reported value could differ from the real resistance value of the diagnostic resistor mounted inside the
antenna assembly due to the antenna cable length, the antenna cable capacity or the measurement method
used.
If the primary / secondary antenna detection function is not required by the customer application, the
ANT_DET pin can be left unconnected and the ANT1 / ANT2 pins can be directly connected to the related
antenna connector by means of a 50 transmission line as illustrated in Figure 35.
2.4.2.2 Guidelines for ANT_DET layout design
The recommended layout for the primary antenna detection circuit to be provided on the application board to
achieve the primary antenna detection functionality, implementing the recommended schematic illustrated in
Figure 36 and Table 27, is explained here:
The ANT1 / ANT2 pins must be connected to the antenna connector by means of a 50 transmission line,
implementing the design guidelines described in section 2.4.1 and the recommendations of the SMA
connector manufacturer.
DC blocking capacitor at ANT1 / ANT2 pins (C2, C3) must be placed in series to the 50 RF line.
The ANT_DET pin must be connected to the 50 transmission line by means of a sense line.
Choke inductors in series at the ANT_DET pin (L1, L2) must be placed so that one pad is on the 50
transmission line and the other pad represents the start of the sense line to the ANT_DET pin.
The additional components (R1, C1 and D1) on the ANT_DET line must be placed as ESD protection.
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2.5 SIM interfaces
2.5.1 Guidelines for SIM circuit design
Guidelines for SIM cards, SIM connectors and SIM chips selection
TOBY-L4 series modules provide two SIM interfaces for the direct connection of two external SIM cards/chips,
which can be used alternatively (only one SIM at a time can be used for network access):
The ISO/IEC 7816, the ETSI TS 102 221 and the ETSI TS 102 671 specifications define the physical, electrical and
functional characteristics of Universal Integrated Circuit Cards (UICC), which contains the Subscriber Identification
Module (SIM) integrated circuit that securely stores all the information needed to identify and authenticate
subscribers over the LTE/3G/2G network.
Removable UICC / SIM card contact mapping is defined by ISO/IEC 7816 and ETSI TS 102 221 as follows:
Contact C1 = VCC (Supply) It must be connected to VSIM / VSIM1
Contact C2 = RST (Reset) It must be connected to SIM_RST / SIM1_RST
Contact C3 = CLK (Clock) It must be connected to SIM_CLK / SIM1_CLK
Contact C4 = AUX1 (Auxiliary contact) It must be left not connected
Contact C5 = GND (Ground) It must be connected to GND
Contact C6 = VPP (Programming supply) It can be left not connected
Contact C7 = I/O (Data input/output) It must be connected to SIM_IO / SIM1_IO
Contact C8 = AUX2 (Auxiliary contact) It must be left not connected
A removable SIM card can have 6 contacts (C1, C2, C3, C5, C6, C7) or 8 contacts, also including the auxiliary
contacts C4 and C8. Only 6 contacts are required and must be connected to the module SIM interface.
Removable SIM cards are suitable for applications requiring a change of SIM card during the product’s lifetime.
A SIM card holder can have 6 or 8 positions if a mechanical card presence detector is not provided, or it can have
6+2 or 8+2 positions if two additional pins relative to the normally-open mechanical switch integrated in the SIM
connector for the mechanical card presence detection are provided. Select a SIM connector providing 6+2 or 8+2
positions if the optional SIM detection feature is required by the custom application, otherwise a connector without
an integrated mechanical presence switch can be selected.
Solderable UICC / SIM chip contact mapping (M2M UICC Form Factor) is defined by ETSI TS 102 671 as:
Case Pin 8 = UICC Contact C1 = VCC (Supply) It must be connected to VSIM / VSIM1
Case Pin 7 = UICC Contact C2 = RST (Reset) It must be connected to SIM_RST / SIM1_RST
Case Pin 6 = UICC Contact C3 = CLK (Clock) It must be connected to SIM_CLK / SIM1_CLK
Case Pin 5 = UICC Contact C4 = AUX1 (Aux.contact) It must be left not connected
Case Pin 1 = UICC Contact C5 = GND (Ground) It must be connected to GND
Case Pin 2 = UICC Contact C6 = VPP (Progr. supply) It can be left not connected
Case Pin 3 = UICC Contact C7 = I/O (Data I/O) It must be connected to SIM_IO / SIM1_IO
Case Pin 4 = UICC Contact C8 = AUX2 (Aux. contact) It must be left not connected
A solderable SIM chip has 8 contacts and can also include the auxiliary contacts C4 and C8 for other uses, but only
6 contacts are required and must be connected to the module SIM card interface as described above.
Solderable SIM chips are suitable for M2M applications where it is not required to change the SIM once installed.
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TOBY-L4 series
VSIMx
SIMx_IO
SIMx_CLK
SIMx_RST
SIM CARD
HOLDER
C5C6C
7
C1C2C
3
SIM Card
Bottom View
(contacts side)
C1
VPP (C6)
VCC (C1)
IO (C7)
CLK (C3)
RST (C2)
GND (C5)
C2 C3C5
J1
C4
D1 D2 D3 D4
C
8
C
4
Reference
Description
Part Number - Manufacturer
C1, C2, C3, C4
47 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H470JA01 - Murata
C5
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C104KA01 - Murata
D1, D2, D3, D4
Very Low Capacitance ESD Protection
PESD0402-140 - Tyco Electronics
J1
SIM Card Holder, 6 p, without card presence switch
Various manufacturers, as C707 10M006 136 2 - Amphenol
Guidelines for single SIM card connection without detection
A removable SIM card placed in a SIM card holder must be connected to the SIM0 or the SIM1 interface of TOBYL4 series modules as illustrated in Figure 37, where the optional SIM detection feature is not implemented.
Follow these guidelines to connect the module to a SIM connector without SIM presence detection:
Connect the UICC / SIM contact C1 (VCC) to the VSIM or the VSIM1 pin of the module.
Connect the UICC / SIM contact C7 (I/O) to the SIM_IO or the SIM1_IO pin of the module.
Connect the UICC / SIM contact C3 (CLK) to the SIM_CLK or the SIM1_CLK pin of the module.
Connect the UICC / SIM contact C2 (RST) to the SIM_RST or the SIM1_RST pin of the module.
Connect the UICC / SIM contact C5 (GND) to ground.
Provide a 100 nF bypass capacitor (e.g. Murata GRM155R71C104K) on SIM supply line, close to the relative
pad of the SIM connector, to prevent digital noise.
Provide a bypass capacitor of about 22 pF to 47 pF (e.g. Murata GRM1555C1H470J) on each SIM line, very
close to each related pad of the SIM connector, to prevent RF coupling especially when the RF antenna is
placed closer than 10 - 30 cm from the SIM card holder.
Provide a very low capacitance (i.e. less than 10 pF) ESD protection (e.g. Tyco PESD0402-140) on each
externally accessible SIM line, close to each relative pad of the SIM connector. The ESD sensitivity rating of the
SIM interface pins is 1 kV (HBM). So that, according to EMC/ESD requirements of the custom application, a
higher protection level can be required if the lines are externally accessible on the application device.
Limit the capacitance and series resistance on each SIM signal to match the SIM requirements (27.7 ns is the
maximum allowed rise time on the clock line, 1.0 µs is the maximum allowed rise time on the data and reset
lines).
Figure 37: Application circuits for the connection to a single removable SIM card, with SIM detection not implemented
Table 28: Example of components for the connection to a single removable SIM card, with SIM detection not implemented
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TOBY-L4 series
VSIMx
SIMx_IO
SIMx_CLK
SIMx_RST
SIM CHIP
SIM Chip
Bottom View
(contacts side)
C1
VPP (C6)
VCC (C1)
IO (C7)
CLK (C3)
RST (C2)
GND (C5)
C2 C3C5
U1
C4
2
8
3
6
7
1
C1C5
C2C6
C3C7
C4C8
8
7
6
5
1
2
3
4
Reference
Description
Part Number - Manufacturer
C1, C2, C3, C4
47 pF Capacitor Ceramic C0G 0402 5% 50 V
GRM1555C1H470JA01 - Murata
C5
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C104KA01 - Murata
U1
SIM chip (M2M UICC Form Factor)
Various Manufacturers
Guidelines for single SIM chip connection
A solderable SIM chip (M2M UICC Form Factor) must be connected the SIM0 / SIM1 interface of TOBY-L4 series
modules as illustrated in Figure 38.
Follow these guidelines to connect the module to a solderable SIM chip without SIM presence detection:
Connect the UICC / SIM contact C1 (VCC) to the VSIM or the VSIM1 pin of the module.
Connect the UICC / SIM contact C7 (I/O) to the SIM_IO or the SIM1_IO pin of the module.
Connect the UICC / SIM contact C3 (CLK) to the SIM_CLK or the SIM1_CLK pin of the module.
Connect the UICC / SIM contact C2 (RST) to the SIM_RST or the SIM1_RST pin of the module.
Connect the UICC / SIM contact C5 (GND) to ground.
Provide a 100 nF bypass capacitor (e.g. Murata GRM155R71C104K) at the SIM supply line close to the relative
pad of the SIM chip, to prevent digital noise.
Provide a bypass capacitor of about 22 pF to 47 pF (e.g. Murata GRM1555C1H470J) on each SIM line, to
prevent RF coupling especially when the RF antenna is placed closer than 10 - 30 cm from the SIM lines.
Limit the capacitance and series resistance on each SIM signal to match the SIM requirements (20.5 ns is the
maximum rise time on the clock line, 1.0 µs is the maximum rise time on the data and reset lines).
Figure 38: Application circuits for the connection to a single solderable SIM chip, with SIM detection not implemented
Table 29: Example of components for the connection to a single solderable SIM chip, with SIM detection not implemented
Various manufacturers, as CCM03-3013LFT R102 - C&K
Guidelines for single SIM card connection with detection
If the optional SIM card detection feature is required by the application, then a removable SIM card placed in a
SIM card holder must be connected to the SIM0 interface of TOBY-L4 series modules as illustrated in Figure 39:
Follow these guidelines to connect the module to a SIM connector implementing SIM presence detection:
Connect the UICC / SIM contact C1 (VCC) to the VSIM pin of the module.
Connect the UICC / SIM contact C7 (I/O) to the SIM_IO pin of the module.
Connect the UICC / SIM contact C3 (CLK) to the SIM_CLK pin of the module.
Connect the UICC / SIM contact C2 (RST) to the SIM_RST pin of the module.
Connect the UICC / SIM contact C5 (GND) to ground.
Connect one pin of the normally-open mechanical switch integrated in the SIM connector (e.g. the SW2 pin
as illustrated in Figure 39) to the GPIO5 input pin of the module.
Connect the other pin of the normally-open mechanical switch integrated in the SIM connector (e.g. the SW1
pin as illustrated in Figure 39) to the V_INT 1.8 V supply output of the module by means of a strong (e.g.
1 k) pull-up resistor, as the R1 resistor in Figure 39.
Provide a weak (e.g. 470 k) pull-down resistor at the SIM detection line, as the R2 resistor in Figure 39.
Provide a 100 nF bypass capacitor (e.g. Murata GRM155R71C104K) at the SIM supply line, close to the related
pad of the SIM connector, to prevent digital noise.
Provide a bypass capacitor of about 22 pF to 47 pF (e.g. Murata GRM1555C1H470J) on each SIM line, very
close to each related pad of the SIM connector, to prevent RF coupling especially when the RF antenna is
placed closer than 10 - 30 cm from the SIM card holder.
Provide a very low capacitance (i.e. less than 10 pF) ESD protection (e.g. Tyco PESD0402-140) on each
externally accessible SIM line, close to each related pad of the SIM connector: ESD sensitivity rating of the SIM
interface pins is 1 kV (HBM), so that, according to the EMC/ESD requirements of the custom application, a
higher protection level can be required if the lines are externally accessible on the application device.
Limit the capacitance and series resistance on each SIM signal to match the SIM requirements (20.5 ns is the
maximum rise time on the clock line, 1.0 µs is the maximum rise time on the data and reset lines).
Figure 39: Application circuit for the connection to a single removable SIM card, with SIM detection implemented
Table 30: Example of components for the connection to a single removable SIM card, with SIM detection implemented
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TOBY-L4 series - System Integration Manual
Guidelines for dual SIM card / chip connection
Two SIM cards / chips can be connected to the SIM interfaces of TOBY-L4 modules as illustrated in Figure 40.
TOBY-L4 series modules do not support the usage of two SIMs at the same time, but two SIMs can be populated
on the application board:
connecting the first SIM to the SIM0 interface of the module and connecting the second SIM to the SIM1
interface of the module, as illustrated in Figure 40 top side
In this case, the SIM interface and the related external SIM card / chip to be used can be selected by means of
the AT+XSIMSWITCH command (see u-blox AT Commands Manual [2]) or by means of uCPU application,
performing the SIM switch operation
providing a suitable switch to connect only the first or only the second SIM at a time to the SIM0 interface of
the module, as illustrated in Figure 40 bottom side
In this case, if the SIM hot insertion / removal feature is enabled on the GPIO5 pin by AT commands (see
sections 1.8.2 and 1.13, and the u-blox AT Commands Manual [2], +UGPIOC, +UDCONF=50 commands) or
by means of uCPU application, than the switch from the first to the second external SIM can be properly done
when a Low logic level is present on the GPIO5pin (“SIM not inserted” = SIM interface not enabled), without
the necessity of a module re-boot, so that the SIM interface will be re-enabled by the module to use the
second SIM when a high logic level is re-applied on the GPIO5 pin. The application processor will drive the
SIM switch using its own GPIO to properly select the SIM that is used by the module. Another GPIO may be
used to handle the SIM hot insertion / removal function of TOBY-L4 series modules, which can also be handled
by other external circuits or by the cellular module GPIO according to the application requirements.
The dual SIM connection circuit illustrated in Figure 40 can be implemented for SIM chips as well.
If it is required to switch between more than 2 SIMs, a circuit similar to the one illustrated in Figure 40 bottom
side can be implemented, using suitable switches.
Follow these guidelines to connect the module to two external UICC / SIM:
Connect the contact C1 (VCC) of the first external UICC / SIM to the VSIM pin of the module and the one of
the second external UICC / SIM to the VSIM1 pin of the module.
Connect the contact C7 (I/O) of the first external UICC / SIM to the SIM_IO pin of the module and the one of
the second external UICC / SIM to the SIM1_IO pin of the module.
Connect the contact C3 (CLK) of the first external UICC / SIM to the SIM_CLK pin of the module and the one
of the second external UICC / SIM to the SIM1_CLK pin of the module.
Connect the contact C2 (RST) of the first external UICC / SIM to the SIM_RST pin of the module and the one
of the second external UICC / SIM to the SIM1_RST pin of the module.
Connect the contact C5 (GND) of each external UICC / SIM to ground.
Provide a 100 nF bypass capacitor (e.g. Murata GRM155R71C104K) at the SIM supply (VSIM / VSIM1), close
to the related pad of each external UICC / SIM, to prevent digital noise.
Provide a bypass capacitor of about 22 pF to 47 pF (e.g. Murata GRM1555C1H470J) on each SIM line, very
close to each related pad of each external SIM connector, to prevent RF coupling especially when the RF
antenna is placed closer than 10 - 30 cm from the SIM card holders.
Provide a very low capacitance (i.e. less than 10 pF) ESD protection (e.g. Tyco Electronics PESD0402-140) on
each externally accessible SIM line, close to each pad of each external SIM connector, according to the
EMC/ESD requirements of the custom application.
Limit the capacitance and series resistance on each SIM signal to match the SIM requirements (20.5 ns is the
maximum rise time on the clock line, 1.0 µs is the maximum rise time on the data and reset lines).
If a circuit as the one illustrated in Figure 40 bottom side is implemented, use a suitable low on resistance (i.e.
few ohms) and low on capacitance (i.e. few pF) 2-throw analog switch (e.g. Fairchild FSA2567) as SIM switch
to ensure high-speed data transfer according to SIM requirements.
4PDT Analog Switch,
with Low On-Capacitance and Low On-Resistance
FSA2567 - Fairchild Semiconductor
Figure 40: Application circuits for the connection to two removable SIM cards, with SIM detection not implemented
Table 31: Example of components for the connection to two removable SIM cards, with SIM detection not implemented
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2.5.2 Guidelines for SIM layout design
The layout of the SIM card interfaces lines (VSIM, SIM_CLK, SIM_IO, SIM_RST for the SIM0 interface, and VSIM1,
SIM1_IO, SIM1_CLK, SIM1_RST for the SIM1 interface) may be critical if the SIM card is placed far away from
the TOBY-L4 series modules or in close proximity to the RF antenna: these two cases should be avoided or at least
mitigated as described below.
In the first case, the long connection can cause the radiation of some harmonics of the digital data frequency as
any other digital interface. It is recommended to keep the traces short and avoid coupling with the RF line or
sensitive analog inputs.
In the second case, the same harmonics can be picked up and create self-interference that can reduce the sensitivity
of LTE/3G/2G receiver channels whose carrier frequency is coincidental with the harmonic frequencies. It is strongly
recommended to place the RF bypass capacitors suggested in Figure 37 near the SIM connector.
In addition, since the SIM card is typically accessed by the end user, it can be subjected to ESD discharges. Add
adequate ESD protection as suggested to protect the module SIM pins near the SIM connector.
Limit the capacitance and series resistance on each SIM signal to match the SIM specifications. The connections
should always be kept as short as possible.
Avoid coupling with any sensitive analog circuit, since the SIM signals can cause the radiation of some harmonics
of the digital data frequency.
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D+
D–
GND
28
USB_D+
27
USB_D–
GND
USB 2.0 DEVICE
CONNECTOR
VBUS
D+
D–
GND
USB 2.0 HOST
PROCESSOR
TOBY-L4 series
VBUS
4
VUSB_DET
D1 D2 D3
C1
C1
28
USB_D+
27
USB_D–
GND
TOBY-L4 series
4
VUSB_DET
168
USB_ID
168
USB_ID
170
USB_SSRX+
171
USB_SSRX–
175
USB_SSTX+
176
USB_SSTX–
170
USB_SSRX+
171
USB_SSRX–
175
USB_SSTX+
176
USB_SSTX–
Reference
Description
Part Number - Manufacturer
C1
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R61A104KA01 - Murata
D1, D2, D3
Very Low Capacitance ESD Protection
PESD0402-140 - Tyco Electronics
2.6 Data communication interfaces
2.6.1 USB interface
2.6.1.1 Guidelines for USB circuit design
Different application circuits can be implemented for the USB interface according to specific use-case:
USB 2.0 interface, with the module acting as USB device, as illustrated in Figure 41 and Table 32
USB 2.0 interface, with the module acting as USB host, as illustrated in Figure 42 and Table 33
USB 3.0 interface, with the module acting as USB device, as illustrated in Figure 43 and Table 34
USB pull-up or pull-down resistors and external series resistors on the USB_D+ and USB_D– lines as required by
the USB 2.0 specification [3] are part of the module USB pins driver and do not need to be externally provided.
Series DC decoupling capacitors are internally provided on the USB_SSTX+ and USB_SSTX– lines as required by
the USB 3.0 specification [4] and do not need to be externally provided.
The USB_SSTX+/USB_SSTX– USB Super-Speed differential transmitter data output lines of the module must be
connected to the USB Super-Speed differential receiver data input lines of the external USB 3.0 host.
The USB_SSRX+/USB_SSRX– USB Super-Speed differential receiver data input lines of the module must be
connected to the USB Super-Speed differential transmitter data output lines of the external USB 3.0 host, with
series DC decoupling capacitors being provided on the host side as per the USB 3.0 specification [4].
Routing the USB pins to a connector, they will be externally accessible on the application device. According to the
EMC/ESD requirements of the application, an additional ESD protection device with very low capacitance should
be provided close to the accessible point on the line connected to this pin.
The USB interface pins ESD sensitivity rating is 1 kV (Human Body Model according to JESD22-A114F).
A higher protection level could be required if the lines are externally accessible and it can be achieved by
mounting a very low capacitance (i.e. less or equal to 1 pF) ESD protection (e.g. Tyco Electronics PESD0402140 ESD protection device) on the lines connected to these pins, close to the accessible points.
The USB pins of the modules can be directly connected to the USB host application processor without additional
ESD protections if they are not externally accessible or according to EMC/ESD requirements.
Figure 41: USB 2.0 interface application circuits, with TOBY-L4 series module acting as a USB device
Table 32: Component for USB 2.0 interface application circuits, with TOBY-L4 series module acting as a USB device
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D+
D–
GND
28
USB_D+
27
USB_D–
GND
USB 2.0 HOST
CONNECTOR
VBUS
D+
D–
GND
USB 2.0 DEVICE
PROCESSOR
TOBY-L4 series
VBUS
4
VUSB_DET
D1 D2 D3
C2
C2
28
USB_D+
27
USB_D–
GND
TOBY-L4 series
4
VUSB_DET
168
USB_ID
168
USB_ID
170
USB_SSRX+
171
USB_SSRX–
175
USB_SSTX+
176
USB_SSTX–
170
USB_SSRX+
171
USB_SSRX–
175
USB_SSTX+
176
USB_SSTX–
Boost
INOUT
Boost
INOUT
C1
5V
5V
C1
VCC
VCC
U1U1
Reference
Description
Part Number - Manufacturer
C1, C2
10 µF Capacitor Ceramic X7R 5750 15% 50 V
C5750X7R1H106MB - TDK
D1, D2, D3
Very Low Capacitance ESD Protection
PESD0402-140 - Tyco Electronics
U1
DC/DC Boost Regulator
Various Manufacturer
D+
D–
GND
28
USB_D+
27
USB_D–
GND
USB 3.0 DEVICE
CONNECTOR
VBUS
D+
D–
GND
USB 2.0 HOST
PROCESSOR
TOBY-L4 series
VBUS
4
VUSB_DET
D1 D2 D3
C1
C1
28
USB_D+
27
USB_D–
GND
TOBY-L4 series
4
VUSB_DET
168
USB_ID
168
USB_ID
170
USB_SSRX+
171
USB_SSRX–
175
USB_SSTX+
176
USB_SSTX–
170
USB_SSRX+
171
USB_SSRX–
175
USB_SSTX+
176
USB_SSTX–
SSRX+
SSRX–
SSTX+
SSTX–
C3
SSTX+
SSTX–
SSRX+
SSRX–
C2
Reference
Description
Part Number - Manufacturer
C1, C2, C3
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R61A104KA01 - Murata
D1, D2, D3
Very Low Capacitance ESD Protection
PESD0402-140 - Tyco Electronics
Figure 42: USB 2.0 interface application circuits, with TOBY-L4 series module acting as a USB host
Table 33: Component for USB 2.0 interface application circuits, with TOBY-L4 series module acting as a USB host
Figure 43: USB 3.0 interface application circuits, with TOBY-L4 series module acting as a USB device
Table 34: Component for USB 3.0 interface application circuits, with TOBY-L4 series module acting as a USB device
USB High-Speed 2.0 host role is not supported by the "50" product versions. USB Super-Speed 3.0 compliant interface will be supported by future firmware versions.
If the USB interface pins are not used, they can be left unconnected on the application board, but it is
recommended to provide accessible test points directly connected to the VUSB_DET, USB_D+, USB_D–
pins, for diagnostic and FW update purposes.
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TOBY-L4 series - System Integration Manual
35 µm
35 µm
35 µm
35 µm
270 µm
270 µm
760 µm
L1 Copper
L3 Copper
L2 Copper
L4 Copper
FR-4 dielectric
FR-4 dielectric
FR-4 dielectric
350 µm 400 µm400 µm350 µm400 µm
35 µm
35 µm
1510 µm
L2 Copper
L1 Copper
FR-4 dielectric
740 µm 410 µm410 µm740 µm410 µm
2.6.1.2 Guidelines for USB layout design
The USB_D+/USB_D–, USB_SSTX+/USB_SSTX– and USB_SSRX+/USB_SSRX– lines require accurate layout
design to achieve reliable signaling at the high speed data rates (up to 480 Mbit/s or up to 5 Gbit/s) supported by
the USB 2.0 or USB 3.0 interface.
The characteristic impedance of the USB_D+/USB_D–, USB_SSTX+/USB_SSTX– and USB_SSRX+/USB_SSRX–
lines is specified by the USB 2.0 specification [3] and the USB 3.0 specification [4]. The most important parameter
is the differential characteristic impedance applicable for the odd-mode electromagnetic field, which should be as
close as possible to 90 differential. Signal integrity may be degraded if the PCB layout is not optimal, especially
when the USB signaling lines are very long.
Use the following general routing guidelines to minimize signal quality problems:
Route USB_D+/USB_D–, USB_SSTX+/USB_SSTX– and USB_SSRX+/USB_SSRX– lines as a differential pair
Route USB_D+/USB_D–, USB_SSTX+/USB_SSTX– and USB_SSRX+/USB_SSRX– lines as short as possible
Ensure the differential characteristic impedance (Z
Ensure the common mode characteristic impedance (Z
) is as close as possible to 90
0
) is as close as possible to 30
CM
Consider design rules for USB_D+/USB_D–, USB_SSTX+/USB_SSTX– and USB_SSRX+/USB_SSRX– similar
to RF transmission lines, these being coupled differential micro-strip or buried stripline: avoid any stubs, abrupt
change of layout, and route on clear PCB area
Figure 44 and Figure 45 provide two examples of coplanar waveguide designs with differential characteristic
impedance close to 90 and common mode characteristic impedance close to 30 . The first transmission line
can be implemented for a 4-layer PCB stack-up herein illustrated; the second transmission line can be implemented
for a 2-layer PCB stack-up herein illustrated.
Figure 44: Example of USB line design, with Z0 close to 90 and ZCM close to 30 , for the described 4-layer board layup
Figure 45: Example of USB line design, with Z0 close to 90 and ZCM close to 30 , for the described 2-layer board layup
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TOBY-L4 series - System Integration Manual
TxD
1.8V Processor / Device
RxD
RTS
CTS
GND
TOBY-L4 series
TXDx
RXDx
RTSx
CTSx
GND
0Ω
TP
0Ω
TP
5
V_INT
TxD
3V Processor / Device
RxD
RTS
CTS
GND
TOBY-L4 series
TXDx
RXDx
RTSx
CTSx
GND
1V8
B1 A1
GND
U1
B3A3
VCCBVCCA
Unidirectional
Voltage Translator
C1
C2
3V0
DIR3
DIR2OE
DIR1
VCC
B2 A2
B4A4
DIR4
TP
0Ω
TP
0Ω
TP
Reference
Description
Part Number - Manufacturer
C1, C2
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R61A104KA01 - Murata
U1
Unidirectional Voltage Translator
SN74AVC4T77416 - Texas Instruments
16
2.6.2 UART interfaces
UART interfaces are not supported by the "50" product version, except for trace logging (diagnostic
purposes) and Ring Indicator functionality over the UART0 interface.
2.6.2.1 Guidelines for UART circuit design
4-wire UART
If RS-232 compatible signal levels are needed, the Maxim MAX13234E voltage level translator can be used. This
chip translates voltage levels from 1.8 V (module side) to the RS-232 standard.
If a 1.8 V external Processor / Device is used, the circuit should be implemented as illustrated in Figure 46.
Figure 46: 4-wire UART interface application circuit to connect an external 1.8 V processor / device
If a 3.0 V external Processor / Device is used, then it is recommended to connect the 1.8 V UART interface of the
module by means of appropriate unidirectional voltage translators using the module V_INT output as a 1.8 V
supply for the voltage translators on the module side, as illustrated in Figure 47.
Figure 47: 4-wire UART interface application circuit to connect an external 3.0V processor / device
Table 35: Component for 4-wire UART interface application circuit to connect an external 3.0V processor / device
Test-Points for diagnostic access are recommended to be provided on the UART0 TXD and RXD lines. They
are not required on other UART lines.
Voltage translator providing partial power down feature so that the external 3.0 V supply can be ramped up before the V_INT 1.8 V supply
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TOBY-L4 series - System Integration Manual
TxD
1.8V Processor / Device
RxD
GND
TOBY-L4 series
TXDx
RXDx
GND
0Ω
TP
0Ω
TP
5
V_INT
TxD
3V Processor / Device
RxD
GND
TOBY-L4 series
TXDx
RXDx
GND
1V8
B1 A1
GND
U1
VCCBVCCA
Unidirectional
Voltage Translator
C1
C2
3V0
DIR1
DIR2
OE
VCC
B2 A2
TP
0Ω
TP
0Ω
TP
Reference
Description
Part Number - Manufacturer
C1, C2
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R61A104KA01 - Murata
U1
Unidirectional Voltage Translator
SN74AVC2T24517 - Texas Instruments
17
2-wire UART
If the functionality of the CTSx and RTSx are not required in the application, or the lines are not available, then:
Consider to connect the module RTSx input line to GND or to the CTSx output line of the module, since the
module requires RTSx active (low electrical level) if HW flow-control is enabled
If RS-232 compatible signal levels are needed, the Maxim MAX13234E voltage level translator can be used. This
chip translates voltage levels from 1.8 V (module side) to the RS-232 standard.
If a 1.8 V external Processor / Device is used, the circuit that should be implemented as illustrated in Figure 48.
Figure 48: 2-wire UART interface application circuit to connect an external 1.8V processor / device
If a 3.0 V external Processor / Device is used, then it is recommended to connect the 1.8 V UART interface of the
module by means of appropriate unidirectional voltage translators using the module V_INT output as a 1.8 V
supply for the voltage translators on the module side, as illustrated in Figure 49.
Figure 49: 2-wire UART interface application circuit to connect an external 3.0 V processor / device
Table 36: Component for 2-wire UART interface application circuit to connect an external 3.0 V processor / device
Test-Points for diagnostic access are recommended to be provided on the UART0 TXD and RXD lines for
diagnostic purposes. Test-Points are not required on other UART lines.
Voltage translator providing partial power down feature so that the external 3.0 V supply can be ramped up before V_INT 1.8 V supply
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TOBY-L4 series - System Integration Manual
1.8V Processor / Device
RI
GND
TOBY-L4 series
11
RI
GND
5
V_INT
RI
3V Processor / Device
GND
TOBY-L4 series
11
RI
GND
1V8
B1 A1
GND
U1
VCCBVCCA
Unidi rectional
Voltage Translator
C1
C2
3V0
DIR2
OE
VCC
B2 A2
TP
DIR1
Reference
Description
Part Number - Manufacturer
C1, C2
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R61A104KA01 - Murata
U1
Unidirectional Voltage Translator
SN74AVC2T24518 - Texas Instruments
18
Ring Indicator
If a 1.8 V external Processor / Device is used, the Ring Indicator circuit should be implemented as illustrated in
Figure 50.
Figure 50: Ring Indicator application circuit to connect an external 1.8V processor / device
If a 3.0 V external Processor / Device is used, then it is recommended to connect the 1.8 V Ring Indicator output
of the module by means of appropriate unidirectional voltage translators using the module V_INT output as a
1.8 V supply for the voltage translator on the module side, as illustrated in Figure 51.
Figure 51: Ring Indicator application circuit to connect an external 3.0V processor / device
Table 37: Component for the Ring Indicator application circuit to connect an external 3.0V processor / device
Voltage translator providing partial power down feature so that the external 3.0 V supply can be ramped up before the V_INT 1.8 V supply
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TOBY-L4 series - System Integration Manual
Additional considerations
If a 3.0 V external Processor / Device is used, the voltage scaling from any 3.0 V output of the external Processor /
Device to the corresponding 1.8 V input of the module can be implemented as an alternative low-cost solution,
by means of an appropriate voltage divider. Consider the value of the pull-up integrated at the input of the module
for the correct selection of the voltage divider resistance values and mind that any DTE signal connected to the
module must be tri-stated or set low when the module is in power-down mode and during the module power-on
sequence (at least until the activation of the V_INT supply output of the module), to avoid latch-up of circuits and
allow a clean boot of the module (see the remark below).
Moreover, the voltage scaling from any 1.8 V output of the cellular module to the corresponding 3.0 V input of
the external Processor / Device can be implemented by means of an appropriate low-cost non-inverting buffer with
open drain output. The non-inverting buffer should be supplied by the V_INT supply output of the cellular module.
Consider the value of the pull-up integrated at each input of the external Processor / Device (if any) and the baud
rate required by the application for the appropriate selection of the resistance value for the external pull-up biased
by the application processor supply rail.
Do not apply voltage to any UART interfaces pin before the switch-on of the UART supply source (V_INT),
to avoid latch-up of circuits and allow a clean boot of the module.
The ESD sensitivity rating of UART interfaces pins is 1 kV (Human Body Model according to JESD22-A114).
A higher protection level could be required if the lines are externally accessible and it can be achieved by
mounting an ESD protection (e.g. EPCOS CA05P4S14THSG varistor array) close to the accessible points.
If the UART interfaces pins are not used, they can be left unconnected on the application board, but it is
recommended to provide accessible test points directly connected to the UART0 TXD and RXD pins for
diagnostic purposes.
2.6.2.2 Guidelines for UART layout design
The UART serial interface requires the same considerations regarding electro-magnetic interference as any other
digital interface. Keep the traces short and avoid coupling with RF line or sensitive analog inputs, since the signals
can cause the radiation of some harmonics of the digital data frequency.
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TOBY-L4 series - System Integration Manual
TOBY-L4 series
(Master, 1.8V)
SCLK
CS
MOSI
MISO
GND
SPI_SCLK
SPI_CS
SPI_MOSI
SPI_MISO
SPI Device
(Slave, 1.8V)
GND
SCLK
CS
MOSI
MISO
SPI Device
(Slave, 1.8V)
GND
GPIO4
2.6.3 SPI interfaces
SPI interfaces are not supported by the "50" product version.
2.6.3.1 Guidelines for SPI circuit design
TOBY-L4 series modules include up to two 1.8 V Serial Peripheral Interfaces to communicate with external SPI slave
devices, with the module acting as SPI master, by means of the uCPU API.
Figure 52 describes a possible application circuit for the SPI0 interface, where two SPI slave devices are connected
to the module using the two SPI0 Chip Select 0 (SPI_CS pin) and SPI0 Chip Select 1 (GPIO4 pin) to select the
specific SPI slave device.
The external SPI slave device must provide compatible voltage levels (1.80 V typ.), otherwise it is recommended to
connect the 1.8 V SPI interface of the module to the external 3.0 V (or similar) SPI device by means of appropriate
unidirectional voltage translators (e.g. TI SN74AVC4T774 or SN74AVC2T245, providing partial power down
feature so that the digital audio device 3.0 V supply can be also ramped up before V_INT 1.8 V supply), using the
module’sV_INT output as a 1.8 V supply for the voltage translators on the module side.
Figure 52: SPI interface application circuit for connecting two external SPI slave devices
2.6.3.2 Guidelines for SPI layout design
The SPI serial interface requires the same considerations regarding electro-magnetic interference as any other
digital interface. Keep the traces short and avoid coupling with RF line or sensitive analog inputs, since the signals
can cause the radiation of some harmonics of the digital data frequency.
UBX-16024839 - R04 Design-in
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Do not apply voltage to any SPI interface pins before the switch-on of the SPI supply source (V_INT), to
avoid latch-up of circuits and allow a clean boot of the module.
The ESD sensitivity rating of SPI interfaces pins is 1 kV (Human Body Model according to JESD22-A114).
A higher protection level could be required if the lines are externally accessible and it can be achieved by
mounting an ESD protection (e.g. EPCOS CA05P4S14THSG varistor array) close to the accessible points.
If the SPI interfaces pins are not used, they can be left unconnected on the application board.
TOBY-L4 series - System Integration Manual
1.8V I2C Device
SDA
SCL
1V8
5
V_INT
R1 R2
1V8 1V 8
SDAx
SCLx
TOBY-L4 series
R1 R2
3V0
SDAx
SCLx
R3 R4
1V8
SDA_A SDA_B
GND
U1
SCL_ASCL_B
VCCA
VCCB
I2C-bus Bidirectional
Voltage Translator
5
V_INT
C1C2
SDA
SCL
OE
GNDGND
3V I2C Device
TOBY-L4 series
GNDGND
Reference
Description
Part Number - Manufacturer
R1, R2, R3, R4
4.7 k Resistor 0402 5% 0.1 W
RC0402JR-074K7L - Yageo Phycomp
C1, C2
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C104KA01 - Murata
U1
I2C-bus Bidirectional Voltage Translator
TCA9406DCUR19 - Texas Instruments
19
2.6.4 DDC (I
DDC (I
2
C) interfaces
2
C) interfaces are not supported by the "50" product version.
2.6.4.1 General guidelines for DDC (I
2
C) circuit design
The DDC I2C-bus pins of the module are open drain outputs conforming to the I2C bus specifications [6]. External
pull-up resistors to a suitable 1.8 V supply (e.g. V_INT) are required for operations: for example, 4.7 k resistors
can be commonly used.
Connect the DDC (I
2
C) pull-ups to the V_INT 1.8 V supply source, or another 1.8 V supply source enabled
after V_INT (e.g., as the GNSS 1.8 V supply present in Figure 54 application circuit), as any external signal
connected to the DDC (I2C) interface must not be set high before the switch-on of the V_INT supply of DDC
(I2C) pins, to avoid latch-up of circuits and allow a clean boot of the module.
The signal shape is defined by the values of the pull-up resistors and the bus capacitance. Long wires on the bus
will increase the capacitance. If the bus capacitance is increased, use pull-up resistors with a nominal resistance
value lower than 4.7 k, to match the I2C bus specifications [6] regarding the rise and fall times of the signals.
Figure 53 and Table 38 describe typical application circuits for connecting TOBY-L4 series modules to 1.8 V I2C
devices (see Figure 53 top side) or 3 V I2C devices (see Figure 53 bottom side).
Figure 53: Application circuit for connecting TOBY-L4 series modules to 1.8 V or 3 V I2C devices
Table 38: Components for connecting TOBY-L4 series modules to 1.8 V or 3 V I2C devices
The ESD sensitivity rating of the DDC (I
A higher protection level could be required if the lines are externally accessible and it can be achieved by
mounting an ESD protection (e.g. EPCOS CA05P4S14THSG varistor array) close to the accessible points.
If the pins are not used as DDC bus interface, they can be left unconnected.
Voltage translator providing partial power down feature so that the external 3 V supply can be also ramped up before V_INT 1.8 V supply
UBX-16024839 - R04 Design-in
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2
C) pins is 1 kV (Human Body Model according to JESD22-A114).
TOBY-L4 series - System Integration Manual
R1
IN
OUT
GND
GNSS LDO
Regulator
SHDNn
u-blox GNSS
1.8 V receiver
SDA2
SCL2
R2
1V8 1V8
VMAIN1V8
U1
22
GPIO2
SDA
SCL
C1
TxD1GPIO3
55
54
24
VCC
R3
GNSS Tx data ready
GNSS supply enabled
TOBY-L4 series
EXTINT0GPIO4
25
GNSS RTC sharing
Reference
Description
Part Number - Manufacturer
R1, R2
4.7 k Resistor 0402 5% 0.1 W
RC0402JR-074K7L - Yageo Phycomp
R3
47 k Resistor 0402 5% 0.1 W
RC0402JR-0747KL - Yageo Phycomp
U1, C1
Voltage Regulator for GNSS receiver and capacitor
See GNSS receiver Hardware Integration Manual
Connection with u-blox 1.8 V GNSS receivers
Figure 54 shows an application circuit for connecting the cellular modules to a u-blox 1.8 V GNSS receiver.
SDA / SCL pins of the cellular module are directly connected to the relative I
2
C pins of the u-blox 1.8 V GNSS
receiver, with appropriate pull-up resistors connected to the 1.8 V GNSS supply enabled after the V_INT supply
of the I2C pins of the cellular module.
GPIO2 pin is connected to the shutdown input pin (SHDNn) of the LDO regulators providing the 1.8 V supply
rail for the u-blox 1.8 V GNSS receiver implementing the “GNSS enable” function, with an appropriate pulldown resistor mounted on the GPIO2 line to avoid an improper switch-on of the u-blox GNSS receiver.
GPIO3 and GPIO4 pins are directly connected respectively to the TXD1 and EXTINT0 pins of the u-blox 1.8 V
GNSS receiver providing “GNSS Tx data ready” and “GNSS RTC sharing” functions.
Figure 54: Application circuit for connecting TOBY-L4 series modules to u-blox 1.8 V GNSS receivers
Table 39: Components for connecting TOBY-L4 series modules to u-blox 1.8 V GNSS receivers
Custom functions over GPIO pins, to improve the integration with u-blox positioning chips and modules,
will be supported by future firmware versions.
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TOBY-L4 series - System Integration Manual
u-blox GNSS
1.8 V receiver
TxD1
SDA2
SCL2
VCC
1V8
C1
R3
5
V_INT
R5
R4
TP
T2
T1
R1 R2
1V8 1V8
GNSS data ready
GNSS supply enabled
22
GPIO2
SDA
SCL
GPIO3
55
54
24
TOBY-L4 series
EXTINT0GPIO4
25
GNSS RTC sharing
Reference
Description
Part Number - Manufacturer
R1, R2
4.7 k Resistor 0402 5% 0.1 W
RC0402JR-074K7L - Yageo Phycomp
R3
47 k Resistor 0402 5% 0.1 W
RC0402JR-0747KL - Yageo Phycomp
R4
10 k Resistor 0402 5% 0.1 W
RC0402JR-0710KL - Yageo Phycomp
R5
100 k Resistor 0402 5% 0.1 W
RC0402JR-07100KL - Yageo Phycomp
T1
P-Channel MOSFET Low On-Resistance
IRLML6401 - International Rectifier or NTZS3151P - ON Semi
T2
NPN BJT Transistor
BC847 - Infineon
C1
100 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C104KA01 - Murata
Figure 55 illustrates an alternative application circuit solution in which the cellular module supplies a u-blox 1.8 V
GNSS receiver. The V_INT 1.8 V regulated supply output of the cellular module can be used as supply source for
a u-blox 1.8 V GNSS receiver (u-blox 6 generation receiver or newer) instead of using an external voltage regulator,
as shown in Figure 54. The V_INT supply is able to support the maximum current consumption of these positioning
receivers.
The internal switching step-down regulator that generates the V_INT supply is set to 1.8 V (typical) when the
cellular module is switched on and it is disabled when the module is switched off.
The supply of the u-blox 1.8 V GNSS receiver can be switched off using an external p-channel MOS controlled by
the GPIO2 pin of the cellular modules by means of a suitable inverting transistor as shown in Figure 55,
implementing the “GNSS supply enable” function. If this feature is not required, the V_INT supply output can be
directly connected to the u-blox 1.8 V GNSS receiver, so that it will switch on when V_INT output is enabled.
According to the V_INT supply output voltage ripple characteristic specified in the TOBY-L4 seriesData Sheet [1]:
Additional filtering may be needed to properly supply an external LNA, depending on the characteristics of
the used LNA, adding a series ferrite bead and a bypass capacitor (e.g. the Murata BLM15HD182SN1 ferrite
bead and the Murata GRM1555C1H220J 22 pF capacitor) at the input of the external LNA supply line.
Figure 55: Application circuit for connecting TOBY-L4 series modules to u-blox 1.8 V GNSS receivers using V_INT as supply
Table 40: Components for connecting TOBY-L4 series modules to u-blox 1.8 V GNSS receivers using V_INT as supply
Custom functions over GPIO pins, to improve the integration with u-blox positioning chips and modules,
will be supported by future firmware versions.
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TOBY-L4 series - System Integration Manual
u-blox GNSS
3.0 V receiver
24
GPIO3
1V8
B1 A1
GND
U3
B2A2
VCCBVCCA
Unidirectional
Voltage Translator
C4
C5
3V0
TxD1
R1
INOUT
GNSS LDO Regulator
SHDNn
R2
VMAIN3V0
U1
22
GPIO2
55
SDA
54
SCL
R4 R5
1V8
SDA_A SDA_B
GND
U2
SCL_ASCL_B
VCCA
VCCB
I2C-bus Bidirectional
Voltage Translator
5
V_INT
C1
C2C3
R3
SDA2
SCL2
VCC
DIR1
DIR2OEn
OE
GNSS data ready
GNSS supply enabled
GND
TOBY-L4 series
EXTINT0GPIO4
25
GNSS RTC sharing
Reference
Description
Part Number - Manufacturer
R1, R2, R4, R5
4.7 k Resistor 0402 5% 0.1 W
RC0402JR-074K7L - Yageo Phycomp
R3
47 k Resistor 0402 5% 0.1 W
RC0402JR-0747KL - Yageo Phycomp
C2, C3, C4, C5
100 nF Capacitor Ceramic X5R 0402 10% 10V
GRM155R71C104KA01 - Murata
U1, C1
Voltage Regulator for GNSS receiver and capacitor
See GNSS receiver Hardware Integration Manual
U2
I2C-bus Bidirectional Voltage Translator
TCA9406DCUR - Texas Instruments
U3
Generic Unidirectional Voltage Translator
SN74AVC2T245 - Texas Instruments
Connection with u-blox 3.0 V GNSS receivers
Figure 56 shows an application circuit for connecting the cellular modules to a u-blox 3.0 V GNSS receiver:
As the SDA and SCL pins of the cellular module are not tolerant up to 3.0 V, the connection to the related
I2C pins of the u-blox 3.0 V GNSS receiver must be provided using a suitable I2C-bus Bidirectional Voltage
Translator with appropriate pull-up resistors (e.g. the TI TCA9406 additionally provides the partial power down
feature so that the GNSS 3.0 V supply can be ramped up before the V_INT 1.8 V cellular supply).
GPIO2 pin is connected to the shutdown input pin (SHDNn) of the LDO regulators providing the 3.0 V supply
rail for the u-blox 3.0 V GNSS receiver implementing the “GNSS enable” function, with an appropriate pulldown resistor mounted on the GPIO2 line to avoid an improper switch-on of the u-blox GNSS receiver.
As the GPIO3 and GPIO4 pins of the cellular module are not tolerant up to 3.0 V, the connection to the
related pins of the u-blox 3.0 V GNSS receiver must be provided using a suitable Unidirectional General Purpose
Voltage Translator (e.g. TI SN74AVC2T245, which additionally provides the partial power down feature so
that the 3.0 V GNSS supply can be also ramped up before the V_INT 1.8 V cellular supply).
Figure 56: Application circuit for connecting TOBY-L4 series modules to u-blox 3.0 V GNSS receivers
Table 41: Components for connecting TOBY-L4 series modules to u-blox 3.0 V GNSS receivers
Custom functions over GPIO pins, to improve the integration with u-blox positioning chips and modules,
will be supported by future firmware versions.
2.6.4.2 Guidelines for DDC (I
The DDC (I2C) serial interface requires the same considerations regarding electro-magnetic interference as any
other digital interface. Keep the traces short and avoid coupling with RF line or sensitive analog inputs, since the
signals can cause the radiation of some harmonics of the digital data frequency.
UBX-16024839 - R04 Design-in
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2
C) layout design
TOBY-L4 series - System Integration Manual
R2
LDO regulator
EMMY-W161
Wi-Fi module
3V3VCC
U1
C1
R1
SD_D0
19
SD_D1
20
SD_D2
21
SD_D3
22
SD_CLK
17
SD_CMD
18
OUTIN
SENSE
BYP
SHDNn
GND
TOBY-L4 series
cellular module
SDIO_D0
66
SDIO_D1
68
SDIO_D2
63
SDIO_D3
67
SDIO_CLK
64
SDIO_CMD
65
V_INT
5
C3
3V3
25
C5
LDO regulator 1V8VCC
U2
C2
OUTIN
SENSE
BYP
SHDNn
GND
C4
VIO1
26
C6
VIO2
27
R3
R4
R5
R6
R7
ANT1
45
ANT2
40
Wi-Fi
antenna
Wi-Fi enable
PDn
28
GPIO1
21
GNDGND
3V3
Open Drain Buffer
R8
2.6.5 SDIO interface
The SDIO interface is not supported by the "50" product version.
2.6.5.1 Guidelines for SDIO circuit design
TOBY-L4 series modules include a 4-bit Secure Digital Input Output interface (SDIO_D0, SDIO_D1, SDIO_D2,
SDIO_D3, SDIO_CLK, SDIO_CMD), where the module acts as an SDIO host controller designed to
communicate with compatible u-blox short range radio communication modules by means of the uCPU API
communicate with external SDIO devices by means of the uCPU API
Connection with u-blox short range radio communication modules
Figure 58 and Table 43 show an application circuit for connecting TOBY-L4 series cellular modules to u-blox
EMMY-W161 short range radio communication modules supporting IEEE 802.11a/b/g/n/ac data rates for Wi-Fi:
The SDIO pins of the cellular module are connected to the related SDIO pins of the u-blox EMMY-W161 short
range radio communication module, with appropriate low value series damping resistors to avoid reflections
and other losses in signal integrity, which may create ringing and loss of a square wave shape.
The most appropriate value for the series damping resistors on the SDIO lines depends on the specific line
lengths and layout implemented. In general, the SDIO series resistors are not strictly required, but it is
recommended to slow the SDIO signal, for example with 22 or 33 resistors, and avoid any possible ringing
problem without violating the rise / fall time requirements.
The V_INT supply output pin of the cellular module is connected to the shutdown input pin (SHDNn) of the
two LDO regulators providing the 3.3 V and 1.8 V supply rails for the u-blox EMMY-W161 module, with
appropriate pull-down resistors to avoid an improper switch-on of the Wi-Fi module before the switch-on of
the V_INT supply source of the cellular module SDIO interface pins.
The GPIO1 pin of the cellular module is connected to the active low full power down input pin (PDn) of the
u-blox EMMY-W161 module, implementing the Wi-Fi enable function.
The WLAN antenna RF input/output (ANT1) of the u-blox EMMY-W161 Wi-Fi module is directly connected to
a Wi-Fi antenna considering that the u-blox EMMY-W161 module integrates a 2.4 GHz BAW band pass filter
that enables co-existence with LTE RF signals.
Figure 57: Application circuit for TOBY-L4 cellular module and u-blox EMMY-W161 short range radio communication module
UBX-16024839 - R04 Design-in
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TOBY-L4 series - System Integration Manual
Reference
Description
Part Number - Manufacturer
C1, C2
1 µF Capacitor Ceramic X7R 0603 10% 25 V
GRM188R71E105KA12 - Murata
C3, C4
10 nF Capacitor Ceramic X7R 0402 10% 16 V
GRM155R71C103KA01 - Murata
C5, C6
10 µF Capacitor Ceramic X5R 0603 20% 6.3 V
GRM188R60J106ME47 - Murata
R1
470 k Resistor 0402 5% 0.1 W
RK73B1ETTD474J - KOA
R2, R3, R4, R5, R6, R7
22 Resistor 0402 5% 0.1 W
RK73B1ETTP220J - KOA
R8
47 k Resistor 0402 5% 0.1 W
RK73B1ETTD473J - KOA
R9
47 k Resistor 0402 5% 0.1 W
RK73B1ETTD473J - KOA
U1
LDO Linear Regulator 3.3 V 0.5 A
LT1963CS8-3.3 - Linear Technology
U2
LDO Linear Regulator 1.8 V 0.3 A
LT1962EMS8-1.8 - Linear Technology
R2
SDIO Device
SD_D0
SD_D1
SD_D2
SD_D3
SD_CLK
SD_CMD
TOBY-L4 series
SDIO_D0
66
SDIO_D1
68
SDIO_D2
63
SDIO_D3
67
SDIO_CLK
64
SDIO_CMD
65
R3
R4
R5
R6
GNDGND
R1
Reference
Description
Part Number - Manufacturer
R1, R2, R3, R4, R5, R6
22 Resistor 0402 5% 0.1 W
RK73B1ETTP220J - KOA
Table 42: Components for connecting TOBY-L4 cellular modules and u-blox EMMY-W161 short range communication modules
Connection with external SDIO devices
Figure 58 and Table 43 show an application circuit example for connecting the SDIO interface of TOBY-L4 series
modules to a 1.8 V SDIO device: the SDIO pins of the cellular module are connected to the related SDIO pins of
the SDIO device, with appropriate low value series damping resistors to avoid reflections and other losses in signal
integrity, which may create ringing and loss of a square wave shape.
The most appropriate value for the series damping resistors on the SDIO lines depends on the specific line lengths
and layout implemented. In general, the SDIO series resistors are not strictly required, but it is recommended to
slow the SDIO signal, for example with 22 or 33 resistors, and avoid any possible ringing problem without
violating the rise / fall time requirements.
Figure 58: Application circuit for connecting TOBY-L4 series modules to a 1.8 V SDIO device
Table 43: Components for connecting TOBY-L4 series modules to a 1.8 V SDIO device
The ESD sensitivity rating of SDIO interface pins is 1 kV (HMB according to JESD22-A114). A higher
If the SDIO interface pins are not used, they can be left unconnected on the application board.
2.6.5.2 Guidelines for SDIO layout design
The SDIO serial interface requires the same considerations regarding electro-magnetic interference as any other
high speed digital interface.
Keep the traces short, avoid stubs and avoid coupling with RF lines / parts or sensitive analog inputs, since the
signals can cause the radiation of some harmonics of the digital data frequency.
Consider the usage of low value series damping resistors to avoid reflections and other losses in signal integrity,
which may create ringing and loss of a square wave shape.
UBX-16024839 - R04 Design-in
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protection level could be required if the lines are externally accessible and this can be achieved by mounting
a very low capacitance ESD protection (e.g. Tyco Electronics PESD0402-140 ESD) close to the accessible
points.
TOBY-L4 series - System Integration Manual
TOBY-L4 series
Ethernet
MAC
RGMII
Connector
Ethernet
PHY
Unshielded Twisted Pair
2.6.6 RGMII interface
The RGMII interface is not supported by the "50" product version.
2.6.6.1 Guidelines for RGMII circuit design
TOBY-L4 series modules include an Ethernet Media Access Control (MAC) block supporting up to 1 Gbit/s data
rate via a Reduced Gigabit Media-Independent Interface compliant with the RGMII Version 1.3 specification [7]
and the RMII Revision 1.2 specification [8].
The module represents an Ethernet MAC controller, which can be connected to a compatible external Ethernet
physical transceiver (PHY) chip to provide communication over Ethernet as illustrated in Figure 59.
The ESD sensitivity rating of RGMII interface pins is 1 kV (HMB according to JESD22-A114). A higher
protection level could be required if the lines are externally accessible and it can be achieved by mounting
a very low capacitance ESD protection (e.g. Tyco Electronics PESD0402-140 ESD) close to the accessible
points.
If the RGMII interface pins are not used, they can be left unconnected on the application board.
2.6.6.2 Guidelines for RGMII layout design
The RGMII / RMII interface requires the same considerations regarding electro-magnetic interference as any other
high speed digital interface.
Keep the traces short, avoid stubs and avoid coupling with RF lines / parts or sensitive analog inputs, since the
signals can cause the radiation of some harmonics of the digital data frequency.
Consider the usage of low value series damping resistors to avoid reflections and other losses in signal integrity,
which may create ringing and loss of a square wave shape.
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