Texas Instruments Incorporated AN-1985 User's Guide

VIN (V)

EFFICIENCY (%)

100

95
90
85
80
75
70

0 16 32 48 64 80

1 Introduction

This wide range evaluation board showcases the LM3429 NFET controller used with a buck-boost current
regulator. It is designed to drive 4 to 8 LEDs at a maximum average LED current of 1A from a DC input
voltage of 10 to 70V.

The evaluation board showcases most features of the LM3429 including PWM dimming, overvoltage
protection and input under-voltage lockout. It also has a right angle connector (J7) which can mate with an
external LED load board allowing for the LEDs to be mounted close to the driver. Alternatively, the LED+
and LED- banana jacks can be used to connect the LED load.

The buck-boost circuit can be easily redesigned for different specifications by changing only a few
components (see Alternate Designs). Note that design modifications can change the system efficiency for
better or worse. See the LM3429 LM3429Q1 N-Channel Controller for Constant Current LED Drivers
(SNVS616) data sheet for a comprehensive explanation of the device and application information.

User's Guide

SNVA403C–July 2009–Revised May 2013

AN-1985 LM3429 Buck-Boost Evaluation Board

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SNVA403C–July 2009–Revised May 2013 AN-1985 LM3429 Buck-Boost Evaluation Board

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Figure 1. Efficiency with 6 Series LEDS AT 1A

1

Copyright © 2009–2013, Texas Instruments Incorporated

D1

OVP

LM3429

nDIM

PGND

NC

DAP

GATE

COMP

CSH

RCT

IS

HSN

HSP

L1

C9

R6

Q1

R1

C7

R13

R5

1

2

3

4

5

6

7

14

13

12

11

10

9

8

R7

R8

AGND

R10

Q3

R4

PWM

Q5

R18

R11

V

IN

R9

R20

C12

V

IN

V

CC

LED-

1
2
3

5
6
7

14
13
12

10

9
8

J7

LED+

V

IN

GND

V

IN

C8

R2

R3

C1

C2, C3,
C16, C18

C4, C6,
C17, C19

R12

4

11

TP7

TP10

TP1

TP2

TP3

TP11

TP12

J1

J2

J4

J5

U1

Schematic

2 Schematic

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AN-1985 LM3429 Buck-Boost Evaluation Board SNVA403C–July 2009–Revised May 2013

Figure 2. Board Schematic

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3 Pin Descriptions

Pin Name Description Application Information

1 V
2 COMP Compensation Connect a capacitor to AGND.

3 CSH Current Sense High dimming, connect a controlled current source or a potentiometer

4 RCT Resistor Capacitor Timing

5 AGND Analog Ground

6 OVP Over-Voltage Protection voltage lockout (OVLO). Turn-off threshold is 1.24V and

7 nDIM Not DIM input

8 NC No Connection Leave open.
9 PGND Power Ground

10 GATE Gate Drive Output Connect to the gate of the external NFET.
11 V

12 IS Main Switch Current Sense R

13 HSP

14 HSN

DAP Star ground, connecting AGND and PGND.

(15)

IN

CC

DAP Thermal pad on bottom of IC

Pin Descriptions

Input Voltage

Internal Regulator Output Bypass with a 2.2 µF–3.3 µF, ceramic capacitor to PGND.

High-Side LED Current Sense Connect through a series resistor to the positive side of the LED

Positive current sense resistor.

High-Side LED Current Sense Connect through a series resistor to the negative side of the

Negative LED current sense resistor.

Bypass with 100 nF capacitor to AGND as close to the device as
possible in the circuit board layout.

Connect a resistor to AGND to set the signal current. For analog
to AGND as detailed in the Analog Dimming section.

Connect a resistor from the switch node and a capacitor to
AGND to set the switching frequency.

Connect to PGND through the DAP copper circuit board pad to
provide proper ground return for CSH, COMP, and RCT.

Connect to a resistor divider from VOto program output over­hysteresis for turn-on is provided by 20 µA current source.

Connect a PWM signal for dimming as detailed in the PWM
Dimming section and/or a resistor divider from VINto program
input under-voltage lockout (UVLO). Turn-on threshold is 1.24V
and hysteresis for turn-off is provided by 20 µA current source.

Connect to AGND through the DAP copper circuit board pad to
provide proper ground return for GATE.

Connect to the drain of the main N-channel MosFET switch for

sensing or to a sense resistor installed in the source of

DS-ON

the same device.

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3

Bill of Materials

4 Bill of Materials

Qty Part ID Part Value Manufacturer Part Number

2 C1, C4 0.1 µF X7R 10% 100V TDK C2012X7R2A104K
4 C2, C3, C16, C18 4.7 µF X7R 10% 100V MURATA GRM55ER72A475KA01L
3 C6, C17, C19 2.2 µF X7R 10% 100V TDK C4532X7R2A225K
1 C7 1000 pF COG/NPO 5% 50V MURATA GRM2165C1H102JA01D
1 C8 1 µF X7R 10% 16V MURATA GRM21BR71C105KA01L
1 C9 2.2 µF X7R 10% 16V MURATA GRM21BR71C225KA12L
1 C12 0.1 µF X7R 10% 25V MURATA GRM21BR71E104KA01L
1 D1 Schottky 100V 12A VISHAY 12CWQ10FNPBF
4 J1, J2, J4, J5 banana jack KEYSTONE 575-8
1 J7 2 x 7 shrouded header SAMTEC TSSH-107-01-SDRA
1 L1 33 µH 20% 6.3A COILCRAFT MSS1278-333MLB
1 Q1 NMOS 100V 40A VISHAY SUD40N10-25
1 Q3 NMOS 60V 260 mA ON-SEMI 2N7002ET1G
1 Q5 PNP 150V 600 mA FAIRCHILD MMBT5401
1 R1 12.4 kΩ 1% VISHAY CRCW080512k4FKEA
1 R2 0Ω 1% VISHAY CRCW08050000Z0EA
2 R3, R20 10Ω 1% VISHAY CRCW080510R0FKEA
1 R4 16.9 kΩ 1% VISHAY CRCW080516k9FKEA
1 R5 1.43 kΩ 1% VISHAY CRCW08051k43FKEA
1 R6 0.05Ω 1% 1W VISHAY WSL2512R0500FEA
2 R7, R8 1.0 kΩ 1% VISHAY CRCW08051k00FKEA
1 R9 0.1Ω 1% 1W VISHAY WSL2512R1000FEA
1 R10 35.7 kΩ 1% VISHAY CRCW080535k7FKEA
1 R11 15.8 kΩ 1% VISHAY CRCW080515k8FKEA
2 R12, R13 10.0 kΩ 1% VISHAY CRCW080510k0FKEA
1 R18 750 kΩ 1% VISHAY CRCW0805750kFKEA
7 TP1, TP2, TP3, turret KEYSTONE 1502-2

1 U1 Buck-boost controller TI LM3429

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TP7, TP10, TP11,

TP12

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5 PCB Layout

PCB Layout

Figure 3. Top Layer

Figure 4. Bottom Layer

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5

2525

=

35.7 k: x 1 nF

fSW =

R10 x C7

= 700 kHz

2525

=

700 kHz x 1 nF

= 35.7 k:

R10 =

fSW x C7

21V

=

21V + 10V

= 0.677

D

MAX

=

VO + V

IN-MIN

V

O

21V

=

21V + 70V

= 0.231

D

MIN

=

VO + V

IN-MAX

V

O

D' = 1 - D = 1 - 0.467 = 0.533

D =

=

21V

VO + V

IN

21V + 24V

= 0.467

V

O

rD = N x r

LED

= 6 x 325 m: = 1.95:

VO = N x V

LED

= 6 x 3.5V = 21V

Design Procedure

6 Design Procedure

Refer to the LM3429 LM3429Q1 N-Channel Controller for Constant Current LED Drivers (SNVS616) data
sheet for design considerations.

6.1 Specifications

N = 6
V

= 3.5V

LED

r

= 325 mΩ

LED

VIN= 24V
V

= 10V; V

IN-MIN

fSW= 700 kHz
V

= 100 mV

SNS

I

= 1A

LED

Δi

= 500 mA

L-PP

Δi
Δv

I

LIM

V
V

LED-PP

IN-PP

= 5A

TURN-ON

TURN-OFF

= 50 mA

= 100 mV

= 10V; V

IN-MAX

= 60V; V

HYS

HYSO

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= 70V

= 3V

= 15V

6.2 Operating Point

Solve for VOand rD:

Solve for D, D', D

MAX

, and D

6.3 Switching Frequency

Assume C7 = 1 nF and solve for R10:

The closest standard resistor is actually 35.7 kΩ therefore the fSWis:

MIN

(1)
(2)

:

(3)
(4)

(5)

(6)

(7)

The chosen components from step 2 are:

6

AN-1985 LM3429 Buck-Boost Evaluation Board SNVA403C–July 2009–Revised May 2013

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(8)

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1A x 0.467

1.95: x 50 mA x 700 kHz

= 6.84 PF

CO =

CO =

rD x 'i

LED-PP

x f

SW

I

LED

x D

L1 = 33 PH

485 mA x 0.533

1A

I

L-RMS

=

I

LED

D'

I

L-RMS

=

1A

0.533

I

L-RMS

= 1.88A

I

LED

'I

L-PP

x D'

2

¸

¸
¹

·

¨

¨
©

§

¸

¸
¹

·

¨

¨
©

§

1 +

12

1

x

1 +

12

1

x

2

x

x

24V x 0.467

=

33 PH x 700 kHz

= 485 mA

'i

L-PP

=

L1 x f

SW

VIN x D

24V x 0.467

=

500 mA x 700 kHz

= 32 PH

L1 =

'i

L-PP

x f

SW

VIN x D

R8 = R7 = 1 k:

R1 = 12.4 k:

R9 = 0.1:

1.24V x 1.0 k:

=

= 1.0A

LED

=

1.24V x R8
R9 x R1

0.1: x 12.4 k:

1A x 12.4 k: x 0.1:

=

1.24V

= 1.0 k:

R8 =

I

LED

x R1 x R9

1.24V

30100815

100 mV

=

1A

= 0.1:

V

SNS

I

C7 = 1 nF

R10 = 35.7 k:

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6.4 Average LED Current

Solve for R9:

Assume R1 = 12.4 kΩ and solve for R8:

The closest standard resistor for R9 is 0.1Ω and the closest for R8 (and R7) is actually 1 kΩ therefore I
is:

The chosen components from step 3 are:

Design Procedure

(9)

(10)

(11)

LED

(12)

(13)

6.5 Inductor Ripple Current

Solve for L1:

The closest standard inductor is 33 µH therefore the actual Δi

Determine minimum allowable RMS current rating:

The chosen component from step 4 is:

6.6 Output Capacitance

L-PP

(14)

is:

(15)

(16)

(17)

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Solve for CO:

Copyright © 2009–2013, Texas Instruments Incorporated

A total value of 6.6 µF (using 3 2.2 µF X7R ceramic capacitors) is chosen therefore the actual Δi

LED-PP

(18)

is:

7

=

= 0.13 PF

C8 =

1

rad

sec

Z

P2

x 5e

6

:

1

1.596 x 5e

6

:

Z

Z1

=

5 x 4510

= 1.596

Z

P2

=

5 x T

U0

min(ZP1, ZZ1)

rad

sec

=

5 x 4510

36k

rad

sec

0.533 x 620V

=

1.467 x 1A x 0.05:

= 4510

TU0 =

(1 + D) x I

LED

x R6

D' x 620V

1.95: x 0.533

2

=

0.467 x 33 PH

= 36k

Z

Z1

=

D x L1

rD x D'

2

rad

sec

1.467

=

1.95: x 6.8 PF

= 110k

Z

P1

=

rD x C

O

1 + D

rad

sec

R6 = 0.05:

=

0.05:

= 4.9A

I

LIM

=

R6

245 mV 245 mV

=

5A

= 0.049:

R6 =

I

LIM

245 mV 245 mV

C6 = C17 = C19 = 2.2 PF

1- 0.677

= 1.45A

1 - D

MAX

D

MAX

I

CO-RMS

= I

LED

x

= 1A x

0.677

1A x 0.467

1.95: x 6.6 PF x 700 kHz

= 52 mA

'i

LED-PP

=

rD x CO x f

SW

I

LED

x D

'i

LED-PP

=

Design Procedure

Determine minimum allowable RMS current rating:

The chosen components from step 5 are:

6.7 Peak Current Limit

Solve for R6:

The closest standard resistor is 0.05 Ω therefore I

The chosen component from step 6 is:

LIM

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(19)

(20)

(21)

(22)

is:

(23)

6.8 Loop Compensation

ω

is approximated:

P1

ω

is approximated:

Z1

TU0is approximated:

To ensure stability, calculate ωP2:

Solve for C8:

Since PWM dimming can be evaluated with this board, a much larger compensation capacitor C8 = 1.0 µF
is chosen.

To attenuate switching noise, calculate ωP3:

(24)

(25)

(26)

(27)

(28)

(29)

8

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I

D-MAX

= I

LED

= 1A

V

RD-MAX

= V

IN-MAX

+ VO = 70V + 21V = 91V

Q1 o 40A, 100V, DPAK

PT = I

T-RMS

2

x R

DSON

= 1.28A2 x 50 m: = 82 mW

x x

1A

D =

0.533

T-RMS

=

I

LED

D'

0.467 = 1.28A

0.677

1 - 0.677

x 1A = 2.1A

I

T-MAX

=

V

T-MAX

= V

IN-MAX

+ VO = 70V + 21V = 91V

C2 = C3 = C16 = C18 = 4.7 PF

1- 0.677

= 1.45A

1 - D

MAX

D

MAX

I

IN-RMS

= I

LED

x

= 1A x

0.677

1A x 0.467

=

100 mV x 700 kHz

= 6.66 PF

CIN =

'V

IN-PP

x f

SW

I

LED

x D

C8 = 1.0 PF
R20 = 10:
C12 = 0.1 PF

=

= 0.091 PF

C12 =

1

rad
sec

1

10: x 1.1M

10: x Z

P3

rad

sec

Z

P3

= 110k x 10 = 1.1M

Z

P3

= max (ZP1, ZZ1) x 10 = ZP1 x 10

rad

sec

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Assume R20 = 10Ω and solve for C12:

The chosen components from step 7 are:

6.9 Input Capacitance

Solve for the minimum CIN:

To minimize power supply interaction a 3x larger capacitance of approximately 20 µF is used, therefore
the actual Δv
capacitors are chosen.

Determine minimum allowable RMS current rating:

is much lower. Since high voltage ceramic capacitor selection is limited, four 4.7 µF X7R

IN-PP

Design Procedure

(30)

(31)

(32)

(33)

The chosen components from step 8 are:

6.10 NFET

Determine minimum Q1 voltage rating and current rating:

A 100V NFET is chosen with a current rating of 40A due to the low R
PT:

The chosen component from step 9 is:

6.11 Diode

Determine minimum D1 voltage rating and current rating:

= 50 mΩ. Determine I

DS-ON

T-RMS

(34)

(35)

(36)

(37)

and

(38)
(39)

(40)

A 100V diode is chosen with a current rating of 12A and VD= 600 mV. Determine PD:

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(41)
(42)

9

Copyright © 2009–2013, Texas Instruments Incorporated

1.24V x R18

V

TURN-OFF

- 1.24V

= 15.8 k:

R11 = =

1.24V x 750 k:
60V - 1.24V

V

HYSO

= R18 x 20 PA = 750 k: x 20 PA = 15V

V

HYSO

20 PA

= 750 k:

R18 =

15V

=

20 PA

R4 = 16.9 k:

R13 = 10 k:

R5 = 1.43 k:

HYS

=

R5

20 PA x 16.9 k: x (1.43 k: + 10 k:)

1.43 k:

HYS

=

+ 20 PA x R

UV2

20 PA x R4 x (R5 + R13)

+ 20 PA x 10 k: = 2.9V

R4 =

R5 x (V

HYS

- 20 PA x R13)

20 PA x (R5 + R13)

= 16.9 k:

R4 =

1.43 k: x (2.9V - 20 PA x 10 k:)
20 PA x (1.43 k: + 10 k:)

V

TURN-ON

=

R5

1.24V x (1.43 k: + 10 k:)

1.43 k:

1.24V x (R5 + R13)

= 9.91V

V

TURN-ON

=

1.24V x R13

V

TURN-ON

- 1.24V

= 1.42 k:

R5 = =

1.24V x 10 k:
10V - 1.24V

D1 o 12A, 100V, DPAK

PD = ID x VFD = 1A x 600 mV = 600 mW

Design Procedure

The chosen component from step 10 is:

6.12 Input UVLO

Since PWM dimming will be evaluated, a three resistor network will be used. Assume R13 = 10 kΩ and
solve for R5:

The closest standard resistor is 1.43 kΩ therefore V

Solve for R4:

TURN-ON

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(43)

(44)

(45)

is:

(46)

The closest standard resistor is 16.9 kΩ making V

The chosen components from step 11 are:

6.13 Output OVLO

Solve for R18:

The closest standard resistor is 750 kΩ therefore V

Solve for R11:

HYS

:

HYSO

(47)

(48)

(49)

(50)

is:

(51)

The closest standard resistor is 15.8 kΩ making V

10

AN-1985 LM3429 Buck-Boost Evaluation Board SNVA403C–July 2009–Revised May 2013

TURN-OFF

Copyright © 2009–2013, Texas Instruments Incorporated

:

(52)

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R11 = 15.8 k:
R18 = 750 k:

V

TURN-OFF

=

R11

1.24V x (15.8 k: + 750 k:)

15.8 k:

1.24V x (R11 + R18)

= 60V

V

TURN-OFF

=

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The chosen components from step 12 are:

Design Procedure

(53)

(54)

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11

I

LED

(A)

V

SW

(V)

60

40

20

0

1.0

0.5

0.0

I

LED

V

SW

2 Ps/DIV

I

LED

(A)

V

DIM

(V)

10

5

0

1.0

0.0

-1.0

I

LED

V

DIM

4 ms/DIV

Typical Waveforms

7 Typical Waveforms

TA= +25°C, VIN= 24V and VO= 21V.

Figure 5. Standard Operation Figure 6. 200Hz 50% PWM Dimming

TP1 Switch Node Voltage (VSW) TP11 Dim Voltage (V

LED Current (I

) LED Current (I

LED

LED

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)

DIM

)

8 Alternate Designs

Alternate designs with the LM3429 evaluation board are possible with very few changes to the existing
hardware. The evaluation board FETs and diodes are already rated higher than necessary for design
flexibility. The input UVLO, output OVP, input and output capacitance can remain the same for the designs
shown below. These alternate designs can be evaluated by changing only R9, R10, and L1.

The table below gives the main specifications for four different designs and the corresponding values for
R9, R10, and L1. PWM dimming can be evaluated with any of these designs.

Specification / Design 1 Design 2 Design 3 Design 4

Component

V

IN

V

O

f

SW

I

LED

R9 0.05Ω 0.2Ω 0.04Ω 0.08Ω

R10 41.2 kΩ 35.7 kΩ 49.9 kΩ 35.7 kΩ

L1 22µH 68µH 15µH 33µH

Table 1. Alternate Design Specification

10V - 45V 15V - 50V 20V - 55V 25V - 60V

14V 21V 28V 35V

600kHz 700kHz 500kHz 700kHz

2A 500mA 2.5A 1.25A

12

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