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TPS60111PWPR

Datasheet TPS60111PWPR, TPS60111PWP Datasheet (Texas Instruments)

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TPS60111
REGULATED 5-V 150-mA LOW-NOISE
CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
1
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
features
Up to 150-mA Output Current
Less Than 10-mVpp Output Voltage Ripple
No Inductors Required/Low EMI
Regulated 5-V ±4% Output
Only Four External Components Required
Up to 90% Efficiency
2.7-V to 5.4-V Input Voltage Range
60-µA Quiescent Supply Current
0.05-µA Shutdown Current
Load Isolated in Shutdown
Space-Saving Thermally-Enhanced TSSOP PowerPAD Package
Evaluation Module Available (TPS60110EVM–132)
applications
Replaces DC/DC Converters With Inductors in
– Battery-Powered Applications – Li-Ion Battery to 5-V Conversion – Portable Instruments – Battery-Powered Microprocessor
Systems – Miniature Equipment – Backup-Battery Boost Converters – PDAs – Laptops – Handheld Instrumentation – Medical Instruments
description
The TPS60111 step-up, regulated charge pump generates a 5-V ±4% output voltage from a 2.7-V to 5.4-V input voltage (three alkaline, NiCd, or NiMH batteries; or, one lithium or lithium ion battery). Output current is 150 mA from a 3-V input. Only four external capacitors are needed to build a complete low-noise dc/dc converter. The push-pull operating mode of two single-ended charge pumps assures the low output voltage ripple as current is continuously transferred to the output. From a 3-V input, the TPS601 11 can start into full load with loads as low as 33 Ω.
The TPS601 11 features either constant frequency mode to minimize noise and output voltage ripple or the power-saving pulse-skip mode to extend battery life at light loads. The TPS601 11 switching frequency is 300 kHz. The logic shutdown function reduces the supply current to 1-µA (max) and disconnects the load from the input. Special current-control circuitry prevents excessive cur­rent from being drawn from the battery during start-up. This dc/dc converter requires no inductors and has low EMI. It is available in the small 20-pin TSSOP PowerPAD package (PWP).
Copyright  1999, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters.
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
PowerPAD is a trademark of Texas Instruments Incorporated.
output voltage ripple
typical operating circuit
Figure 1
SKIP =COM = CLK = 0 V VIN = 3.6 V IO = 150 mA CO = 22 µF + 10 µF
X5R Ceramic
5.2
5
5.05
5.1
5.15
4.8
4.85
4.9
4.95
– Output Voltage – VV
O
52.50 0.5 1 1.5 2 3 3.5 4 4.5
t – Time – µs
IN IN
C1+ C1– ENABLE
OUT OUT
FB
C2+ C2–
SYNC
SKIP COM CLK
PGND GND
INPUT
2.7 V to
5.4 V
CIN
4.7 µF
OUTPUT 5 V 150 mA
C
O
15 µF
C
2F
1 µF
C
1F
1 µF
+
OFF/ON
TPS60110
+
TPS60111 REGULATED 5-V 150-mA LOW-NOISE CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
2
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
1 2 3 4 5 6 7 8 9 10
20 19 18 17 16 15 14 13 12 11
GND
SYNC
ENABLE
FB
OUT
C1+
IN
C1– PGND PGND
GND CLK COM SKIP OUT C2+ IN C2– PGND PGND
PWP PACKAGE
(TOP VIEW)
Figure 2. Bottom View of PWP Package,
Showing the Thermal Pad
Thermal
Pad
AVAILABLE OPTIONS
PACKAGE
TSSOP
†
(PWP)
TPS60111PWP
†
This package is available taped and reeled. To order this packaging option, add an R suffix to the part number (e.g., TPS601 11PWPR).
Terminal Functions
TERMINAL
NAME NO.
I/O
DESCRIPTION
CLK 19 I Input for external clock signal. If the internal clock is used, connect this terminal to GND. C1+ 6 Positive terminal of the charge-pump capacitor C
1F
C1– 8 Negative terminal of the charge-pump capacitor C
1F
C2+ 15 Positive terminal of the charge-pump capacitor C
2F
C2– 13 Negative terminal of the charge-pump capacitor C
2F
COM 18 I Mode selection.
When COM is logic low the charge pump operates in push-pull mode to minimize output ripple. When COM is connected to IN the regulator operates in single-ended mode requiring only one flying capacitor.
ENABLE 3 I ENABLE Input. The device turns off, the output disconnects from the input, and the supply current decreases to
0.05 µA when ENABLE is a logic low. Connect ENABLE to IN for normal operation.
FB 4 I FEEDBACK input. Connect FB to OUT as close to the load as possible to achieve best regulation. Resistive divider
is on-chip to match internal reference voltage of 1.22 V . GND 1, 20 GROUND. Analog ground for internal reference and control circuitry. Connect to PGND through a short trace. IN 7, 14 I Supply Input. Connect to an input supply in the 2.7-V to 5.4-V range. Bypass IN to GND with a (CO/2) µF capacitor.
Connect both INs through a short trace. OUT 5, 16 O Regulated 5-V power output. Connect both OUTs through a short trace and bypass OUT to GND with the output
filter capacitor CO. PGND 9–12 PGND power ground. Charge-pump current flows through this pin. Connect all PGNDs together. SKIP 17 I Mode selection. When SKIP is logic low the charge pump operates in constant-frequency mode. Thus output ripple
and noise are minimized. When SKIP is connected to IN, the regulator operates in low-quiescent-current
pulse-skip mode. SYNC 2 I Selection for external clock signal. Connect to GND to use the internally generated clock signal. Connect to IN
for external synchronization. In this case, the clock signal needs to be fed through CLK.
TPS60111
REGULATED 5-V 150-mA LOW-NOISE
CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
3
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
absolute maximum ratings (unless otherwise noted)
†‡
Input voltage range, V
I
(IN, OUT, ENABLE, SKIP, COM, CLK, FB, SYNC) –0.3 V to 5.5 V. . . . . . . . . . . . . . . .
Differential input voltage, V
ID
(C1+, C2+ to GND) –0.3 V to (VO + 0.3 V). . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Differential input voltage, V
ID
(C1–, C2– to GND) –0.3 V to (VIN + 0.3 V). . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Continuous total power dissipation See Dissipation Rating Tables. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Continuous output current 200 mA. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Storage temperature range, T
stg
–55°C to 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Lead temperature 1,6 mm (1/16 inch) from case for 10s 260°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
Maximum junction temperature, TJ 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .
†
Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
‡
V
ENABLE
, V
SKIP
, V
COM
, V
CLK
and V
SYNC
can exceed VIN up to the maximum rated voltage without increasing the leakage current
drawn by these mode select inputs.
DISSIPATION RATING TABLE 1 – FREE-AIR TEMPERATURE (see Figure 3)
T
≤ 25°C DERATING FACTOR T
= 70°C T
= 85°C
PACKAGE
A
POWER RATING ABOVE TA = 25°CAPOWER RATINGAPOWER RATING
PWP 700 mW 5.6 mW/°C 448 mW 364 mW
DISSIPATION RATING TABLE 2 – CASE TEMPERATURE (see Figure 4)
T
≤ 62.5°C DERATING FACTOR T
= 70°C T
= 85°C
PACKAGE
C
POWER RATING ABOVE TC = 62.5°CCPOWER RATINGCPOWER RATING
PWP 25 W 285.7 mW/°C 22.9 W 18.5 W
Figure 3
1200
800
400
0
25 50 75 100
– Maximum Continuous Dissipation – mW
DISSIPATION DERATING CURVE
§
vs
FREE-AIR TEMPERATURE
125 150
1400
1000
600
200
PWP Package R
θJA
= 178°C/W
P
D
TA – Free-Air Temperature – °C
Figure 4
MAXIMUM CONTINUOUS DISSIPATION
§
vs
CASE TEMPERATURE
TC – Case Temperature – °C
15
10
5
0
25 50 75 100
20
25
30
125 150
Measured with the exposed thermal pad coupled to an infinite heat sink with a thermally conductive compound (the thermal conductivity of the compound is 0.815 W/m ⋅°C). The R
θJC
is 3.5°C/W.
PWP Package
– Maximum Continuous Dissipation – W P
D
§
Dissipation rating tables and figures are provided for maintenance of junction temperature at or below absolute maximum temperature of 150°C. It is recommended not to exceed a junction temperature of 125°C.
TPS60111 REGULATED 5-V 150-mA LOW-NOISE CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
4
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
electrical characteristics at CIN = 15 µF, C1F = C2F = 2.2 µF†, CO = 33 µF, TC = –40°C to 85°C, V
IN
= 3 V, VFB = VO, V
ENABLE
= VIN, V
SKIP
= VIN or 0 V and V
COM
= V
CLK
= V
SYNC
= 0 V (unless otherwise
noted)
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
V
IN
Input voltage
2.7 5.4 V
I
O(MAX)
Maximum output current 150 mA
2.7 V < VIN < 3 V, 0 < IO < 75 mA, V
O(Start-Up)
= 5 V, TC = 25°C
4.8 5 5.2
V
O
Output voltage
3 V < VIN < 5 V, 0 < IO < 150 mA
4.8 5 5.2
V
5 V < VIN < 5.4 V, 0 < IO < 150 mA 4.8 5 5.25
V
O(RIP)
Output voltage ripple IO = 150 mA, V
SKIP
= 0 V 10
‡
mV
PP
I
O(LEAK)
Output leakage current VIN = 3.6 V, V
ENABLE
= 0 V 1 µA
Quiescent current
V
SKIP
= VIN = 3.6 V 60 90 µA
I
Q
(no-load input current)
V
SKIP
= 0 V, VIN = 3.6 V
2.8 mA
I
DD(SDN)
Shutdown supply current VIN = 3.6 V, V
ENABLE
= 0 V 0.05 1 µA
f
OSC(int)
Internal switching frequency VIN = 3.6 V 200 300 400 kHz
f
OSC(ext)
External clock frequency V
SYNC
= VIN,V
IN
= 2.7 V to 5.4 V 400 600 800 kHz
External clock duty cycle V
SYNC
= VIN,V
IN
= 2.7V to 5.4 V 20% 80%
Efficiency IO = 75 mA 80%
V
INL
Input voltage low, ENABLE, SKIP, COM, CLK, SYNC
VIN = 2.7 V
0.3 × V
IN
V
V
INH
Input voltage high, ENABLE, SKIP, COM, CLK, SYNC
VIN = 5.4 V
0.7 × V
IN
V
I
I(LEAK)
Input leakage current, ENABLE, SKIP, COM, CLK, SYNC
V
ENABLE
= V
SKIP
= V
COM
= V
CLK
=
V
SYNC
= V
GND
or V
IN
0.01 0.1 µA
Output load regulation
VO = 5 V, 1 mA < IO < 150 mA TC = 25°C
0.002 %/mA
Output line regulation
3 V < VIN < 5 V, VO = 5 V, IO = 75 mA, TC = 25°C
0.6 %/V
Short circuit current
VIN = 3.6 V VO = 0 V, TC = 25°C
150 mA
†
Use only ceramic capacitors with X5R or X7R dielectric as flying capacitors.
‡
Achieved with CO = 22 µF + 10 µF X5R dielectric ceramic capacitor
TPS60111
REGULATED 5-V 150-mA LOW-NOISE
CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
5
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
†
Figure 5
50
40
20
0
0.1 1 10
Efficiency – %
70
90
EFFICIENCY
vs
OUTPUT CURRENT
100
100 1000
80
60
30
10
IO – Output Current – mA
V
(SKIP)
= V
IN
VIN = 3 V
VIN = 3.3 V
VIN = 3.6 V
VIN = 2.7 V
Figure 6
50
40
20
0
110
Efficiency – %
70
90
EFFICIENCY
vs
OUTPUT CURRENT
100
100 1000
80
60
30
10
IO – Output Current – mA
V
(SKIP)
= 0 V
VIN = 2.7 V
VIN = 3 V
VIN = 3.3 V
VIN = 3.6 V
Figure 7
60
50
40
2.5 3 3.5 4
– Quiescent Supply Current –
80
QUIESCENT SUPPLY CURRENT
vs
INPUT VOLTAGE
90
4.5 5.5
70
VIN – Input Voltage – V
I
Q
Aµ
V
(SKIP)
= V
IN
5
65
55
45
85
75
Figure 8
– Quiescent Supply Current – mA
QUIESCENT SUPPLY CURRENT
vs
INPUT VOLTAGE
VIN – Input Voltage – V
I
Q
2.5 3 3.5 4 4.5 5.55
V
(SKIP)
= 0 V
2.4
2
1.6
3.2
3.6
2.8
2.6
2.2
1.8
3.4
3
†TC = 25°C, V
COM
= V
SYNC
= 0 V, CIN = 15 µF, C1F and C2F = 2.2 µF (X7R ceramic), CO = 33 µF, unless otherwise noted
TPS60111 REGULATED 5-V 150-mA LOW-NOISE CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
6
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
†
Figure 9
IO – Output Current – mA
5
4.9
4.8
4.7 110
– Output Voltage – V
5.1
5.2
OUTPUT VOLTAGE
vs
OUTPUT CURRENT
5.3
100 1000
V
O
V
(SKIP)
= 0 V
VIN = 4 V
VIN = 3.6 V
VIN = 3 V
VIN = 2.7 V
VIN = 5.4 V
Figure 10
IO – Output Current – mA
5
4.9
4.8
4.7 110
– Output Voltage – V
5.1
5.2
OUTPUT VOLTAGE
vs
OUTPUT CURRENT
5.3
100 1000
V
O
V
(SKIP)
= V
IN
VIN = 4 V
VIN = 3.6 V
VIN = 3 V
VIN = 2.7 V
VIN = 5.4 V
Figure 11
5.04
4.98
4.94
4.9
– Output Voltage – V
5.06
5.08
OUTPUT VOLTAGE
vs
INPUT VOLTAGE
5.1
5.02
5
4.96
4.92
VIN – Input Voltage – V
V
O
V
(SKIP)
= 0 V
2.5 3 3.5 4 4.5 5.55
IO = 1 mA to 10 mA
IO = 150 mA
Figure 12
5.04
4.98
4.94
4.9
– Output Voltage – V
5.06
5.08
OUTPUT VOLTAGE
vs
INPUT VOLTAGE
5.1
5.02
5
4.96
4.92
VIN – Input Voltage – V
V
O
2.5 3 3.5 4 4.5 5.55
V
(SKIP)
= V
IN
IO = 1 mA to 150 mA
†TC = 25°C, V
COM
= V
SYNC
= 0 V, CIN = 15 µF, C1F and C2F = 2.2 µF (X7R ceramic), CO = 33 µF, unless otherwise noted
TPS60111
REGULATED 5-V 150-mA LOW-NOISE
CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
7
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
†
Figure 13
5.03
5.02
5.01 024
5.04
OUTPUT VOLTAGE
vs
TIME
5.05
610
t – Time – µs
V
(SKIP)
= 0 V VIN = 3.6 V IO = 150 mA CO = 22 µF + 10 µF X5R ceramic
Constant Frequency Mode
– Output Voltage – V V
O
8
Figure 14
5.03
5.01
4.99 0102030
5.05
OUTPUT VOLTAGE
vs
TIME
5.07
40 50
t – Time – µs
V
(SKIP)
= V
IN
VIN = 3.6 V IO = 150 mA
Pulse-Skip Mode
– Output Voltage – V V
O
Figure 15
5.01
200
100
0
0 2 4 6 8 10 12
– Output Voltage – V
5.02
5.04
t – Time – ms
LOAD TRANSIENT RESPONSE
5.05
14 16 18 20
300
5.03
V
O
– Output Current – mA I
O
V
(SKIP)
= 0 V IO = 10 mA to 150 mA VIN = 3.6 V
Constant Frequency Mode
Figure 16
5
200
100
0
0 2 4 6 8 10 12
5.02
5.06
t – Time – ms
LOAD TRANSIENT RESPONSE
5.08
14 16 18 20
300
5.04
V
(SKIP)
= VIN = 3.6 V
IO = 10 mA to 150 mA
Pulse-Skip Mode
– Output Voltage – V V
O
– Output Current – mA I
O
†TC = 25°C, V
COM
= V
SYNC
= 0 V, CIN = 15 µF, C1F and C2F = 2.2 µF (X7R ceramic), CO = 33 µF, unless otherwise noted
TPS60111 REGULATED 5-V 150-mA LOW-NOISE CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
8
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
†
Figure 17
5
4
3
2
0123456
– Output Voltage – V
5.02
5.06
t – Time – ms
LINE TRANSIENT RESPONSE
5.08
78 910
5
5.04
V
O
– Input Voltage – V V
IN
V
(SKIP)
= 0 V
IO = 150 mA
Constant Frequency Mode
Figure 18
5
4
3
2
0123456
5.02
5.06
t – Time – ms
LINE TRANSIENT RESPONSE
5.08
78 910
5
5.04
V
(SKIP)
= V
IN
IO = 150 mA
Pulse-Skip Mode
– Output Voltage – V V
O
– Input Voltage – V V
IN
Figure 19
50
40
20
0
0 2.5 5
Output – dB
60
80
f – Frequency – MHz
FREQUENCY SPECTRUM
CONSTANT FREQUENCY MODE
‡
90
7.5 10
70
30
10
Vµ
V
(SKIP)
= 0 V VIN = 3 V IO = 150 mA RBW = 300 Hz
Figure 20
40
20
0
0 2.5 5
Output – dB
60
100
f – Frequency – MHz
FREQUENCY SPECTRUM
PULSE-SKIP MODE
‡
7.5 10
Vµ
V
(SKIP)
= V
IN
VIN = 3 V IO = 150 mA RBW = 300 Hz
80
†TC = 25°C, V
COM
= V
SYNC
= 0 V, CIN = 15 µF, C1F and C2F = 2.2 µF (X7R ceramic), CO = 33 µF, unless otherwise noted
‡Test circuit: TPS60110EVM–132 with TPS6011 1
TPS60111
REGULATED 5-V 150-mA LOW-NOISE
CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
9
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
TYPICAL CHARACTERISTICS
†
Figure 21
50
20
10
0
0 2.5 5
60
70
f – Frequency – MHz
FREQUENCY SPECTRUM
CONSTANT FREQUENCY MODE
‡
90
7.5 10
30
40
80
Output – dB Vµ
V
(SKIP)
= 0 V VIN = 3 V IO = 10 mA RBW = 300 Hz
Figure 22
50
40
20
0
0 2.5 5
Output – dB
60
80
f – Frequency – MHz
FREQUENCY SPECTRUM
PULSE-SKIP MODE
‡
90
7.5 10
70
30
10
Vµ
V
(SKIP)
= V
IN
VIN = 3 V IO = 10 mA RBW = 300 Hz
Figure 23
Skip = High
Skip = Low
50
30 20
0
2.5 3 3.5 4
Efficiency – %
70
80
EFFICIENCY
vs
INPUT VOLTAGE
100
4.5 5.5
10
40
60
90
VIN – Input Voltage – V
5
IO = 150 mA
Figure 24
t – Time –µs
3
2
1
0
– Output Voltage – V
4
5
START-UP TIMING
6
200
V
O
R0 = 33.3 Ω VIN = 3 V
Enable
OUTPUT
–1
400 1200
0
600 800 1000
†TC = 25°C, V
COM
= V
SYNC
= 0 V, CIN = 15 µF, C1F and C2F = 2.2 µF (X7R ceramic), CO = 33 µF, unless otherwise noted
‡Test circuit: TPS60110EVM–132 with TPS6011 1
TPS60111 REGULATED 5-V 150-mA LOW-NOISE CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
10
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
detailed description
operating principle
The TPS601 1 1 charge pump provides a regulated 5-V output from a 2.7-V to 5.4-V input. It delivers a maximum load current of 150 mA. Designed specifically for space critical battery powered applications, the complete charge pump circuit requires only four external capacitors. The circuit can be optimized for highest efficiency at light loads or lowest output noise. The TPS601 11 consists of an oscillator , a 1.22-V bandgap reference, an internal resistive feedback circuit, an error amplifier, high current MOSFET switches, a shutdown/start-up circuit, and a control circuit (Figure 25).
C1+
C1–
ENABLE
OUT
FB
0°
180°
PGND
C
1F
IN
CHARGE PUMP 2
C2+
C2–
OUT
PGND
C
2F
IN
T
22
T
21
OSCILLATOR
GND
SKIP
COM
CLK
V
REF
–
+
–
+
CONTROL
CIRCUIT
0.8 × V
IN
–
+
–
+
SHUTDOWN/
START-UP CONTROL
SYNC
T
11
T
12
T
13
T
14
T
24
T
23
CHARGE PUMP 1
Figure 25. Functional Block Diagram TPS60111
The oscillator runs at a 50% duty cycle. The device consists of two single-ended charge pumps which operate with 180° phase shift. Each single ended charge pump transfers charge into its transfer capacitor (CxF) in one half of the period. During the other half of the period (transfer phase), CxF is placed in series with the input to transfer its charge to C
O
. While one single-ended charge pump is in the charge phase, the other one is in the
transfer phase. This operation guarantees an almost constant output current which ensures a low output ripple. If the clock were to run continuously , this process would eventually generate an output voltage equal to two times
the input voltage (hence the name doubler). In order to provide a regulated fixed output voltage of 5 V, the TPS601 1 1 uses either pulse-skip mode or constant-frequency mode. Pulse-skip mode and constant-frequency mode are externally selected via the SKIP input pin.
TPS60111
REGULATED 5-V 150-mA LOW-NOISE
CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
11
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
detailed description (continued)
start-up procedure
During start-up, i.e. when ENABLE is set from logic low to logic high, the switches T12 and T14 (charge pump
1), and the switches T22 and T24 (charge pump 2) are conducting to charge up the output capacitor until the output voltage VO reaches 0.8×VIN. When the start-up comparator detects this limit, the IC begins to operate in the mode selected with SKIP and COM. This start-up charging of the output capacitor guarantees a short start-up time and eliminates the need for a Schottky diode between IN and OUT.
pulse-skip mode
In pulse-skip mode (SKIP = high), the error amplifier disables switching of the power stages when it detects an output higher than 5 V. The oscillator halts. The IC then skips switching cycles until the output voltage drops below 5 V . Then the error amplifier reactivates the oscillator and switching of the power stages starts again. The pulse-skip regulation mode minimizes operating current because it does not switch continuously and deactivates all functions except bandgap reference and error amplifier when the output is higher than 5 V . When switching is disabled from the error amplifier, the load is also isolated from the input. SKIP is a logic input and should not remain floating. The typical operating circuit of the TPS601 1 1 in pulse skip mode is shown in Figure
1.
constant-frequency mode
When SKIP is low, the charge pump runs continuously at the frequency f
OSC
. The control circuit, fed from the error amplifier, controls the charge on C1F and C2F by driving the gates of the FETs T12/T13 and T22/T23, respectively. When the output voltage falls, the gate drive increases, resulting in a larger voltage across C
1F
and C2F. This regulation scheme minimizes output ripple. Since the device switches continuously, the output noise contains well-defined frequency components, and the circuit requires smaller external capacitors for a given output ripple. However, constant-frequency mode, due to higher operating current, is less ef ficient at light loads than pulse-skip mode.
IN IN
C1+ C1– ENABLE
OUT OUT
FB
C2+ C2–
SYNC
SKIP COM CLK
PGND GND
INPUT
2.7 V to 5.4 V
CIN
4.7 µF
OUTPUT 5 V 150 mA
CO = 33 µF
C
2F
1 µF
C
1F
1 µF
+
OFF/ON
TPS60111
+
Figure 26. Typical Operating Circuit TPS60111 in Constant Frequency Mode
Table 1. Tradeoffs Between Operating Modes
FEATURE PULSE-SKIP MODE
(SKIP = High)
CONSTANT-FREQUENCY MODE
(SKIP = Low)
Best light-load efficiency X Smallest external component size for a given output ripple X Output ripple amplitude Small amplitude Very small amplitude Output ripple frequency Variable Constant Load regulation Very good Good
NOTE: Even in pulse-skip mode the output ripple amplitude is small if the push-pull operating mode is selected via COM.
TPS60111 REGULATED 5-V 150-mA LOW-NOISE CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
12
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
detailed description (continued)
push-pull operating mode
In push-pull operating mode (COM = low), the two single-ended charge pumps operate with 180° phase shift. The oscillator signal has a 50% duty cycle. Each single-ended charge pump transfers charge into its transfer capacitor (CxF) in one-half of the period. During the other half of the period (transfer phase), CxF is placed in series with the input to transfer its charge to C
O
. While one single-ended charge pump is in the charge phase, the other one is in the transfer phase. This operation guarantees an almost constant output current which ensures a low output ripple. COM is a logic input and should not remain floating. The typical operating circuit of the TPS60111 in push-pull mode is shown in Figure 1 and Figure 26.
single-ended operating mode
When COM is high, the device runs in single-ended operating mode. The two single-ended charge pumps operate in parallel without phase shift. They transfer charge into the transfer capacitor (CF) in one half of the period. During the other half of the period (transfer phase), CF is placed in series with the input to transfer its charge to CO. In single-ended operating mode only one transfer capacitor (CF = C1F + C2F) is required, resulting in less board space.
IN IN
C1+ C1– ENABLE
OUT OUT
FB
C2+ C2–
SYNC
SKIP COM CLK
PGND GND
INPUT
2.7 V to 5.4 V
CIN
4.7 µF
OUTPUT 5 V 150 mA
CO = 15 µF
CF = 2.2 µF
+
OFF/ON
TPS60111
+
Figure 27. Typical Operating Circuit TPS60111 in Single-Ended Operating Mode
Table 2. Tradeoffs Between Operating Modes
FEATURE PUSH-PULL MODE
(COM = Low)
SINGLE-ENDED MODE
(COM = High)
Output ripple amplitude Small amplitude Large amplitude Smallest board space X
TPS60111
REGULATED 5-V 150-mA LOW-NOISE
CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
13
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
detailed description (continued)
shutdown
Driving ENABLE low places the device in shutdown mode. This disables all switches, the oscillator, and control logic. The device typically draws 0.05-µA (1-µA max) of supply current in this mode. Leakage current drawn from the output is as low as 1 µA max. The device exits shutdown once ENABLE is set high level. The typical no-load shutdown exit time is 20 µs. When the device is in shutdown, the load is isolated from the input and the output is high impedance.
external clock signal
If the device operates at a user-defined frequency , an external clock signal can be used. Therefore, SYNC needs to be connected to IN and the external oscillator signal can drive CLK. The maximum external frequency is limited to 800 kHz. The switching frequency of the converter is half of the external oscillator frequency. It is recommended to operate the charge pump in constant-frequency mode if an external clock signal is used so that the output noise contains only well-defined frequency components.
IN IN
C1+ C1– ENABLE
OUT OUT
FB
C2+
C2–
SYNC
SKIP COM CLK
PGND GND
INPUT
2.7 V to 5.4 V
CIN
4.7 µF
OUTPUT 5 V 150 mA
CO = 33 µF
C
2F
1 µF
C
1F
1 µF
+
OFF/ON
TPS60111
+
External Clock
Figure 28. Typical Operating Circuit TPS60111 With External Synchronization
TPS60111 REGULATED 5-V 150-mA LOW-NOISE CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
14
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
APPLICATION INFORMATION
capacitor selection
The TPS601 1 1 requires only four external capacitors as shown in the basic application circuit. Their values are closely linked to the output current capacity , output noise requirements, and mode of operation. Generally , the transfer capacitors (CxF) will be the smallest.
The input capacitor improves system efficiency by reducing the input impedance and stabilizes the input current. CIN is recommended to be about two to four times as large as CxF.
The output capacitor (CO) can be selected from 8-times to 50-times larger than CxF, depending on the mode of operation and ripple tolerance†. Tables 3 and 4 show capacitor values recommended for low quiescent-current operation (pulse-skip mode) and for low output voltage ripple operation (constant-frequency mode). A recommendation is given for smallest size.
Table 3. Recommended Capacitor Values for Low Quiescent-Current Operation
†
(pulse-skip mode)
VIN
I
[mA]
C
IN
[µF]
CxF
C
O
[µF]
OUTPUT
VOLTAGE
[V]
O
[]
TANTALUM CERAMIC
[µF]
TANTALUM CERAMIC
RIPPLE V
PP
[mV]
3.6 75 4.7 1 15 150
3.6 75 4.7 (X7R) 1 10 (X5R) 105
3.6 150 4.7 1 15 150
3.6 150 4.7 (X7R) 1 10 (X5R) 105
†
All measurements are done with additional 1-µF X7R ceramic capacitors at input and output.
Table 4. Recommended Capacitor Values for Low Output Voltage Ripple Operation
†
(constant-frequency mode)
VIN
I
O
C
IN
[µF]
CxF
C
O
[µF]
OUTPUT
VOLTAGE
[V]
[mA]
TANTALUM CERAMIC
[µF]
TANTALUM CERAMIC
RIPPLE V
PP
[mV]
3.6 75 4.7 1 33 10
3.6 75 4.7 (X7R) 1 22 + 10, (X5R) 6
3.6 150 4.7 1 33 17
3.6 150 4.7 (X7R) 1 22 + 10, (X5R) 10
†
All measurements are done with additional 1-µF X7R ceramic capacitors at input and output.
†
In constant-frequency mode always select CO ≥ 33 µF
TPS60111
REGULATED 5-V 150-mA LOW-NOISE
CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
15
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
APPLICATION INFORMATION
For the TPS60111, the smallest board space size can be achieved using Sprague’s 595D-series tantalum capacitors for input and output. However, with the trend towards high capacitance ceramic capacitors in smaller size packages, these type of capacitors might soon become competitive in size.
Table 5. Recommended Capacitors
MANUFACTURER PART NUMBER CAPACITANCE TYPE
Taiyo Yuden LMK212BJ105KG–T
LMK212BJ225MG–T
LMK316BJ475KL–T
JMK316BJ106ML–T
LMK432BJ226MM–T
1 µF
2.2 µF
4.7 µF 10 µF 22 µF
Ceramic Ceramic Ceramic Ceramic Ceramic
AVX 0805ZC105KAT2A
1206ZC225KAT2A TPSC475K035R0600 TPSC156K020R0450 TPSC336K010R0375
1 µF
2.2 µF
4.7 µF 15 µF 33 µF
Ceramic
Ceramic Tantalum Tantalum Tantalum
Sprague 595D475X0016A2T
595D156X06R3A2T
595D156X0016B2T
595D336X06R3A2T
595D336X0016B2T 595D336X0016C2T
4.7 µF 15 µF 15 µF 33 µF 33 µF 33 µF
Tantalum Tantalum Tantalum Tantalum Tantalum Tantalum
Kemet T494B475M010AS
T494C156K010AS T494C336K010AS
4.7 µF 15 µF 33 µF
Tantalum Tantalum Tantalum
Table 6 lists the manufacturers of recommended capacitors. In most applications surface-mount tantalum capacitors will be the right choice. However, ceramic capacitors will provide the lowest output voltage ripple due to their typically lower ESR.
Table 6. Recommended Capacitor Manufacturers
MANUFACTURER CAPACITOR TYPE INTERNET
Taiyo Yuden X7R/X5R ceramic www.t–yuden.com AVX X7R/X5R ceramic
TPS–series tantalum
www.avxcorp.com
Sprague 595D–series tantalum
593D–series tantalum
www.vishay.com
Kemet T494–series tantalum www.kemet.com
power dissipation
The power dissipated in the TPS60111 depends on output current and is approximated by:
P
DISS
+
IO ǒ2VIN*
V
O
Ǔ
for IQtt
I
O
P
DISS
must be less than that allowed by the package rating. See the ratings for 20-PowerPAD package
power-dissipation limits and deratings.
TPS60111 REGULATED 5-V 150-mA LOW-NOISE CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
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APPLICATION INFORMATION
layout
All capacitors should be soldered in close proximity to the IC. A PCB layout proposal for a two-layer board is given in Figure 29. Care has been taken to connect both single-ended charge pumps symmetrically to the load to achive optimized output voltage ripple performance. The proposed layout also provides improved thermal performance as the exposed leadframe is soldered to the PCB. The bottom layer of the PCB is a ground plain only . All ground areas on the PCB should be connected. Connect ground areas on top layer to the bottom layer via through hole connections.
GND
GND
GND
ENABLE
SYNC
C1+
C1–
GND
GND
OUT
IN
CLK COM SKIP
C2+
C2–
Figure 29. Recommended PCB Layout for TPS60111 (top view)
The evaluation module designed for the TPS601 10 can, with slight modifications, be used for evaluation of the TPS60111. The EVM can be ordered under literature code SLVP132 or under product code TPS60110EVM–132.
TPS60111
REGULATED 5-V 150-mA LOW-NOISE
CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
17
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
APPLICATION INFORMATION
applications proposals
TPS60111 with LC output filter for ultra low ripple
For applications where extremely low output ripple is required, a small LC filter is recommended. This is shown in Figure 30. The addition of a small inductor and filter capacitor will reduce the output ripple well below what could be achieved with capacitors alone. The corner frequency of 500 kHz was chosen above the 300 kHz switching frequency to avoid loop stability issues in case the feedback is taken from the output of the LC filter. Leaving the feedback (FB) connection point before the LC filter, the filter capacitance value can be increased to achieve even higher ripple attenuation without affecting stability margin.
IN IN
C1+ C1– ENABLE
OUT OUT
FB
C2+ C2–
SYNC
SKIP COM CLK
PGND GND
INPUT
2.7 V to 5.4 V
CIN
4.7 µF
OUTPUT 5 V 150 mA
CO = 33 µF
C
2F
1 µF
C
1F
1 µF
+
OFF/ON
TPS60111
+ 1 µF
+
0.1 µH
Figure 30. TPS60111 With LC Filter for Ultra Low Output Ripple Applications
related information
application reports
For more application information see:
PowerPAD Application Report
(Literature Number: SLMA002)
TPS6010x/TPS6011x Charge Pump Application Report
(Literature Number: SLVA070)
device family products
Other devices in this family are:
PART NUMBER
LITERATURE
NUMBER
DESCRIPTION
TPS60100 SL VS213 Regulated 3.3-V, 200-mA Low-Noise Charge Pump DC/DC Converter TPS60101 SL VS214 Regulated 3.3-V, 100-mA Low-Noise Charge Pump DC/DC Converter TPS60110 SLVS215 Regulated 5-V, 300-mA Low-Noise Charge Pump DC/DC Converter
TPS60111 REGULATED 5-V 150-mA LOW-NOISE CHARGE PUMP DC/DC CONVERTER
SLVS216A – JUNE 1999 – SEPTEMBER 1999
18
POST OFFICE BOX 655303 • DALLAS, TEXAS 75265
MECHANICAL DATA
PWP (R-PDSO-G**) PowerPAD PLASTIC SMALL-OUTLINE PACKAGE
4073225/E 03/97
0,50
0,75
0,25
0,15 NOM
Thermal Pad (See Note D)
Gage Plane
2824
7,70
7,90
20
6,40
6,60
9,60
9,80
6,60 6,20
11
0,19
4,50 4,30
10
0,15
20
A
1
0,30
1,20 MAX
1614
5,10
4,90
PINS **
4,90
5,10
DIM
A MIN
A MAX
0,05
Seating Plane
0,65
0,10
M
0,10
0°–8°
20-PIN SHOWN
NOTES: A. All linear dimensions are in millimeters.
B. This drawing is subject to change without notice. C. Body dimensions do not include mold flash or protrusions. D. The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane. This pad is electrically
and thermally connected to the backside of the die and possibly selected leads.
E. Falls within JEDEC MO-153
PowerPAD is a trademark of Texas Instruments Incorporated.
IMPORTANT NOTICE
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TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in accordance with TI’s standard warranty. T esting and other quality control techniques are utilized to the extent TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed, except those mandated by government requirements.
CERT AIN APPLICATIONS USING SEMICONDUCTOR PRODUCTS MAY INVOLVE POTENTIAL RISKS OF DEATH, PERSONAL INJURY, OR SEVERE PROPERTY OR ENVIRONMENTAL DAMAGE (“CRITICAL APPLICATIONS”). TI SEMICONDUCTOR PRODUCTS ARE NOT DESIGNED, AUTHORIZED, OR WARRANTED TO BE SUITABLE FOR USE IN LIFE-SUPPORT DEVICES OR SYSTEMS OR OTHER CRITICAL APPLICATIONS. INCLUSION OF TI PRODUCTS IN SUCH APPLICA TIONS IS UNDERSTOOD T O BE FULLY AT THE CUSTOMER’S RISK.
In order to minimize risks associated with the customer’s applications, adequate design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards.
TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other intellectual property right of TI covering or relating to any combination, machine, or process in which such semiconductor products or services might be or are used. TI’s publication of information regarding any third party’s products or services does not constitute TI’s approval, warranty or endorsement thereof.
Copyright 1999, Texas Instruments Incorporated
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