Datasheet TPA2001D2PWPR, TPA2001D2PWP Datasheet (Texas Instruments)

TPA2001D2

1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

 Modulation Scheme Optimized to Operate

Without a Filter

 1 W Into 8-Ω Speakers (THD+N< 0.4%)
 < 0.08% THD+N at 0.5 W, 1 kHz, Into 8-Ω

Load

 Extremely Efficient 3

Class-D Technology:
– Low Supply Current (No Filter) ...8 mA
– Low Supply Current (Filter) ...15 mA
– Low Shutdown Current ...1 µA
– Low Noise Floor ...56 µV
– Maximum Efficiency Into 8 Ω, 75 – 85%
– 4 Internal Gain Settings ...8 – 23.5 dB
– PSRR . . . –77 dB

rd

Generation 5-V

RMS

PGND

LOUTN

GAIN0

PV

DD

LINN
AGND
COSC

RINN

PV

DD

SHUTDOWN

ROUTN

PGND

PWP PACKAGE

(TOP VIEW)

1
2
3
4
5
6
7
8
9
10
11
12

24
23
22
21
20
19
18
17
16
15
14
13

 Integrated Depop Circuitry
 Short-Circuit Protection (Short to Battery,

Ground, and Load)

 –40°C to 85°C Operating Temperature

Range

description

The TPA2001D2 is the third generation 5-V class-D amplifier from Texas Instruments. Improvements to
previous generation devices include: lower supply current, lower noise floor, better ef ficiency , four different gain
settings, smaller packaging, and fewer external components. The most significant advancement with this device
is its modulation scheme that allows the amplifier to operate without the output filter. Eliminating the output filter
saves the user approximately 30% in system cost and 75% in PCB area.

PGND
LOUTP
BYPASS
PV

DD

LINP
V

DD

ROSC
RINP
PV

DD

GAIN1
ROUTP
PGND

The TPA2001D2 is a monolithic class-D power IC stereo audio amplifier, using the high switching speed of
power MOSFET transistors. These transistors reproduce the analog signal through high-frequency switching
of the output stage. The TPA2001D2 is configured as a bridge-tied load (BTL) amplifier capable of delivering
greater than 1 W of continuous average power into an 8-Ω load at less than 0.6% THD+N from a 5-V power
supply in the high fidelity range (20 Hz to 20 kHz). With 1 W being delivered to an 8-Ω load at 1 kHz, the typical
THD+N is less than 0.08%.

A BTL configuration eliminates the need for external coupling capacitors on the output. Low supply current of
8 mA makes the device ideal for battery-powered applications. Protection circuitry increases device reliability:
thermal, over-current, and under-voltage shutdown.

Efficient class-D modulation enables the TPA2001D2 to operate at full power into 8-Ω loads at an ambient
temperature of 85°C.

AVAILABLE OPTIONS

PACKAGED DEVICE

TSSOP (PWP)

Copyright  2000, Texas Instruments Incorporated

–40°C to 85°C TPA2001D2PWP

NOTE: The PWP package is available taped and reeled. To

Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.

PowerPAD is a trademark of Texas Instruments.

PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of Texas Instruments
standard warranty. Production processing does not necessarily include
testing of all parameters.

T

A

order a taped and reeled part, add the suffix R to the
part number (e.g., TPA2001D2PWPR).

POST OFFICE BOX 655303 • DALLAS, TEXAS 75265

1

TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

functional block diagram

RINN

RINP

SHUTDOWN

GAIN1
GAIN0

COSC
ROSC

BYPASS

LINP

Gain

2

Gain

Adjust

_

+

_

+

Gain

Adjust

Biases

and

References

Gain

Adjust

DD

V

DD

Ramp

Generator

AGNDV

PV

DD

+
_

_
+

Protection

Thermal VDD ok

+
_

Start-up

Logic

Gate

Drive

Gate

Drive

Gate

Drive

OC

Detect

OC

Detect

ROUTN

PGND
PV

DD

ROUTP

PGND

PV

DD

LOUTP

LINN

_
+

Gain

Adjust

+

_

_
+

Gate

Drive

PGND
PV

DD

LOUTN

PGND

2

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TPA2001D2

1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

Terminal Function

TERMINAL

NAME NO.

AGND 6 – Analog ground
BYPASS 22 I Tap to voltage divider for internal midsupply bias generator used for analog reference.

COSC 7 I
GAIN0 3 I Bit 0 of gain control (TTL logic level)

GAIN1 15 I Bit 1 of gain control (TTL logic level)
LINN 5 I Left channel negative differential audio input
LINP 20 I Left channel positive differential audio input
LOUTN 2 O Left channel negative audio output
LOUTP 23 O Left channel positive audio output

PGND

PV

DD

RINN 8 I Right channel negative differential audio input
RINP 17 I Right channel positive differential audio input

ROSC 18 I
ROUTN 11 O Right channel negative audio output

ROUTP 14 O Right channel positive output
SHUTDOWN 10 I
V

DD

1, 24 – Power ground for left channel H-bridge

12, 13 – Power ground for right channel H-bridge

4, 21 – Power supply for left channel H-bridge
9, 16 – Power supply for right channel H-bridge

I/O

A capacitor connected to this terminal sets the oscillation frequency in conjunction with ROSC. For proper
operation, connect a 220 pF capacitor from COSC to ground.

A resistor connected to this terminal sets the oscillation frequency in conjunction with COSC. For proper
operation, connect a 120 kΩ resistor from ROSC to ground.

Places the amplifier in shutdown mode if a TTL logic low is placed on this terminal; normal operation if a TTL
logic high is placed on this terminal.

19 – Analog power supply

DESCRIPTION

absolute maximum ratings over operating free-air temperature (unless otherwise noted)

†

Supply voltage, VDD, PVDD –0.3 V to 6 V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Input voltage, VI –0.3 V to VDD+0.3 V. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Continuous total power dissipation See Dissipation Rating Table. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Operating free-air temperature range, T
Operating junction temperature range, T
Storage temperature range, T

stg

–40°C to 85°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

A

–40°C to 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

J

–65°C to 150°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds 260°C. . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .

†

Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.

DISSIPATION RATING TABLE

PACKAGE

PWP 2.7 W 21.8 mW/°C 1.7 W 1.4 W

TA ≤ 25°C

POWER RATING

DERATING FACTOR

ABOVE TA = 25°C

TA = 70°C

POWER RATING

TA = 125°C

POWER RATING

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3

TPA2001D2

GAIN0

GAIN1

1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

recommended operating conditions

MIN MAX UNIT

Supply voltage, VDD, PV
High-level input voltage, V
Low-level input voltage, V
Operating free-air temperature, T
PWM Frequency 200 300 kHz

DD

IL

IH

GAIN0, GAIN1, SHUTDOWN 2 V
GAIN0, GAIN1, SHUTDOWN 0.8 V

A

electrical characteristics, TA = 25°C, VDD = PVDD = 5 V (unless otherwise noted)

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

| VOO | Output offset voltage (measured differentially) VI = 0 V 10 mV
PSRR Power supply rejection ratio VDD=PVDD = 4.5 V to 5.5 V –77 dB
I

IH

I

IL

I

DD

I

DD

I

DD(SD)

High-level input current VDD=PVDD = 5.5 V, VI = VDD = PV
Low-level input current VDD=PVDD = 5.5 V, VI = 0 V –1 µA
Supply current No filter (with or without speaker load) 8 10 mA
Supply current
Supply current, shutdown mode 1 10 µA

With filter, L = 22 µH, C = 1 µF

DD

4.5 5.5 V

–40 85 °C

1 µA

15 mA

operating characteristics, TA = 25°C, VDD = PVDD = 5 V , RL = 8 Ω, Gain = 8 dB (unless otherwise noted)

PARAMETER TEST CONDITIONS MIN TYP MAX UNIT

P

O

THD+N Total harmonic distortion plus noise PO = 0.5 W, f = 20 Hz to 20 kHz <0.2%
B

OM

k

SVR

SNR Signal-to-noise ratio 20 Hz to 20 kHz 87 dBV

Z

I

Output power THD = 0.4%, f = 1 kHz, RL = 8 Ω 1 W

Maximum output power bandwidth THD = 5% 20 kHz
Supply ripple rejection ratio f = 1 kHz, C

Integrated noise floor 20 Hz to 20 kHz, No input 56
Input impedance >20 kΩ

(BYPASS)

= 0.4 µF –60 dB

µV

Table 1. Gain Settings

AMPLIFIER GAIN

GAIN0 GAIN1

0 0 8 104
0 1 12 74
1 0 17.5 44
1 1 23.5 24

(dB)

TYP TYP

INPUT IMPEDANCE

(kΩ)

4

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TPA2001D2

1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

APPLICATION INFORMATION

eliminating the output filter with the TPA2001D2

This section will focus on why the user can eliminate the output filter with the TPA2001D2.

effect on audio

The class-D amplifier outputs a pulse-width modulated (PWM) square wave, which is the sum of the switching
waveform and the amplified input audio signal. The human ear acts as a band-pass filter such that only the
frequencies between approximately 20 Hz and 20 kHz are passed. The switching frequency components are
much greater than 20 kHz, so the only signal heard is the amplified input audio signal.

traditional class-D modulation scheme

The traditional class-D modulation scheme, which is used in the TPA005Dxx family, has a differential output
where each output is 180 degrees out of phase and changes from ground to the supply voltage, V
the differential pre-filtered output varies between positive and negative VDD, where filtered 50% duty cycle yields
0 volts across the load. The traditional class-D modulation scheme with voltage and current waveforms is shown
in Figure 1. Note that even at an average of 0 volts across the load (50% duty cycle), the current to the load is
high causing high loss thus causing a high supply current.

DD

. Therefore,

OUT+

OUT–

+5 V

Differential Voltage

Across Load

O V

–5 V

Current

Figure 1. Traditional Class-D Modulation Scheme’s Output Voltage and Current Waveforms Into an

Inductive Load With no Input

TPA2001D2 modulation scheme

The TPA2001D2 uses a modulation scheme that still has each output switching from 0 to the supply voltage.
However, OUT+ and OUT– are now in phase with each other with no input. The duty cycle of OUT+ is greater
than 50% and OUT– is less than 50% for positive voltages. The duty cycle of OUT+ is less than 50% and OUT–
is greater than 50% for negative voltages. The voltage across the load sits at 0 volts throughout most of the
switching period greatly reducing the switching current, which reduces any I

2

R losses in the load.

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5

TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

APPLICATION INFORMATION

OUT+

OUT–

Differential

Voltage

Across

Load

+5 V

0 V

–5 V

Current

OUT+

Output = 0 V

Differential

Voltage

Across

Load

OUT–

+5 V

0 V

–5 V

Current

Output > 0 V

Figure 2. The TPA2001D2 Output Voltage and Current Waveforms Into an Inductive Load

efficiency: why you must use a filter with the traditional class-D modulation scheme

The main reason that the traditional class-D amplifier needs an output filter is that the switching waveform
results in maximum current flow. This causes more loss in the load, which causes lower ef ficiency. The ripple
current is large for the traditional modulation scheme because the ripple current is proportional to voltage
multiplied by the time at that voltage. The differential voltage swing is 2 ×VDD and the time at each voltage is
half the period for the traditional modulation scheme. An ideal LC filter is needed to store the ripple current from
each half cycle for the next half cycle, while any resistance causes power dissipation. The speaker is both
resistive and reactive, whereas an LC filter is almost purely reactive.

The TP A2001D2 modulation scheme has very little loss in the load without a filter because the pulses are very
short and the change in voltage is V

instead of 2 × VDD. As the output power increases, the pulses widen

DD

making the ripple current larger. Ripple current could be filtered with an LC filter for increased ef ficiency , but for
most applications the filter is not needed.

An LC filter with a cut-off frequency less than the class-D switching frequency allows the switching current to
flow through the filter instead of the load. The filter has less resistance than the speaker that results in less power
dissipated, which increases efficiency.

6

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TPA2001D2

1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

APPLICATION INFORMATION

effects of applying a square wave into a speaker

Audio specialists have said for years not to apply a square wave to speakers. If the amplitude of the waveform
is high enough and the frequency of the square wave is within the bandwidth of the speaker, the square wave
could cause the voice coil to jump out of the air gap and/or scar the voice coil. A 250-kHz switching frequency ,
however, is not significant because the speaker cone movement is proportional to 1/f
the audio band. Therefore, the amount of cone movement at the switching frequency is very small. However,
damage could occur to the speaker if the voice coil is not designed to handle the additional power. To size the
speaker for added power, the ripple current dissipated in the load needs to be calculated by subtracting the
theoretical supplied power, P
P

. The switching power dissipated in the speaker is the inverse of the measured efficiency, η

OUT

minus the theoretical efficiency, η

SPKR

= P

SUP

– P

SUP THEORETICAL

THEORETICAL

SUP THEORETICAL

, from the actual supply power, P

.

(at max output power)

2

for frequencies beyond

, at maximum output power,

SUP

MEASURED

(1)P

,

SPKR
SPKR

= P
= 1/η

/ P

SUP

OUT

MEASURED

– P

SUP THEORETICAL

– 1/η

THEORETICAL

/ P

(at max output power)

OUT

(at max output power)

The maximum efficiency of the TPA2001D2 with an 8-Ω load is 85%. Using equation 3 with the efficiency at
maximum power (78%) there is an additional 106 mW dissipated in the speaker. The added power dissipated
in the speaker is not an issue as long as it is taken into account when choosing the speaker.

when to use an output filter

Design the TPA2001D2 without the filter if the traces from amplifier to speaker are short. The TPA2001D2
passed FCC and CE radiated emissions with no shielding with speaker wires 8 inches long or less. Notebook
PCs and powered speakers where the speaker is in the same enclosure as the amplifier are good applications
for class-D without a filter.

A ferrite bead filter can often be used if the design is failing radiated emissions without a filter, and the frequency
sensitive circuit is greater than 1 MHz. This is good for circuits that just have to pass FCC and CE because FCC
and CE only test radiated emissions greater than 30 MHz. If choosing a ferrite bead, choose one with high
impedance at high frequencies, but very low impedance at low frequencies.

Use an output filter if there are low frequency (< 1 MHz) EMI sensitive circuits and/or there are long leads from
amplifier to speaker.

gain setting via GAIN0 and GAIN1 inputs

The gain of the TPA2001D2 is set by two input terminals, GAIN0 and GAIN1.
The gains listed in Table 2 are realized by changing the taps on the input resistors inside the amplifier. This

causes the input impedance, Z
by ratios of resistors, so the actual gain distribution from part-to-part is quite good. However, the input
impedance may shift by 30% due to shifts in the actual resistance of the input resistors.

, to be dependent on the gain setting. The actual gain settings are controlled

I

(2)P
(3)P

For design purposes, the input network (discussed in the next section) should be designed assuming an input
impedance of 20 kΩ, which is the absolute minimum input impedance of the TPA2001D2. At the higher gain
settings, the input impedance could increase as high as 115 kΩ.

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7

TPA2001D2

GAIN0

GAIN1

1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

APPLICATION INFORMATION

Table 2. Gain Settings

AMPLIFIER GAIN

GAIN0 GAIN1

0 0 8 104
0 1 12 74
1 0 17.5 44
1 1 23.5 24

(dB)

TYP TYP

INPUT IMPEDANCE

(kΩ)

input resistance

Each gain setting is achieved by varying the input resistance of the amplifier, which can range from its smallest
value to over 6 times that value. As a result, if a single capacitor is used in the input high pass filter, the –3 dB
or cut-off frequency will also change by over 6 times. If an additional resistor is connected from the input pin
of the amplifier to ground, as shown in the figure below, the variation of the cut-off frequency will be much
reduced.

Z

F

C

Input

Signal

i

IN

R

Z

I

The –3 dB frequency can be calculated using equation 4:

f

–3 dB



2 C

1



R  Z

i



I

If the filter must be more accurate, the value of the capacitor should be increased while value of the resistor to
ground should be decreased. In addition, the order of the filter could be increased.

input capacitor, C

i

In the typical application an input capacitor, Ci, is required to allow the amplifier to bias the input signal to the
proper dc level for optimum operation. In this case, Ci and the input impedance of the amplifier, ZI, form a
high-pass filter with the corner frequency determined in equation 5.

–3 dB

f

c(highpass)



2 Z

1

C

i

I

f

c

(4)

(5)

8

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TPA2001D2

1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

APPLICATION INFORMATION

The value of Ci is important as it directly affects the bass (low frequency) performance of the circuit. Consider
the example where ZI is 20 kΩ and the specification calls for a flat bass response down to 80 Hz. Equation 5
is reconfigured as equation 6.



1

2 ZIf

c

is 0.1 µF so one would likely choose a value in the range of 0.1 µF to 1 µF . If the gain is known

i

C

i

In this example, C
and will be constant, use ZI from T able 1 to calculate Ci. A further consideration for this capacitor is the leakage
path from the input source through the input network (C

) and the feedback network to the load. This leakage

i

current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high
gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When
polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most
applications as the dc level there is held at VDD/2, which is likely higher than the source dc level. Note that it
is important to confirm the capacitor polarity in the application.

Ci must be 10 times smaller than the bypass capacitor to reduce clicking and popping noise from power on/off
and entering and leaving shutdown. After sizing Ci for a given cut-off frequency, size the bypass capacitor to
10 times that of the input capacitor.

/ 10

BYP

power supply decoupling, C

S

The TP A2001D2 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling
to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also
prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is
achieved by using two capacitors of different types that target different types of noise on the power supply leads.
For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance
(ESR) ceramic capacitor, typically 0.1 µF placed as close as possible to the device V

lead works best. For

DD

filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF or greater placed near
the audio power amplifier is recommended.

(6)

(7)Ci ≤ C

midrail bypass capacitor, C

The midrail bypass capacitor, C
start-up or recovery from shutdown mode, C

BYP

, is the most critical capacitor and serves several important functions. During

BYP

determines the rate at which the amplifier starts up. The second

BYP

function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This
noise is from the midrail generation circuit internal to the amplifier, which appears as degraded PSRR and
THD+N.

Bypass capacitor, C

, values of 0.47 µF to 1 µF ceramic or tantalum low-ESR capacitors are recommended

BYP

for the best THD and noise performance.
Increasing the bypass capacitor reduces clicking and popping noise from power on/off and entering and leaving

shutdown. To have minimal pop, C

≥ 10 × C

BYP

i

should be 10 times larger than Ci.

BYP

(8)C

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9

TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

APPLICATION INFORMATION

differential input

The differential input stage of the amplifier cancels any noise that appears on both input lines of a channel. To
use the TP A2001D2 EVM with a differential source, connect the positive lead of the audio source to the RINP
(LINP) input and the negative lead from the audio source to the RINN (LINN) input. T o use the TP A2001D2 with
a single-ended source, ac ground the RINN and LINN inputs through a capacitor and apply the audio single to
the RINP and LINP inputs. In a single-ended input application, the RINN and LINN inputs should be ac grounded
at the audio source instead of at the device inputs for best noise performance.

shutdown modes

The TP A2001D2 employs a shutdown mode of operation designed to reduce supply current, IDD, to the absolute
minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN input terminal
should be held high during normal operation when the amplifier is in use. Pulling SHUTDOWN low causes the
outputs to mute and the amplifier to enter a low-current state, I
unconnected because amplifier operation would be unpredictable.

using low-ESR capacitors

DD(SD)

= 1 µA. SHUTDOWN should never be left

Low-ESR capacitors are recommended throughout this application section. A real (as opposed to ideal)
capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this
resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this
resistance the more the real capacitor behaves like an ideal capacitor.

evaluation circuit

GND

LIN+

LIN–

RIN–

RIN+

GND

SHUTDOWN

C1

0.1 µF

C2

0.1 µF

C3

0.1 µF

C4

0.1 µF

120 k

GAIN0

PGND
LOUTN

120 k
R1

C18

R3

0.1 µF

C17

0.1 µF

C7

220 pF

S1

GAIN0
LPVDD

LINN
AGND
COSC
RINN

RPVDD
SHUTDOWN

ROUTN
PGND

U1

TPA2001D2

PGND

LOUTP

BYPASS

LPVDD

LINP

VDD

ROSC

RINP

RPVDD

GAIN1

ROUTP

PGND

0.1 µF

C19

0.1 µF

C21

C20

0.1 µF

120k

C5

C6

R2

C8

10 uF

1 µF

10 µF

120 k

R4

GAIN1

LOUT–

GND

LOUT+

VDD
VDD

ROUT+

GND
GND
GND

NOTE: R1, R3, and R4 are used in the EVM but are not required for normal applications.

10

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ROUT–

TPA2001D2

1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

APPLICATION INFORMATION

Table 3. TPA2001D2 Evaluation Bill of Materials

REFERENCE DESCRIPTION SIZE QUANTITY MANUFACTURER PART NUMBER

C1–4,
C17–21

C5 Capacitor, ceramic, 1.0 µF, +80%/–20%, Y5V , 16 V 0805 1 Murata GRM40-Y5V105Z16
C6, C8 Capacitor, ceramic, 10 µF, +80%/–20%, Y5V , 16 V 1210 2 Murata GRM235-Y5V106Z16
C7 Capacitor, ceramic, 220 pF, ±10%, XICON, 50 V 0805 2 Mouser 140–CC501B221K

Capacitor, ceramic chip, 0.1 µF, ±10%, X7R, 50 V 0805 9 Kemet C0805C104K5RAC

R2, R1†,

†

R3†, R4
U1 IC, TPA2001D2, audio power amplifier, 2-W,

†

These components are used in the EVM, but they are not required for normal applications.

Resistor, chip, 120 kΩ, 1/10 W, 5%, XICON 0805 2 Mouser 260–120K

2-channel, class-D

24 pin

TSSOP

1 TI TPA2001D2PWP

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11

TPA2001D2
1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER

SLOS292A – MARCH 2000 – REVISED APRIL 2000

MECHANICAL DATA

PWP (R-PDSO-G**) PowerPAD PLASTIC SMALL-OUTLINE

20 PINS SHOWN

0,65

20

1

1,20 MAX

0,30

0,19

11

4,50
4,30

10

A

0,15
0,05

PINS **

DIM

M

0,10

6,60
6,20

Seating Plane

0,10

1614

Thermal Pad
(See Note D)

20

0,15 NOM

0°–8°

Gage Plane

0,25

0,75
0,50

2824

A MAX

A MIN

NOTES: A. All linear dimensions are in millimeters.

B. This drawing is subject to change without notice.
C. Body dimensions do not include mold flash or protrusions.
D. The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane.

This pad is electrically and thermally connected to the backside of the die and possibly selected leads.

E. Falls within JEDEC MO-153

PowerPAD is a trademark of Texas Instruments Incorporated.

5,10

4,90

5,10

4,90

6,60

6,40

7,90

7,70

9,80

9,60

4073225/F 10/98

12

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