Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments
查询ADS1601供应商查询ADS1601供应商
SBAS322 − DECEMBER 2004
FEATURES
D High Speed:
Data Rate: 1.25MSPS
Bandwidth: 615kHz
D Outstanding Performance:
SNR: 92dB at fIN = 100kHz, −1dBFS
THD: −103dB at fIN = 100kHz, −6dBFS
SFDR: 105dB at fIN = 100kHz, −6dBFS
D Ease-of-Use:
High-Speed 3-Wire Serial Interface
Directly Connects to TMS320 DSPs
On-Chip Digital Filter Simplifies Anti-Alias
Requirements
Simple Pin-Driven Control—No On-Chip
Registers to Program
Selectable On-Chip Voltage Reference
Simultaneous Sampling with Multiple
ADS1601s
D Low Power:
330mW at 1.25MSPS
145mW at 625kSPS
Power-Down Mode
APPLICATIONS
D Sonar
D Vibration Analysis
D Data Acquisition
VREFP VREFN RBIASVMID VCAP AVDD DVDD IOVDD
Referenceand Bias Circuits
AINP
AINN
Modulator
ADS1601
∆Σ
FIR Digital Filter
InterfaceLinear Phase
Serial
DGNDAGND
CLK
SYNC
FSO
FSO
SCLK
SCLK
DOUT
DOUT
OTR
PD
REFEN
DESCRIPTION
The ADS1601 is a high-speed, high-precision,
delta-sigma analog-to-digital converter (ADC)
manufactured on an advanced CMOS process. The
ADS1601 oversampling topology reduces clock jitter
sensitivity during the sampling of high-frequency, large
amplitude signals by a factor of four over that achieved by
Nyquist-rate ADCs. Consequently, signal-to-noise ratio
(SNR) is particularly improved. Total harmonic distortion
(THD) is −103dB, and the spurious-free dynamic range
(SFDR) is 105dB.
Optimized for power and performance, the ADS1601
dissipates only 330mW while providing a full-scale
differential input range of ±3V. Having such a wide input
range makes out-of-range signals unlikely. The OTR pin
indicates if an analog input out-of-range condition does
occur. Th e d i fferential input signal is measured against the
differential reference, which can be generated internally or
supplied externally on the ADS1601.
The ADS1601 uses an inherently stable advanced
modulator with an on-chip decimation filter. The filter stop
band extends to 19.3MHz, which greatly simplifies the
anti-aliasing circuitry. The modulator samples the input
signal up to 20MSPS, depending on f
decimation filter uses a series of four half-band FIR filter
stages to provide 75dB of stop band attenuation and
0.001dB of passband ripple.
Output data is provided over a simple 3-wire serial
interface at rates up to 1.25MSPS, with a −3dB bandwidth
of 615kHz. The output data or its complementary format
directly connects to DSPs such as TI’s TMS320 family,
FPGAs, or ASICs. A dedicated synchronization pin
enables simultaneous sampling with multiple ADS1601s
in multi-channel systems. Power dissipation is set by an
external resistor that allows a reduction in dissipation
when operating at slower speeds. All of the ADS1601
features are controlled by dedicated I/O pins, which
simplify operation by eliminating the need for on-chip
registers.
The high performing, easy-to-use ADS1601 is especially
suitable for demanding measurement applications in
sonar, vibration analysis, and data acquisition. The
ADS1601 is offered in a small, 7mm x 7mm TQFP-48
package and is specified from −40°C to +85°C.
, while the 16x
CLK
semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
! "# $ %& $ " '&(% ) )&%$
%"# $'%"%$ ' * #$ " +$ $&#$ $)) ,-
)&% '%$$ )$ %$$- %&) $ " '#$
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Copyright 2004, Texas Instruments Incorporated
SBAS322 − DECEMBER 2004
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PACKAGE/ORDERING INFORMATION
For the most current package and ordering information see
the Package Option Addendum located at the end of this
datasheet.
ABSOLUTE MAXIMUM RATINGS
over operat i n g f ree-air temperature range unless otherwise noted
ADS1601 UNIT
AVDD to AGND −0.3 to +6 V
DVDD to DGND −0.3 to +3.6 V
IOVDD to DGND −0.3 to +6 V
AGND to DGND −0.3 to +0.3 V
Input Current 100mA, Momentary
Input Current 10mA, Continuous
Analog I/O to AGND −0.3 to AVDD + 0.3 V
Digital I/O to DGND −0.3 to IOVDD + 0.3 V
Maximum Junction Temperature +150 °C
Operating Temperature Range −40 to +105 °C
Storage Temperature Range −60 to +150 °C
Lead Tem perature (soldering, 10s) +260 °C
(1)
Stresses above these ratings may cause permanent damage.
Exposure to absolute maximum conditions for extended periods
may degrade device reliability. These are stress ratings only , an d
functional operation of the device at these or any other conditions
beyond those specified is not implied.
(1)
This integrated circuit can be damaged by ESD. Texas
Instruments recommends that all integrated circuits be
handled with appropriate precautions. Failure to observe
proper handling and installation procedures can cause damage.
ADS1601 passes standard 200V machine model and 1.5K CDM
testing. ADS1601 passes 1kV human body model testing (TI Standard
is 2kV).
ESD damage can range from subtle performance degradation to
complete device failure. Precision integrated circuits may be more
susceptible t o damage because very small parametric changes could
cause the device not to meet its published specifications.
2
Signal-to-noise ratio (SNR)
Total harmonic distortion (THD)
Signal-to-noise + distortion (SINAD)
Spurious-free dynamic range (SFDR)
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SBAS322 − DECEMBER 2004
ELECTRICAL CHARACTERISTICS
All specifications at TA = −40°C to +85°C, AVDD = 5V, DVDD = IOVDD = 3V, f
unless otherwise noted.
PARAMETER TEST CONDITIONS MIN TYP MAX UNIT
Analog Input
Differential input voltage (VIN)
(AINP − AINN)
Common-mode input voltage (VCM)
(AINP + AINN) / 2
Differential input voltage (VIN)
(AINP or AINN with respect to AGND)
Dynamic Specifications
Data Rate
Signal-to-noise ratio (SNR)
Total harmonic distortion (THD)
Signal-to-noise + distortion (SINAD)
Spurious-free dynamic range (SFDR)
Intermodulation distortion (IMD)
Aperture delay 4 ns
0dBFS ±V
0dBFS −0.1 3.5 V
fIN = 10kHz, −1dBFS 92 dB
fIN = 10kHz, −3dBFS 87 90 dB
fIN = 10kHz, −6dBFS 84 87 dB
fIN = 100kHz, −1dBFS 92 dB
fIN = 100kHz, −3dBFS 87 90 dB
fIN = 100kHz, −6dBFS 84 87 dB
fIN = 500kHz, −1dBFS 91 dB
fIN = 500kHz, −3dBFS 89 dB
fIN = 500kHz, −6dBFS 87 dB
fIN = 10kHz, −1dBFS −91 dB
fIN = 10kHz, −3dBFS −100 −90 dB
fIN = 10kHz, −6dBFS −104 −97 dB
fIN = 100kHz, −1dBFS −88 dB
fIN = 100kHz, −3dBFS −96 −90 dB
fIN = 100kHz, −6dBFS −103 −96 dB
fIN = 500kHz, −1dBFS −115 dB
fIN = 500kHz, −3dBFS −112 dB
fIN = 500kHz, −6dBFS −110 dB
fIN = 10kHz, −1dBFS 88 dB
fIN = 10kHz, −3dBFS 85 89 dB
fIN = 10kHz, −6dBFS 84 87 dB
fIN = 100kHz, −1dBFS 87 dB
fIN = 100kHz, −3dBFS 85 88 dB
fIN = 100kHz, −6dBFS 84 86 dB
fIN = 500kHz, −1dBFS 91 dB
fIN = 500kHz, −3dBFS 89 dB
fIN = 500kHz, −6dBFS 87 dB
fIN = 10kHz, −1dBFS 92 dB
fIN = 10kHz, −3dBFS 91 100 dB
fIN = 10kHz, −6dBFS 98 109 dB
fIN = 100kHz, −1dBFS 88 dB
fIN = 100kHz, −3dBFS 90 97 dB
fIN = 100kHz, −6dBFS 97 105 dB
fIN = 500kHz, −1dBFS 120 dB
fIN = 500kHz, −3dBFS 118 dB
fIN = 500kHz, −6dBFS 115 dB
f1 = 499kHz, −6dBFS
f2 = 501kHz, −6dBFS
= 20MHz, V
CLK
= +3V , VCM = +2.7V , and R
REF
ADS1601
REF
2.7 V
f
CLK
ǒ
1.25
20MHz
94 dB
= 60kΩ,
BIAS
Ǔ
V
MSPS
3
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SBAS322 − DECEMBER 2004
ELECTRICAL CHARACTERISTICS (continued)
All specifications at TA = −40°C to +85°C, AVDD = 5V, DVDD = IOVDD = 3V, f
unless otherwise noted.
PARAMETER UNITMAXTYPMINTEST CONDITIONS
Digital Filter Characteristics
Passband 0
Passband ripple ±0.001 dB
−0.1dB attenuation
Passband transition
−3.0dB attentuation
Stop band
Stop band attenuation 75 dB
Group delay
Settling time Complete settling
Static Specifications
Resolution 16 Bits
No missing codes 16 Bits
Input-referred noise 0.5 0.75 LSB, rms
Integral nonlinearity −0.5dBFS signal 0.75 LSB
Differential nonlinearity 0.25 LSB
Offset error −0.05 %FSR
Offset error drift 0.5 ppmFSR/°C
Gain error 0.25 %
Gain error drift Excluding reference drift 10 ppm/°C
Common-mode rejection At DC 75 dB
Power-supply rejection At DC 65 dB
Internal Voltage Reference REFEN = low
V
= (VREFP − VREFN) 2.75 3 3.25 V
REF
VREFP 3.5 3.8 4.1 V
VREFN 0.5 0.8 1.1 V
VMID 2.3 2.4 2.6 V
V
drift 50 ppm/°C
REF
Startup time 15 ms
External Voltage Reference REFEN = High
V
= (VREFP − VREFN) 2.0 3 3.25 V
REF
VREFP 3.5 4 4.25 V
VREFN 0.5 1 1.5 V
VMID 2.3 2.5 2.6 V
= 20MHz, V
CLK
= +3V , VCM = +2.7V , and R
REF
ADS1601
f
CLK
ǒ
575
20MHz
f
CLK
ǒ
615
20MHz
f
CLK
ǒ
20MHz
Ǔ
20MHZ
ǒ
20.8
f
CLK
20MHZ
ǒ
40.8
f
CLK
0.7
= 60kΩ,
BIAS
f
CLK
ǒ
550
20MHz
Ǔ
Ǔ
f
CLK
ǒ
19.3
20MHz
Ǔ
Ǔ
kHz
Ǔ
kHz
kHz
MHz
Ǔ
µs
µs
4
Power dissipation
Power dissipation
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SBAS322 − DECEMBER 2004
ELECTRICAL CHARACTERISTICS (continued)
All specifications at TA = −40°C to +85°C, AVDD = 5V, DVDD = IOVDD = 3V, f
unless otherwise noted.
PARAMETER UNITMAXTYPMINTEST CONDITIONS
Clock Input
Frequency (f
Duty Cycle f
Digital Input/Output
V
IH
V
IL
V
OH
V
OL
Input leakage DGND < V
Power-Supply Requirements
AVDD 4.75 5.25 V
DVDD 2.7 3.3 V
IOVDD IOH = 50µA 2.7 5.25 V
AVDD current (I
DVDD current (I
IOVDD current (I
Temperature Range
Specified −40 +85 °C
Operating −40 +105 °C
Storage −60 +150 °C
) 20 MHz
CLK
= 20MHz 45 55 %
CLK
IOH = 50µA IOVDD − 0.5 V
IOL = 50µA DGND + 0.5 V
< IOVDD ±10 µA
DIGIN
)
AVDD
) IOVDD = 3V 15 18 mA
DVDD
) IOVDD = 3V 3 8 mA
IOVDD
REFEN = low 65 77 mA
REFEN = high 55 65 mA
AVDD = 5V, DVDD = 3V,
IOVDD = 3V, REFEN
PD = low, CLK disabled 10 mW
= high
= 20MHz, V
CLK
= +3V , VCM = +2.7V , and R
REF
BIAS
= 60kΩ,
ADS1601
0.7 IOVDD IOVDD V
DGND 0.3 IOVDD V
330 380 mW
5
SBAS322 − DECEMBER 2004
DEFINITIONS
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Absolute Input Voltage
Absolute input voltage, given in volts, is the voltage of each
analog input (AINN or AINP) with respect to AGND.
Aperture Delay
Aperture delay is the delay between the rising edge of CLK
and the sampling of the input signal.
Common-Mode Input Voltage
Common-mode input voltage (VCM) is the average voltage
of the analog inputs:
(AINP ) AINN)
2
Differential Input Voltage
Differential input voltage (VIN) is the voltage difference
between the analog inputs (AINP−AINN).
Differential Nonlinearity (DNL)
DNL, given in least-significant bits of the output code
(LSB), is the maximum deviation of the output code step
sizes from the ideal value of 1LSB.
Full-Scale Range (FSR)
FSR is the difference between the maximum and minimum
measurable input signals (FSR = 2V
REF
).
Gain Error
Gain error, given in %, is the error of the full-scale input
signal with respect to the ideal value.
Gain Error Drift
Gain error drift, given in ppm/_C, is the drift over
temperature of t h e g a i n e r r o r. The gain error is specified as
the larger of the drift from ambient (T = 25_C) to the
minimum or maximum operating temperatures.
Integral Nonlinearity (INL)
INL, given in least-significant bits of the output code (LSB),
is the maximum deviation of the output codes from a best
fit line.
Intermodulation Distortion (IMD)
IMD, given in dB, is measured while applying two input
signals of the same magnitude, but with slightly different
frequencies. It is calculated as the difference between the
rms amplitude of the input signal to the rms amplitude of
the peak spurious signal.
Offset Error
Offset Error , given in % of FSR, is the output reading when
the differential input is zero.
Offset Error Drift
Offset error drift, given in ppm of FSR/_C, is the drift over
temperature of the of fset error. The offset error is specified
as the larger of the drift from ambient (T = 25_C) to the
minimum or maximum operating temperatures.
Signal-to-Noise Ratio (SNR)
SNR, given in dB, is the ratio of the rms value of the input
signal to the sum of all the frequency components below
f
/2 (the Nyquist frequency) excluding the first six
CLK
harmonics of the input signal and the dc component.
Signal-to-Noise and Distortion (SINAD)
SINAD, given in dB, is the ratio of the rms value of the input
signal to the sum of all the frequency components below
f
/2 (the Nyquist frequency) including the harmonics of
CLK
the input signal but excluding the dc component.
Spurious-Free Dynamic Range (SFDR)
SFDR, given in dB, is the difference between the rms
amplitude of the input signal to the rms amplitude of the
peak spurious signal.
Total Harmonic Distortion (THD)
THD, given in dB, is the ratio of the sum of the rms value
of the first six harmonics of the input signal to the rms value
of the input signal.
6
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FUNCTION
DESCRIPTION
PIN ASSIGNMENTS
VREFP
VREFP
VMID
VREFN
VREFN
VCAP
AVDD
AGND
CLK
AGND
48 47 46 45 44 43 42 41 40 39 38
SBAS322 − DECEMBER 2004
DGND
IOVDD
TQFP PACKAGE
(TOP VIEW)
AGND
AVDD
AGND
AINN
AINP
AGND
AVDD
RBIAS
AGND
AVDD
AGND
AVDD
1
2
3
4
5
6
7
8
9
10
11
12
13 14 15 16 17 18 19 20 21 22 233724
NC
REFEN
ADS1601
PD
NC
RPULLUP
DVDD
DGND
SYNC
OTR
DVDD
DGND
NC
36
DGND
35
NC
34
DVDD
33
DGND
32
FSO
31
FSO
30
DOUT
29
DOUT
28
SCLK
27
SCLK
26
NC
25
NC
Terminal Functions
TERMINAL
NAME NO.
AGND 1, 3, 6, 9, 11, 39, 41 Analog Analog ground
AVDD 2, 7, 10, 12, 42 Analog Analog supply
AINN 4 Analog input Negative analog input
AINP 5 Analog input Positive analog input
RBIAS 8 Analog Terminal for external analog bias setting resistor.
REFEN 13 Digital input: active low Internal reference enable. Internal pull-down resistor of 170kΩ to DGND.
NC 14, 16, 24−26, 35 Do not connect These terminals must be left unconnected.
RPULLUP 15 Digital Input Pull-up to DVDD with 10kΩ resistor (see Figure 50).
PD 17 Digital input: active low Power down all circuitry. Internal pull-up resistor of 170kΩ to DGND.
DVDD 18, 23, 34 Digital Digital supply
DGND 19, 22, 33, 36, 38 Digital Digital ground
SYNC 20 Digital input Synchronization control input
OTR 21 Digital output Indicates analog input signal is out of range.
SCLK 28 Digital output Serial clock output
SCLK 27 Digital output Serial clock output, complementary signal.
DOUT 30 Digital output Data output
DOUT 29 Digital output Data output, complementary signal.
FSO 32 Digital output Frame synchronization output
FSO 31 Digital output Frame synchronization output, complementary signal.
IOVDD 37 Digital Digital I/O supply
CLK 40 Digital input Clock input
VCAP 43 Analog Terminal for external bypass capacitor connection to internal bias voltage.
VREFN 44, 45 Analog Negative reference voltage
VMID 46 Analog Midpoint voltage
VREFP 47, 48 Analog Positive reference voltage
7
t
Settling time of ADS1601
(1)
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SBAS322 − DECEMBER 2004
TIMING DIAGRAMS
CLK
t
STL
SYNC
FSO
TIMING REQUIREMENTS
For TA = −40°C to +85°C, DVDD = 2.7V to 3.6V, IOVDD = 2.7V to 5.25V.
SYMBOL DESCRIPTION MIN TYP MAX UNIT
t
SYPW
STL
NOTE: (1) An FSO pulse occuring prior to T
SYNC positive pulse width
t
SYPW
Figure 1. Initialization Timing
≥ 816 CLK period should be ignored.
STL
2 16 CLK periods
51 52 Conversions
816 832 CLK periods
t
DPD
t
CPW
t
CPW
Bit 1 Bit 0 (LSB)Bit 15 (MSB) Bit14
New Data
CLK
FSO
SCLK
DOUT
t
C
t
CF
t
FPW
t
CS
t
DHD
Bit 0 (LSB)
Old Data
Figure 2. Data Retrieval Timing
TIMING REQUIREMENTS
For TA = −40°C to +85°C, DVDD = 2.7V to 3.6V, IOVDD = 2.7V to 5.25V.
SYMBOL DESCRIPTION MIN TYP MAX UNIT
t
t
CPW
t
CF
t
FPW
t
CS
t
DHD
t
DPD
C
CLK period (1/f
CLK
)
CLK positive or negative pulse width
Rising edge of CLK to rising edge of FSO
FSO positive pulse width
Rising edge of CLK to rising edge of SCLK
SCLK rising edge to old DOUT invalid (hold time)
SCLK rising edge to new DOUT valid (propagation delay)
50 ns
25 ns
15 ns
1 CLK period
15 ns
0 ns
5 ns
8
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SPECTRAL RESPONSE
SPECTRAL RESPONSE
SPECTRAL RESPONSE
SPECTRAL RESPONSE
SPECTRAL RESPONSE
SPECTRAL RESPONSE
TYPICAL CHARACTERISTICS
All specifications at TA = 25°C, AVDD = 5V, DVDD = IOVDD = 3V, f
otherwise noted.
= 20MHz, V
CLK
= +3V , VCM = +2.7V , and R
REF
SBAS322 − DECEMBER 2004
= 60kΩ, unless
BIAS
0
−
20
−
40
−
60
−
80
−
100
Amplitude (dB)
−
120
−
140
−
160
0 100 200 300
0
−
20
−
40
−
60
−
80
−
100
Amplitude (dB)
−
120
−
140
−
160
0 100 200 300
Frequency (kHz)
Figure 3
Frequency (kHz)
fIN= 10kHz,−1dBFS
SNR = 92dB
THD =−91dB
SFDR = 92dB
400 500 600
fIN= 10kHz,−10dBFS
SNR = 83dB
THD =−106dB
SFDR = 111dB
400 500 600
0
−
20
−
40
−
60
−
80
−
100
Amplitude (dB)
−
120
−
140
−
160
0 100 200 300
0
−
20
−
40
−
60
−
80
−
100
Amplitude (dB)
−
120
−
140
−
160
0 100 200 300
fIN=10kHz,−6dBFS
SNR = 87dB
THD =−108dB
SFDR = 111dB
400 500 600
Frequency (kHz)
Figure 4
fIN= 100kHz,−1dBFS
SNR = 92dB
THD =−88dB
SFDR = 88dB
400 500 600
Frequency (kHz)
0
−
20
−
40
−
60
−
80
−
100
Amplitude (dB)
−
120
−
140
−
160
0 100 200 300
Figure 5
Frequency (kHz)
Figure 7
fIN= 100kHz,−6dBFS
SNR = 87dB
THD =−103dB
SFDR = 105dB
400 500 600
Figure 6
0
−
20
−
40
−
60
−
80
−
100
Amplitude (dB)
−
120
−
140
−
160
0100200300
Figure 8
fIN= 100kHz,−10dBFS
SNR = 83dB
THD =−103dB
SFDR= 105dB
400 500 600
Frequency (kHz)
9
SPECTRAL RESPONSE
SPECTRAL RESPONSE
SPECTRAL RESPONSE
SNR, THD, and SFDR vs INPUT SIGNAL AMPLITUDE
SNR, THD, and SFDR vs INPUT SIGNALAMPLITUDE
Figure 14
SNR, THD, and SFDR vs INPUT SIGNALAMPLITUDE
SBAS322 − DECEMBER 2004
TYPICAL CHARACTERISTICS (continued)
All specifications at TA = 25°C, AVDD = 5V, DVDD = IOVDD = 3V, f
otherwise noted.
= 20MHz, V
CLK
= +3V , VCM = +2.7V , and R
REF
= 60kΩ, unless
BIAS
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0
fIN= 504kHz,−1dBFS
−
20
SNR = 91dB
THD =−117dB
−
40
SFDR = 122dB
−
60
−
80
−
100
Amplitude (dB)
−
120
−
140
−
160
0
100 200 300
Frequency (kHz)
400 500 600
Figure 9
0
fIN= 504kHz,−10dBFS
−
20
SNR = 83dB
THD =−110dB
−
40
SFDR = 117dB
−
60
−
80
−
100
Amplitude (dB)
−
120
−
−
140
160
0
100 200 300
400 500 600
Frequency (kHz)
SIGNAL−TO−NOISE RATIO,
Figure 11
−
−
−
−
−
100
Amplitude (dB)
−
120
−
140
−
160
140
120
100
TOTALHARMONIC DISTORTION,
SPURIOUS−FREE DYNAMIC RANGE (dB)
0
fIN= 504kHz,−6dBFS
20
SNR = 86dB
THD =−110dB
40
SFDR = 115dB
60
80
0
80
60
40
20
−80−70−
100 200 300
Frequency (kHz)
400 500 600
Figure 10
SFDR
THD
60−50−40−30−20−10 0
Input Signal Amplitude, V
(dB)
IN
Figure 12
SNR
fIN=10kHz
140
120
100
SIGNAL−TO−NOISE RATIO,
TOTAL HARMONIC DISTORTION,
SPURIOUS−FREE DYNAMIC RANGE (dB)
80
60
40
20
−
80−70−60−50−40−30−20−10 0
Input Signal Amplitude, V
SFDR
Figure 13
10
THD
IN
SNR
fIN=100kHz
(dB)
140
120
100
80
60
SIGNAL−TO−NOISE RATIO,
40
TOTALHARMONIC DISTORTION,
20
SPURIOUS−FREE DYNAMIC RANGE (dB)
−80−70−
SFDR
THD
SNR
fIN= 500kHz
60−50−40−30−20−10 0
Input Signal Amplitude, V
(dB)
IN
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SIGNAL−TO−NOISERATIO
TOTAL HARMONIC DISTORTION
SPURIOUS−FREE DYNAMIC RANGE
SIGNAL−TO−NOISERATIO
TOTAL HARMONIC DISTORTION
SPURIOUS−FREE DYNAMICRANGE
TYPICAL CHARACTERISTICS (continued)
All specifications at TA = 25°C, AVDD = 5V, DVDD = IOVDD = 3V, f
otherwise noted.
= 20MHz, V
CLK
= +3V , VCM = +2.7V , and R
REF
SBAS322 − DECEMBER 2004
= 60kΩ, unless
BIAS
100
95
90
85
SNR (dB)
80
75
70
10k 100k 1M
vs INPUT FREQUENCY
VIN=−1dB
V
IN
V
IN
InputFrequency,f
(Hz)
IN
=−6dB
=−10dB
Figure 15
120
VIN=−10dB
110
V
=−6dB
IN
100
SFDR (dB)
90
V
=−1dB
IN
vs INPUT FREQUENCY
−
80
VIN=−1dB
−
90
−
100
THD (dB)
VIN=−10dB
−
110
V
=−6dB
IN
−
120
10k 100k 1M
vs INPUT FREQUENCY
InputFrequency,f
(Hz)
IN
Figure 16
vs INPUT COMMON−MODE VOLTAGE
fIN=10kHz,VIN=−1dB
fIN= 100kHz, VIN=−6dB
fIN= 100kHz, VIN=−1dB
fIN= 10kHz, VIN=−6dB
SNR (dB)
100
95
90
85
80
75
80
10k 100k 1M
Input Frequency, fIN(Hz)
Figure 17
−
80
−
90
−
100
THD (dB)
−
110
−
120
1.0 1.4 1.8 2.2 2.6 3.0 3.4
vs INPUT COMMON−MODE VOLTAGE
fIN= 100kHz, VIN=−1dB
fIN=10kHz,VIN=−1dB
fIN=10kHz,VIN=−6dB
fIN= 100kHz, VIN=−6dB
Input Common−Mode Voltage, VCM(V)
Figure 19
70
1.01.41.82.22.63.03.4
Input Common−Mode Voltage, VCM(V)
Figure 18
120
110
100
SFDR (dB)
90
80
1.0 1.4 1.8 2.2 2.6 3.0 3.4
vs INPUT COMMON−MODE VOLTAGE
fIN=10kHz,VIN=−6dB
fIN= 10kHz, VIN=−1dB
Input Common−Mode Voltage, VCM(V)
fIN= 100kHz, VIN=−6dB
fIN= 100kHz,VIN=−1dB
Figure 20
11
SIGNAL−TO−NOISERATIO
TOTAL HA RMONIC DISTORTION
SPURIOUS−FREE DYNAMIC RANGE
OFFSETDRIFT OVER TIME
SBAS322 − DECEMBER 2004
TYPICAL CHARACTERISTICS (continued)
All specifications at TA = 25°C, AVDD = 5V, DVDD = IOVDD = 3V, f
otherwise noted.
= 20MHz, V
CLK
= +3V , VCM = +2.7V , and R
REF
= 60kΩ, unless
BIAS
www.ti.com
100
95
90
85
SNR (dB)
80
75
VIN=−6dBFS,fIN=10kHz
70
0 5 10 15 20
vs CLOCK FREQUENCY
=210k
= 267k
Ω
Ω
R
BIAS
R
BIAS
Clock Frequency, f
CLK
R
(MHz)
Figure 21
120
110
100
SFDR (dB)
90
VIN=−6dBFS, fIN=10kHz
80
0 5 10 15 20
vs CLOCK FREQUENCY
R
BIAS
Ω
=60k
R
= 210k
BIAS
Clock Frequency, f
CLK
Ω
(MHz)
R
BIAS
R
BIAS
Figure 23
R
BIAS
BIAS
= 140k
=267k
=60k
= 140k
Ω
−
80
VIN=−6dBFS, fIN= 10kHz
−
Ω
Ω
90
−
100
THD (dB)
−
110
−
120
0 5 10 15 20
vs CLOCK FREQUENCY
R
BIAS
=267k
Ω
Ω
CLK
R
BIAS
R
= 60k
BIAS
Clock Frequency, f
=210k
(MHz)
Ω
= 140k
Ω
R
BIAS
Figure 22
NOISE vs DC INPUT VOLTAGE
RMS Noise (LSB)
1000
100
10
0.1
1
−
−
3
−
2
13012
Input DC Voltage (V)
Ω
Figure 24
12
1500
1400
1300
1200
1100
1000
900
800
700
600
Occurrences
500
400
300
200
100
0
−
−3−2−
4
NOISE HISTOGRAM
Output Code (LSB)
Figure 25
VIN=0V
101 2 34
3
2
1
0
−
1
Offset (LSB)
−
2
−
3
−
4
0 100 200 300 400 500 600 700 800 900 1000
Time Interval (s)
Figure 26
www.ti.com
POWER−SUPPLY CURRENT
ANALOG SUPPLYCURRENTvs R
SIGNAL−TO−NOISE RATIO vs TEMPERATURE
SPURIOUS−FREE DYNAMIC RANGE
TYPICAL CHARACTERISTICS (continued)
All specifications at TA = 25°C, AVDD = 5V, DVDD = IOVDD = 3V, f
otherwise noted.
= 20MHz, V
CLK
= +3V , VCM = +2.7V , and R
REF
SBAS322 − DECEMBER 2004
= 60kΩ, unless
BIAS
80
70
60
50
40
30
Current (mA)
20
10
R
=60kΩ,f
BIAS
0
−
40
−
vs TEMPERATURE
I
(REFEN = l ow)
AVDD
I
(REFEN = high)
AVDD
I
DVDD+IIOVDD
=20MHz
CLK
15 10 35 60 85
Temperature (_C)
Figure 27
70
(mA)
60
AVDD
50
40
30
20
Analog SupplyCurrent, I
10
0 50 100 150 200 250 300
R
I
AVDD
BIAS
I
(REFEN = low)
AVDD
(REFEN = high)
Ω
(k
)
f
CLK
BIAS
=20MHz
80
70
60
50
40
30
Supply Current (mA)
20
10
0
SUPPLY−CURRENT vs CLOCK FREQUENCY
I
(REFEN= low)
AVDD
I
(REFEN = high)
AVDD
I
IOVDD+IDVDD
R
BIAS
0 5 10 15 20 25
Clock Frequency, f
CLK
(MHz)
Figure 28
100
95
90
85
SNR (dB)
80
75
fIN=100kHz
70
−
40
−
15 10 35 60 85
Temperature (_C)
Ω
=60k
VIN=−1dB
VIN=−6dB
VIN=−10dB
Figure 29
TOTALHARMONIC DISTORTION vs TEMPERATURE
−
80
VIN=−1dB
−
90
V
=−6dB
IN
−
100
THD (dB)
−
−
110
120
VIN=−10dB
−
40
−
15 10 35 60 85
Temperature (_C)
Figure 31
fIN=100kHz
SFDR (dB)
120
110
100
90
80
VIN=−6dB
V
IN
−
40
Figure 30
vs TEMPERATURE
VIN=−10dB
=−1dB
−
15 10 35 60 85
Temperature (_C)
Figure 32
fIN=100kHz
13
V
vs TEMPERATURE
INTERMODULATION RESPONSE
SBAS322 − DECEMBER 2004
TYPICAL CHARACTERISTICS (continued)
All specifications at TA = 25°C, AVDD = 5V, DVDD = IOVDD = 3V, f
otherwise noted.
= 20MHz, V
CLK
= +3V , VCM = +2.7V , and R
REF
= 60kΩ, unless
BIAS
www.ti.com
3
2.99
2.98
2.97
2.96
(V)
2.95
REF
V
2.94
2.93
2.92
2.91
2.90
−
40
REF
−
15 10 35 60 85
Temperature (_C)
Figure 33
0
−
20
−
40
−
60
−
80
Amplitude (dB)
−
100
−
120
−
140
480 485 490 495 500 505 510 515 520
Frequency (kHz)
Figure 34
f
=499kHz
IN1
=501kHz
f
IN2
IMD =−94dB
14
www.ti.com
SBAS322 − DECEMBER 2004
OVERVIEW
The ADS1601 is a high-performance delta-sigma ADC.
The modulator uses an inherently stable 2-1-1 multi-stage
architecture incorporating proprietary circuitry that allows
for very linear high-speed operation. The modulator
samples the input signal at 20MSPS (when f
A low-ripple linear phase digital filter decimates the
modulator output by 16 to provide high resolution 16-bit
output data.
Conceptually, the modulator and digital filter measure the
differential input signal, V
scaled differential reference, V
= (AINP – AINN), against the
IN
= (VREFP – VREFN),
REF
as shown in Figure 35. The voltage reference can either be
generated internally or supplied externally . A 3-wire serial
interface, designed for direct connection to DSPs, outputs
the data. A separate power supply for the I/O allows flexibility for interfacing to different logic families. Out-of-range
conditions are indicated with a dedicated digital output pin.
Analog power dissipation is controlled using an external
resistor. This control allows reduced dissipation when operating at slower speeds. When not in use, power consumption can be dramatically reduced by setting the PD
pin low to enter Power-Down mode.
ANALOG INPUTS (AINP, AINN)
The ADS1601 measures the differential signal,
V
= (AINP − AINN), against the differential reference,
IN
V
= (VREFP – VREFN). The most positive measurable
REF
differential input is V
, which produces the most positive
REF
= 20MHz).
CLK
digital output code of 7FFFh. Likewise, the most negative
measurable dif ferential input is –V
, which produces the
REF
most negative digital output code of 8000h.
The ADS1601 supports a very wide range of input signals.
For V
= 3V, the full-scale input voltages are ±3V.
REF
Having such a wide input range makes out-of-range
signals unlikely. However, should an out-of-range signal
occur, the digital output OTR will go high.
The analog inputs must be driven with a differential signal
to achieve optimum performance. For the input signal:
V
AINP) AINN
+
CM
2
the recommended common-mode voltage is 2.7V. In
addition to the differential and common-mode input
voltages, the absolute input voltage is also important. This
is the voltage on either input (AINP or AINN) with respect
to AGND. The range for this voltage is:
* 0.1V t (AINN or AIN P) t 4.6V
If either input is taken below –0.1V, ESD protection diodes
on the inputs will turn on. Exceeding 4.6V on either input
will result in degradation in the linearity performance. ESD
protection diodes will also turn on if the inputs are taken
above AVDD (+5V).
The recommended absolute input voltage is:
* 0.1V t (AINN or AIN P) t 4.2V
Keeping the inputs within this range provides for optimum
performance.
AINP
AINN
VREFN IOVDDVREFP
Σ
V
REF
V
IN
Σ
Σ∆
Modulator
Digital
Filter
Serial
Interface
Figure 35. Conceptual Block Diagram
CLK
FSO
FSO
SCLK
SCLK
DOUT
DOUT
15
SBAS322 − DECEMBER 2004
www.ti.com
INPUT CIRCUITRY
The ADS1601 uses switched-capacitor circuitry to measure
the input voltage. Internal capacitors are charged by the
inputs and then discharged internally with this cycle
repeating at the frequency of CLK. Figure 36 shows a
conceptual diagram of these circuits. Switches S2 represent
the net effect of the modulator circuitry in discharging the
sampling capacitors; the actual implementation is different.
The timing for switches S1 and S2 is shown in Figure 37.
ADS1601
8pF
VMID
8pF
VMID
S
2
S
2
AINP
AINN
AGND
S
10pF
S
10pF
1
1
Figure 36. Conceptual Diagram of Internal
Circuitry Connected to the Analog Inputs
t
=1/f
S1
S2
SAMPLE
On
Off
On
Off
CLK
external capacitors, between the inputs and from each
input to AGND, improve linearity and should be placed as
close to the pins as possible. Place the drivers close to the
inputs and use good capacitor bypass techniques on their
supplies, such as a smaller high-quality ceramic capacitor
in parallel with a larger capacitor. Keep the resistances
used in the driver circuits low—thermal noise in the driver
circuits degrades the overall noise performance. When the
signal can be ac-coupled to the ADS1601 inputs, a simple
RC filter can set the input common-mode voltage. The
ADS1601 is a high-speed, high-performance ADC.
Special care must be taken when selecting the test
equipment and setup used with this device. Pay particular
attention to the signal sources to ensure they do not limit
performance when measuring the ADS1601.
Ω
392
Ω
392
V
IN
−
2
Ω
392
(1)
V
CM
Ω
Ω
392
V
IN
2
Ω
392
(1)
V
CM
Ω
(1) Recom mended VCM=2.7V.
(2) Optionalac−coupling circuit provides common−mode input voltage.
(3) Increaseto 390pF whenf
40pF
0.01µF
1k
V
CM
1k
0.01µF
49.9
(2)
100pF
Ω
(2)
(1)
100pF
(2)
Ω
49.9
(2)
100pF
OPA2822
1µF392
Ω
392
40pF
OPA2822
1µF392
≤ 100kHz for improvedSNR and THD.
IN
Ω
Ω
AGND
AINP
(3)
ADS1601
AINN
Figure 38. Recommended Driver Circuit Using the
OPA2822
Figure 37. Timing for the Switches in Figure 36
DRIVING THE INPUTS
The external ci rcuits driving the ADS1601 inputs must be
able to h andle t he l oad p resented b y the switching capacitors
within the ADS1601. The input switches S1 in Figure 36 are
closed for approximately one-half of the sampling period,
t
, allowing only ≈ 24ns for the internal capacitors to be
sample
charged by the inputs when f
= 20MHz.
CLK
Figure 38 and Figure 39 show the recommended circuits
when using single-ended or differential op amps,
respectively. The analog inputs must be driven
differentially to achieve optimum performance. The
16
22pF
Ω
+V
24.9
Ω
Ω
392
−
V
IN
IN
392
V
CM
Ω
392
THS4503
392
22pF
Ω
24.9
100pF
100pF
Ω
100pF
AINP
ADS1601
AINN
Figure 39. Recommended Driver Circuit Using the
THS4503 Differential Amplifier
www.ti.com
SBAS322 − DECEMBER 2004
REFERENCE INPUTS (VREFN, VREFP, VMID)
The ADS1601 can operate from an internal or external
voltage reference. In either case, the reference voltage
V
is set by the differential voltage between VREFN a nd
REF
VREFP: V
= (VREFP – VREFN). VREFP and VREFN
REF
each use two pins, which should be shorted together.
VMID equals approximately 2.5V and is used by the
modulator. VCAP connects to an internal node and must
also be bypassed with an external capacitor.
INTERNAL REFERENCE (REFEN = LOW)
To use the internal reference, set the REFEN pin low. This
activates the internal circuitry that generates the reference
voltages. The internal reference voltages are applied to
the pins. Good bypassing of the reference pins is critical
to achieve optimum performance and is done by placing
the bypass capacitors as close to the pins as possible.
Figure 40 shows the recommended bypass capacitor
values. Use high-quality ceramic capacitors for the smaller
values. Avoid loading the internal reference with external
circuitry. I f the ADS1601 internal reference is to be used by
other circuitry, buffer the reference voltages to prevent
directly loading the reference pins.
ADS1601
VREFP
10µF
0.1µF
10µF 0.1µF
10µF 0.1µF
0.1µF
AGND
VREFP
VMID
VREFN
VREFN
VCAP
0.1µF
Figure 40. Reference Bypassing When Using the
Internal Reference
of providing both a dc and a transient current. Figure 41
shows a simplified diagram of the internal circuitry of the
reference when the internal reference is disabled. As with
the input circuitry, switches S1 and S2 open and close as
shown by the timing in Figure 37.
ADS1601
S
VREFP
VREFP
VREFN
VREFN
1
S
Ω
S
1
50pF300
2
Figure 41. Conceptual Internal Circuitry for the
Reference When REFEN = High
Figure 42 shows the recommended circuitry for driving
these reference inputs. Keep the resistances used in the
buffer circuits low to prevent excessive thermal noise from
degrading performance. Layout of these circuits is critical;
be sure to follow good high-speed layout practices. Place
the buffers, and especially the bypass capacitors, as close
to the pins as possible. VCAP is unaffected by the setting
on REFEN
and must be bypassed when using the internal
or an external reference.
392Ω
0.001µF
ADS1601
VREFP
VREFP
0.1µF
VMID
0.1µF
VREFN
VREFN
2.5V
OPA2822
4V
392Ω
0.001µF
OPA2822
392Ω
0.001µF
OPA2822
1V
10µF
0.1µF
10µF
10µF 0.1µF
EXTERNAL REFERENCE (REFEN = HIGH)
To use an external reference, set the REFEN pin high. This
deactivates the internal generators for VREFP, VREFN
and VMID, and saves approximately 25mA of current on
the analog supply (AVDD). The voltages applied to these
pins must be within the values specified in the Electrical
Characteristics table. Typically, VREFP = 4V, VMID = 2.5V
and VREFN = 1V. The external circuitry must be capable
VCAP
0.1µF
AGND
Figure 42. Recommended Buffer Circuit When
Using an External Reference
17
ALLOWABLE
SBAS322 − DECEMBER 2004
www.ti.com
CLOCK INPUT (CLK)
The ADS1601 requires an external clock signal to be
applied to the CLK input pin. The sampling of the
modulator is controlled by this clock signal. As with any
high-speed data converter, a high quality clock is essential
for optimum performance. Crystal clock oscillators are the
recommended CLK source; other sources, such as
frequency synthesizers, are usually inadequate. Make
sure to avoid excess ringing on the CLK input; keeping the
trace as short as possible will help.
Measuring high-frequency, large amplitude signals
requires tight control of clock jitter. The uncertainty during
sampling of the input from clock jitter limits the maximum
achievable SNR. This effect becomes more pronounced
with higher frequency and larger magnitude inputs.
Fortunately, the ADS1601 oversampling topology reduces
clock jitter sensitivity over that of Nyquist rate converters
such as pipeline and successive approximation
converters by a factor of
Ǹ
16
.
In order to not limit the ADS1601 SNR performance, keep
the jitter on the clock source below the values shown in
Table 1. When measuring lower frequency and lower
amplitude inputs, more CLK jitter can be tolerated. In
determining the allowable clock source jitter, select the
worst-case input (highest frequency, largest amplitude)
that will be seen in the application.
Table 1. Maximum Allowable Clock Source Jitter
for Different Input Signal Frequencies and
Amplitude
INPUT SIGNAL
MAXIMUM
FREQUENCY
500kHz −0.5dB 6ps
500kHz −20dB 60ps
100kHz −0.5dB 30ps
100kHz −20dB 300ps
MAXIMUM
AMPLITUDE
MAXIMUM
CLOCK SOURCE
JITTER
DATA FORMAT
The 16-bit output data is in binary two’s complement
format as shown in Table 2. When the input is positive
out-of-range, exceeding the positive full-scale value of
V
, the output clips to all 7FFFh and the OTR output
REF
goes high.
Likewise, when the input is negative out-of-range by going
below the negative full-scale value of –V
, the output
REF
clips to 8000h and the OTR output goes high. The OTR
remains high while the input signal is out-of-range.
Table 2. Output Code Versus Input Signal
INPUT SIGNAL
(INP – INN)
≥ +V
−V
v −V
(1)
Excludes effects of noise, INL, offset and gain errors.
(> 0dB) 7FFFh 1
REF
V
(0dB) 7FFFh 0
REF
+V
REF
215* 1
0 0000h 0
−V
REF
215* 1
15
2
REF
ǒ
REF
215* 1
15
2
ǒ
215* 1
Ǔ
Ǔ
IDEAL OUTPUT
(1)
CODE
0001h 0
FFFFh 0
8000h 0
8000h 1
OTR
OUT-OF-RANGE INDICATION (OTR)
If the output code exceeds the positive or negative
full-scale, the out-of-range digital output OTR will go high
on the falling edge of SCLK. When the output code returns
within the full-scale range, OTR returns low on the falling
edge of SCLK.
DATA RETRIEVAL
Data retrieval is controlled through a simple serial
interface. The interface operates in a master fashion by
outputting both a frame sync indicator (FSO) and a serial
clock (SCLK). Complementary outputs are provided for
the frame sync output (FSO
output (DOUT
). When not needed, leave the
), serial clock (SCLK) and data
complementary outputs unconnected.
18
www.ti.com
SBAS322 − DECEMBER 2004
INITIALIZING THE ADS1601
After the power supplies have stabilized, you must
initialize the ADS1601 by issuing a SYNC pulse as shown
in Figure 1. This operation needs only to be done once
after power-up and does not need to be performed when
exiting the Power-Down mode.
SYNCHRONIZING MULTIPLE ADS1601s
The SYNC input can be used to synchronize multiple
ADS1601s to provide simultaneous sampling. All devices
to be synchronized must use a common CLK input. With
the CLK inputs running, pulse SYNC on the falling edge of
CLK, as shown in Figure 43. Afterwards, the converters
will be converting synchronously with the FSO outputs
updating simultaneously. After synchronization, FSO is
held low until the digital filter has fully settled.
SYNC
CLK
ADS1601
SYNC
CLK
ADS1601
SYNC
CLK
1
FSO
DOUT
2
FSO
DOUT
FSO
DOUT
FSO
DOUT
1
1
2
2
STEP RESPONSE
Figure 44 plots the normalized step response for an input
applied at t = 0. The x-axis units of time are conversions
cycles. It takes 51 cycles to fully settle; for f
= 20MHz,
CLK
this corresponds to 40.8µs.
1.2
1.0
0.8
0.6
0.4
Step Response
0.2
0
−
0.2
010203040
Time(ConversionCycles)
50
Figure 44. Step Response
CLK ...
SYNC
FSO
1
FSO
2
...
t
STL
Figure 43. Synchronizing Multiple Converters
19
SBAS322 − DECEMBER 2004
www.ti.com
FREQUENCY RESPONSE
The linear phase FIR digital filter sets the overall frequency
response. Figure 45 shows the frequency response from
dc to 10MHz for f
= 20MHz. The frequency response
CLK
of the ADS1601 filter scales directly with CLK frequency.
For example, if the CLK frequency is decreased by half (to
10MHz), the values on the X-axis in Figure 45 would need
to be scaled by half, with the span becoming dc to 5MHz.
Figure 46 shows the passband ripple from dc to 600kHz
(f
= 20MHz). Figure 47 shows a closer view of the
CLK
passband transition by plotting the response from 400kHz
to 650kHz (f
20
0
−
20
−
40
−
60
−
80
Magnitude (dB)
−
100
−
120
−
140
= 20MHz).
CLK
f
= 20MHz
CLK
0123 546789
Frequency (MHz)
10
0.5
0
−
0.5
−
1.0
−
1.5
−
2.0
Magnitude (dB)
−
2.5
−
3.0
−
3.5
400 450 500 550 600
Frequency (kHz)
f
CLK
= 20MHz
650
Figure 47. Passband Transition
ANTI−ALIAS REQUIREMENTS
Higher frequency, out-of-band signals must be eliminated
to prevent aliasing with ADCs. Fortunately, the ADS1601
on-chip digital filter greatly simples this filtering
requirement. Figure 48 shows the ADS1601 response out
to 60MHz (f
= 20MHz). Since the stopband extends out
CLK
to 19.3MHz, the anti-alias filter in front of the ADS1601
only needs to be designed to remove higher frequency
signals thatn this, which can usually be accomplished with
a simple RC circuit on the input driver.
Magnitude (dB)
Figure 45. Frequency Response
0.001
0.0008
0.0006
0.0004
0.0002
0
−
0.0002
−
0.0004
−
0.0006
−
0.0008
−
0.001
0 100 200 300
Frequency (kHz)
Figure 46. Passband Ripple
f
= 20MHz
CLK
400 500
600
20
0
−
20
−
40
−
60
−
80
Magnitude (dB)
−
100
−
120
−
140
0 1020304050
Frequency(MHz)
f
CLK
= 20MHz
Figure 48. Frequency Response Out to 120MHz
60
20
www.ti.com
SBAS322 − DECEMBER 2004
ANALOG POWER DISSIPATION
An external resistor connected between the RBIAS pin
and the analog ground sets the analog current level, as
shown in Figure 49. The current is inversely proportional
to the resistor value. Table 3 shows the recommended
values of R
for different CLK frequencies. Notice that
BIAS
the analog current can be reduced when using a slower
frequency CLK input because the modulator has more
time to settle. Avoid adding any capacitance in parallel to
R
, since this will interfere with the internal circuitry
BIAS
used to set the biasing.
ADS1601
RBIAS
R
BIAS
AGND
Figure 49. External Resistor Used to Set Analog
Power Dissipation
Table 3. Recommended R
Different CLK Frequencies
DATA
f
CLK
5MHz 315kSPS 267k 110mW
10MHz 625kSPS 210k 145mW
15MHz 940kSPS 140k 200mW
20MHz 1.25MSPS 60k 325mW
RATE
R
BIAS
Resistor Values for
BIAS
TYPICAL POWER DISSIPATION
WITH REFEN HIGH
POWER DOWN (PD)
When not in use, the ADS1601 can be powered down by
taking the PD
pin low. All circuitry will be shut down,
including the voltage reference. To minimize the digital
current during power down, stop the clock signal supplied
to the CLK input. There is an internal pull-up resistor of
170kΩ on the PD
pin, but it is recommended that this pin
be connected to IOVDD if not used. Make sure to allow
time for the reference to start up after exiting power-down
mode. The internal reference typically requires 15ms.
After the reference has stabilized, allow at least 100
conversions for the modulator and digital filter to settle
before retrieving data.
21
SBAS322 − DECEMBER 2004
www.ti.com
POWER SUPPLIES
Three supplies are used on the ADS1601: analog (AVDD),
digital (DVDD) and digital I/O (IOVDD). Each supply must
be suitably bypassed to achieve the best performance. It
is recommended that a 1µF and 0.1µF ceramic capacitor
be placed as close to each supply pin as possible. Connect
each supply-pin bypass capacitor to the associated
DVDD
47µF4.7µF1µF0.1µF
IOVDD
47µF
AVDD
47µF
4.7µF
4.7µF
If using separate analog and
digital ground planes, connect
together on the ADS1601 PCB.
1µF
1µF
0.1µF
0.1µF
1 36DGND
C
P
2
3
6
ground, as shown in Figure 50. Each main supply bus
should also be bypassed with a bank of capacitors from
47µF to 0.1µF, as shown.
The I/O and digital supplies (IOVDD and DVDD) can be
connected together when using the same voltage. In this
case, only o n e b a n k o f 4 7 µF to 0.1µF capacitors is needed
on the main supply bus, though each supply pin must still
be bypassed with a 1µF and 0.1µF ceramic capacitor.
C
P
42 41 55 38 37 34 33
AGND
AVDD
AGND
AVDD
AGND
C
P
AGND
DGND
C
P
DVDD
IOVDD
DGND
DGND
AGND
NOTE: CP=1µF0.1µF
Figure 50. Recommended Power-Supply Bypassing
C
P
AVDD
7
9
AGND
C
P
AVDD
10
11
AGND
C
P
12
AVDD
RPULLUP
15
18
Ω
10k
ADS1601
DVDD
DGND
19 22 23
C
P
DGND
DVDD
C
P
22
www.ti.com
SBAS322 − DECEMBER 2004
LAYOUT ISSUES AND COMPONENT SELECTION
The ADS1601 is a very high-speed, high-resolution data
converter. In order to achieve maximum performance, the
user must give very careful consideration to both the layout
of the printed circuit board (PCB) in addition to the routing
of the traces. Capacitors that are critical to achieve the
best performance from the device should be placed as
close to the pins of the device as possible. These include
capacitors related the analog inputs, the reference and the
power supplies.
For critical capacitors, it is recommended that Class II
dielectrics such as Z5U be avoided. These dielectrics
have a narrow operating temperature, a large tolerance on
the capacitance and will lose up to 20% of the rated
capacitance over 10,000 hours. Rather, select capacitors
with a Class I dielectric. C0G (also known as NP0), for
example, has a tight tolerance < ±30PPM/°C and is very
stable over time. Should Class II capacitors be chosen
because of the size constraints, select an X7R or X5R
dielectric to minimize the variations of the capacitor’s
critical characteristics.
The resistors used in the circuits driving the input and
reference should be kept as low as possible to prevent
excess thermal noise from degrading the system
performance.
D Full-duplex communication
D Double-buffered data registers
D Independent framing and clocking for reception and
transmission of data
The sequence begins with a one-time synchronization of
the serial port by the microprocessor. The ADS1601
recognizes the SYNC signal if it is high for a least 1 CLK
period. Transfers are initiated by the ADS1601 after the
SYNC signal is de-asserted by the microprocessor.
The FSO signal from the ADS1601 indicates that data is
available to be read, and is connected to the Frame Sync
Receive (FSR) pin of the DSP. The Clock Receiver (CLKR)
is derived directly from the ADS1601 serial clock output to
ensure continued synchronization of data with the clock.
ADS1601
FSO
SCLK
DOUT
TMS320
FSR
CLKR
DR
The digital outputs from the device should always be
buffered. This will have a number of benefits: it will reduce
the loading of the internal digital buffers, which decreases
noise generated within the device, and it will also reduce
device power consumption.
APPLICATIONS INFORMATION
Interfacing the ADS1601 to the TMS320 DSP family.
Since the ADS1601 communicates with the host via a
serial interface, the most suitable method to connect to any
of the TMS320 DSPs is via the Multi-channel Buffered
Serial Port (McBSP). A typical connection to the TMS320
DSP is shown in Figure 51. The McBSP provides a host
of functions including:
SYNC
FSX
Figure 51. ADS1601—TMS320 Interface
Connection
An Evaluation Module (EVM) is available from Texas
Instruments. The module consists of the ADS1601 and
supporting circuits, allowing users to quickly assess the
performance and characteristics of the ADS1601. The
EVM easily connects to various microcontrollers and DSP
systems. For more details, or to download a copy of the
ADS1601EVM User’s Guide, visit the Texas Instruments
web site at www.ti.com.
23
PACKAGE OPTION ADDENDUM
www.ti.com
30-Mar-2005
PACKAGING INFORMATION
Orderable Device Status
(1)
Package
Type
Package
Drawing
Pins Package
Qty
Eco Plan
ADS1601IPFBR ACTIVE TQFP PFB 48 1000 Green (RoHS &
no Sb/Br)
ADS1601IPFBT ACTIVE TQFP PFB 48 250 Green (RoHS &
no Sb/Br)
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS) or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
(2)
Lead/Ball Finish MSL Peak Temp
CU NIPDAU Level-2-260C-1 YEAR
CU NIPDAU Level-2-260C-1 YEAR
(3)
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is
provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the
accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take
reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on
incoming materials and chemicals. TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited
information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI
to Customer on an annual basis.
Addendum-Page 1
MECHANICAL DATA
MTQF019A – JANUARY 1995 – REVISED JANUARY 1998
PFB (S-PQFP-G48) PLASTIC QUAD FLATPACK
37
48
1,05
0,95
0,50
36
0,27
0,17
25
24
13
1
5,50 TYP
7,20
SQ
6,80
9,20
SQ
8,80
12
M
0,08
0,05 MIN
Seating Plane
0,13 NOM
Gage Plane
0,25
0°–7°
0,75
0,45
1,20 MAX
NOTES: A. All linear dimensions are in millimeters.
B. This drawing is subject to change without notice.
C. Falls within JEDEC MS-026
0,08
4073176/B 10/96
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