ST VIPer53EDIP - E, VIPer53ESP - E User Manual

!

VIPer53EDIP - E

VIPer53ESP - E

OFF-line Primary Switch

Features

■Switching frequency up to 300kHz

■Current mode control with adjustable limitation

■Soft start and shut-down control

■Automatic burst mode in standby condition (“Blue Angel“ compliant )

■Undervoltage lockout with Hysteresis

■Integrated start-up current source

■Over-temperature protection

■Overload and short-circuit control

■Overvoltage protection

■In compliance with the 2002/95/EC European Directive

Description

The VIPer53E combines an enhanced current mode PWM controller with a high voltage MDMesh Power MOSFET in the same package.

Block diagram

PowerSO-10

DIP-8

Typical applications cover offline power supplies with a secondary power capability ranging up to 30W in wide range input voltage, or 50W in single European voltage range and DIP-8 package and 40W in wide range input voltage, or 65W in single European voltage range and PowerSO-10 package, with the following benefits:

–Overload and short-circuit events controlled by feedback monitoring and delayed device reset;

–Efficient standby mode by enhanced pulse skipping.

–Integrated start-up current source is disabled during normal operation to reduce the input power.

		OSC					DRAIN
ON/OFF
	OSCILLATOR
	PWM
	LATCH
OVERTEMP.	R1	S		BLANKING TIME
DETECTOR				SELECTION
		FF	Q		1V
	R2
	R3 R4 R5
				PWM		HCOMP
UVLO				COMPARATOR	0.5V
COMPARATOR
VDD				150/400ns
				BLANKING		CURRENT
8.4/						AMPLIFIER
11.5V
8V				STANDBY		Vcc
				COMPARATOR	0.5V
125k						IC OMP
4V				OVERLOAD
				COMPARATOR	4.4V
OVERVOLTAGE
COMPARATOR
						4.5V
18V
TOVL						COMP	SOURCE
January 2006			DocRev1				1/31
							www.st.com

Contents	VIPer53EDIP - E / VIPer53ESP - E

Contents

1	Electrical data . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		. 3
	1.1	Maximum rating . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .	3
	1.2	Thermal data . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .	3
2	Electrical characteristics . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		4
3	Pin connections and function . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		7
4	Rectangular U-I Output characteristics . . . . . . . . . . . . . . . . . . . . . . . . . .		8
5	Secondary Feedback Configuration Example . . . . . . . . . . . . . . . . . . . .		9
6	Current Mode Topology . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		10
7	Standby Mode . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		11
8	High Voltage Start-up Current Source . . . . . . . . . . . . . . . . . . . . . . . . . .		13
9	Short-Circuit and Overload Protection . . . . . . . . . . . . . . . . . . . . . . . . .		15
10	Regulation Loop Stability . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		16
11	Special Recommendations . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		18
12	Software Implementation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		19
13	Operation pictures . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		20
14	Mechanical Data . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		26
15	Order codes . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		29
16	Revision history . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . .		30

2/31

DocRev1

VIPer53EDIP - E / VIPer53ESP - E	Electrical data

1 Electrical data

1.1Maximum rating

Stressing the device above the rating listed in the “Absolute Maximum Ratings” table may cause permanent damage to the device. These are stress ratings only and operation of the device at these or any other conditions above those indicated in the Operating sections of this specification is not implied. Exposure to Absolute Maximum Rating conditions for extended periods may affect device reliability. Refer also to the STMicroelectronics SURE Program and other relevant quality documents.

	Table 1.	Absolute maximum rating
	Symbol	Parameter	Value	Unit
	VDS	Continuous Drain Source Voltage (TJ= 25 ... 125°C) (1)	-0.3 ... 620	V
	ID	Continuous Drain Current	Internally limited	A
	VDD	Supply Voltage	0 ... 19	V
	VOSC	OSC Input Voltage Range	0 ... VDD	V
	ICOMP	COMP and TOVL Input Current Range (1)	-2 ... 2	mA
	ITOVL
		Electrostatic Discharge:
	VESD	Machine Model (R = 0Ω; C = 200pF)	200	V
		Charged Device Model	1.5	kV
	TJ	Junction Operating Temperature	Internally limited	°C
	TC	Case Operating Temperature	-40 to 150	°C
	TSTG	Storage Temperature	-55 to 150	°C

1.In order to improve the ruggedness of the device versus eventual drain overvoltages, a resistance of 1kΩ should be inserted in series with the TOVL pin.\

1.2Thermal data

Table 2.	Thermal data
Symbol	Parameter		PowerSO-10 (1)	DIP-8 (2)	Unit
RthJC	Thermal Resistance Junction-case	Max	2	20	°C/W
RthJA	Thermal Resistance Ambient-case	Max	60	80	°C/W

1.When mounted on a standard single-sided FR4 board with 50mm² of Cu (at least 35 mm thick) connected to the DRAIN pin.

2.When mounted on a standard single-sided FR4 board with 50mm² of Cu (at least 35 mm thick) connected to the device tab.

DocRev1

3/31

Electrical characteristics	VIPer53EDIP - E / VIPer53ESP - E

2 Electrical characteristics

TJ = 25°C, VDD = 13V, unless otherwise specified
Table 3.	Power section
Symbol	Parameter		Test conditions		Min.	Typ.	Max.	Unit
BVDSS	Drain-Source	ID = 1mA; VCOMP = 0V			620			V
	Voltage
IDSS	Off State Drain	VDS = 500V; VCOMP = 0V; Tj = 125°C					150	µA
	Current
	Static Drain-Source	ID = 1A; VCOMP = 4.5V; VTOVL = 0V
RDS(on)		TJ = 25°C				0.9	1	Ω
	On State Resistance
		TJ = 100°C					1.7	Ω
tfv	Fall Time	ID = 0.2A; VIN = 300V (1)				100		ns
trv	Rise Time	ID = 1A; VIN = 300V (1)				50		ns
Coss	Drain Capacitance	VDS = 25V				170		pF
CEon	Effective Output	200V < V	DSon	< 400V (2)		60		pF
	Capacitance

1.On clamped inductive load

2.This parameter can be used to compute the energy dissipated at turn on Eton according to the initial drain to source voltage VDSon and the following formula:

E		=	1	C		300	2	VDSon	1.5
	ton		--		Eon			----------------
			2					300

	Table 4.	Oscillator Section
	Symbol	Parameter	Test Conditions	Min.	Typ.	Max.	Unit
	FOSC1	Oscillator Frequency	RT = 8kΩ; CT = 2.2nF	95	100	105	kHz
		Initial Accuracy	Figure 15 on page 23
			RT = 8kΩ; CT = 2.2nF
	FOSC2	Oscillator Frequency	Figure 17 on page 24	93	100	107	kHz
		Total Variation	VDD = VDDon ... VDDovp;
			TJ = 0 ... 100°C
	VOSChi	Oscillator Peak			9		V
		Voltage
	VOSClo	Oscillator Valley			4		V
		Voltage

4/31

DocRev1

VIPer53EDIP - E / VIPer53ESP - E

Electrical characteristics

Table 5.

Supply Section

Symbol

Parameter

Test Conditions

Min.

Typ.

Max.

Unit

VDSstart

Drain Voltage Starting

VDD = 5V; IDD = 0mA

34

50

V

Threshold

IDDch1

Startup Charging Current

VDD = 0 ... 5V; VDS = 100V

-12

mA

Figure 9 on page 22

IDDch2

Startup Charging Current

VDD = 10V; VDS = 100VFigure 9.

-2

mA

IDDchoff

Startup Charging Current

VDD = 5V; VDS = 100VFigure 11.

0

mA

in Thermal Shutdown

TJ > TSD - THYST

I

Operating Supply Current

F

= 0kHz; V

COMP

= 0V

8

11

mA

DD0

Not Switching

sw

I

Operating Supply Current

F

=100kHz

9

mA

DD1

Switching

sw

VDDoff

VDD Undervoltage

Figure 9 on page 22

7.5

8.4

9.3

V

Shutdown Threshold

VDDon

VDD Startup Threshold

Figure 9.

10.2

11.5

12.8

V

VDDhyst

VDD Threshold

Figure 9.

2.6

3.1

V

Hysteresis

VDDovp

VDD Overvoltage

Figure 9.

17

18

19

V

Shutdown Threshold

Table 6.

Pwm Comparator Section

Symbol

Parameter

Test Conditions

Min.

Typ.

Max.

Unit

HCOMP

∆VCOMP / ∆IDPEAK

VCOMP = 1 ... 4 V Figure 14.

dID/dt = 0

1.7

2

2.3

V/A

VCOMPos

VCOMP Offset

dID/dt = 0 Figure 14.

0.5

V

Peak Drain Current

ICOMP = 0mA; VTOVL = 0V

IDlim

Figure 14.

Limitation

1.7

2

2.3

A

dID/dt = 0

IDmax

Drain Current

VCOMP = VCOMPovl; VTOVL = 0V

Capability

dID/dt = 0

1.6

1.9

2.3

A

td

Current Sense Delay

ID = 1A

250

ns

to Turn-Off

VCOMPbl

VCOMP Blanking Time

Figure 10 on page 22

1

V

Change Threshold

tb1

Blanking Time

VCOMP < VCOMPBLFigure 10.

300

400

500

ns

tb2

Blanking Time

VCOMP > VCOMPBLFigure 10.

100

150

200

ns

tONmin1

Minimum On Time

VCOMP < VCOMPBL

450

600

750

ns

DocRev1

5/31

Electrical characteristics

VIPer53EDIP - E / VIPer53ESP - E

Table 6.

Pwm Comparator Section

Symbol

Parameter

Test Conditions

Min.

Typ.

Max.

Unit

tONmin2

Minimum On Time

VCOMP > VCOMPBL

250

350

450

ns

VCOMPoff

VCOMP Shutdown

Figure 13 on page 23

0.5

V

Threshold

V

COMPhi

V

COMP

High Level

I

COMP

=0mA (1)

4.5

V

ICOMP

COMP Pull Up Current

VCOMP= 2.5V

0.6

mA

1.In order to ensure a correct stability of the internal current source, a 10nF capacitor (minimum value 8nF) should always be present on the COMP pin.

	Table 7.	Overload Protection Section
	Symbol	Parameter	Test Conditions	Min.	Typ.	Max.	Unit
	VCOMPovl	VCOMP Overload	ITOVL = 0mA Figure 7 on page 20		4.35		V
		Threshold	(1)
		VCOMPhi to VCOMPovl	VDD = VDDoff ... VDDreg;
	VDIFFovl		ITOVL= 0mA	50	150	250	mV
		Voltage Difference
			Figure 7. (1)
	VOVLth	VTOVL Overload	Figure 7.		4		V
		Threshold
	tOVL	Overload Delay	COVL = 100nF Figure 7.		8		ms
	1. VCOMPovl is always lower than VCOMPhi

Table 8.	Over temperature Protection Section
Symbol	Parameter	Test Conditions	Min.	Typ.	Max.	Unit
TSD	Thermal Shutdown	Figure 11 on page 22	140	160		°C
	Temperature
THYST	Thermal Shutdown	Figure 11 on page 22		40		°C
	Hysteresis

Table 9. Typical Output Power Capability

	Type	European	US / Wide range
		(195 - 265Vac)	(85 - 265Vac)
	VIPer53EDIP-E	50W	30W
	VIPer53ESP-E	65W	40W

6/31

DocRev1

VIPer53EDIP - E / VIPer53ESP - E	Pin connections and function

3 Pin connections and function

Figure 1. Pin connection (top view)
COMP 1	8	TOVL	DRAIN
			NC	1	10	SOURCE
OSC 2	7	VDD	NC	2	9	NC
			NC	3	8	NC
SOURCE 3	6	NC	VDD	4	7	OSC
			TOVL	5	6	COMP
SOURCE 4	5	DRAIN

DIP-8	PowerSO-10
Figure 2. Current and voltage conventions

	IDD		ID
	VDD		DRAIN
	IOSC
	OSC
	15V
VDD			VDS
	TOVL	COMP	SOURCE
	ITOVL
	VOSC
		ICOMP
	VTOVL
		VCOMP

Table 10.	Pin function
Pin Name		Pin Function
		Power supply of the control circuits. Also provides the charging current of the external
		capacitor during start-up.
VDD		The functions of this pin are managed by four threshold voltages:
		- VDDon: Voltage value at which the device starts switching (Typically 11.5 V).

-VDDoff: Voltage value at which the device stops switching (Typically 8.4 V).

-VDDovp: Triggering voltage of the overvoltage protection (Trimmed to 18 V).

SOURCE Power MOSFET source and circuit ground reference.

DRAIN

Power MOSFET drain. Also used by the internal high voltage current source during the start-up phase, to charge the external VDD capacitor.

Allows the setting of the dynamic characteristic of the converter through an external passive network. The useful voltage range extends from 0.5V to 4.5V. The Power

COMP MOSFET is always off below 0.5V, and the overload protection is triggered if the voltage exceeds 4.35V. This action is delayed by the timing capacitor connected to the TOVL pin.

TOVL

Allows the connection of an external capacitor for delaying the overload protection, which is triggered by a voltage on the COMP pin higher than 4.4V.

OSC	Allows the setting of the switching frequency through an external Rt-Ct network.

DocRev1

7/31

Rectangular U-I Output characteristics	VIPer53EDIP - E / VIPer53ESP - E

4 Rectangular U-I Output characteristics

Figure 3. Off Line Power Supply With Optocoupler Feedback

	F1
AC IN	C1				D1
			T1
	R1					C2		R2
							C3
								T2
							D2
									L1
								D4
					R4		D3	C8	C9	DC OUT
		R3		VDD		DRAIN
								C10
			OSC		CONTROL
									R8
	C4		COMP		TOVL	SOURCE
								U2
				R5	R9
			C12		1k
		C5
			10nF
				C7	C6				C11
									R7
								U3
									R6

8/31

DocRev1

VIPer53EDIP - E / VIPer53ESP - E	Secondary Feedback Configuration Example

5 Secondary Feedback Configuration Example

The secondary feedback is implemented through an optocoupler driven by a programmable zener diode (TL431 type) as shown in Figure 3 on page 8

The optocoupler is connected in parallel with the compensation network on the COMP pin which delivers a constant biasing current of 0.6mA to the optotransistor. This current does not depend on the compensation voltage, and so it does not depend on the output load either. Consequently, the gain of the optocoupler ensures a constant biasing of the TL431 device (U3), which is responsible for secondary regulation. If the optocoupler gain is sufficiently low, no additional components are required to a minimum current biasing of U3. Additionally, the low biasing current protects the optocoupler from premature failure.

The constant current biasing can be used to simplify the secondary circuit: instead of a TL431, a simple zener and resistance network in series with the optocoupler diode can insure a good secondary regulation. Current flowing in this branch remains constant just as it does by using a TL431, so typical load regulation of 1% can be achieved from zero to full output current with this simple configuration.

Since the dynamic characteristics of the converter are set on the secondary side through components associated to U3, the compensation network has only a role of gain stabilization for the optocoupler, and its value can be freely chosen. R5 can be set to a fixed value of 2.2kΩ, offering the possibility of using C7 as a soft start capacitor: When starting up the converter, the VIPer53E device delivers a constant current of 0.6mA on the COMP pin, creating a constant voltage of 1.3V in R5 and a rising slope across C7. This voltage shape, together with the operating range of 0.5V to 4.5V provides a soft startup of the converter. The rising speed of the output voltage can be set through the value of C7. The C4 and C6 values must be adjusted accordingly in order to ensure a correct startup.

DocRev1

9/31

Current Mode Topology	VIPer53EDIP - E / VIPer53ESP - E

6 Current Mode Topology

The VIPer53E implements the conventional current mode control method for regulating the output voltage. This kind of feedback includes two nested regulation loops:

The inner loop controls the peak primary current cycle by cycle. When the Power MOSFET output transistor is on, the inductor current (primary side of the transformer) is monitored

with a SenseFET technique and converted into a voltage. When VS reaches VCOMP, the power switch is turned off. This structure is completely integrated as shown on the Block

Diagram of Figure on page 1, with the current amplifier, the PWM comparator, the blanking time function and the PWM latch. The following formula gives the peak current in the Power MOSFET according to the compensation voltage:

IDpeak	VCOMP – VCOMPos
	= -------------------------------------------------
	HCOMP

The outer loop defines the level at which the inner loop regulates peak current in the power switch. For this purpose, VCOMP is driven by the feedback network (TL431 through an optocoupler in secondary feedback configuration, see Figure 3 on page 8) and is sets accordingly the peak drain current for each switching cycle.

As the inner loop regulates the peak primary current in the primary side of the transformer, all input voltage changes are compensated for before impacting the output voltage. This results in an improved line regulation, instantaneous correction to line changes, and better stability for the voltage regulation loop.

Current mode topology also provides a good converter start-up control. The compensation voltage can be controlled to increase slowly during the start-up phase, so the peak primary current will follow this soft voltage slope to provide a smooth output voltage rise, without any overshoot. The simpler voltage mode structure which only controls the duty cycle, leads generally to high current at start-up with the risk of transformer saturation.

An integrated blanking filter inhibits the PWM comparator output for a short time after the integrated Power MOSFET is switched on. This function prevents anomalous or premature termination of the switching pulse in the case of current spikes caused by primary side transformer capacitance or secondary side rectifier reverse recovery time when working in continuous mode.

10/31

DocRev1