– 30 kHz for VIPER06Xx
– 60 kHz for VIPER06Lx
– 115 kHz for VIPER06Hx
■ No need for an auxiliary winding in low-power
applications
■ Standby power < 30 mW at 265 V
Limiting current with adjustable set point
■
■ On-board soft-start
■ Safe auto-restart after a fault condition
■ Hysteretic thermal shutdown
AC
VIPER06
Fixed-frequency VIPer™ plus family
Datasheet — production data
Figure 1.Typical application
Applications
■ Replacement of capacitive power supplies
■ Home appliances
■ Power metering
■ LED drivers
Description
The VIPER06 is an offline converter with an 800 V
avalanche rugged power section, a PWM
controller, a user-defined overcurrent limit, openloop failure protection, hysteretic thermal
protection, soft startup and safe auto-restart after
any fault condition. The device is able to power
itself directly from the rectified mains, eliminating
the need for an auxiliary bias winding. Advanced
frequency jittering reduces EMI filter cost. Burst
mode operation and the device’s very low power
consumption both help to meet the standards set
by energy-saving regulations.
March 2012Doc ID 022794 Rev 11/28
This is information on a product in full production.
1. Typical continuous power in non-ventilated enclosed adapter measured at 50 ° C ambient.
2. Maximum practical continuous power in an open-frame design at 50 ° C ambient, with adequate heat
sinking.
4/28Doc ID 022794 Rev 1
(1)
AC
Open frame
(2)
Adapter
85-265 V
(1)
AC
Open frame
(2)
VIPER06Pin settings
DRAIN
DRAIN
AM11339v1
DRAIN
DRAIN
DRAIN
DRAIN
DRAIN
GND
VDD
FB
COMP
LIM
3 Pin settings
Figure 3.Connection diagram (top view)
Note:The copper area for heat dissipation has to be designed under the DRAIN pins.
Table 2.Pin description
Pin
NameFunction
DIP-7SSO10
11GND
22VDD
33LIM
44FB
55COMP
7, 86-10DRAIN
Connected to the source of the internal power MOSFET and controller
ground reference.
Supply voltage of the control section. This pin provides the charging
current of the external capacitor.
This pin allows setting the drain current limitation. The limit can be
reduced by connecting an external resistor between this pin and GND.
Pin left open if default drain current limitation is used.
Inverting input of the internal transconductance error amplifier.
Connecting the converter output to this pin through a single resistor
results in an output voltage equal to the error amplifier reference
voltage (see V
in Table 6). An external resistor divider is
FB_REF
required for higher output voltages.
Output of the internal transconductance error amplifier. The
compensation network has to be placed between this pin and GND to
achieve stability and good dynamic performance of the voltage control
loop. The pin is used also to directly control the PWM with an
optocoupler. The linear voltage range extends from V
V
COMPH
(Ta bl e 6 ).
COMPL
to
High-voltage drain pins. The built-in high-voltage switched startup bias
current is drawn from these pins too.
Pins connected to the metal frame to facilitate heat dissipation.
Doc ID 022794 Rev 15/28
Electrical dataVIPER06
4 Electrical data
4.1 Maximum ratings
Table 3.Absolute maximum ratings
Symbol
V
DRAIN
E
AV
I
AR
I
DRAIN
V
COMP
V
FB
V
LIM
V
DD
I
DD
P
TOT
T
J
T
STG
Pin
(DIP-7)
Parameter
Value
MinMax
7, 8Drain-to-source (ground) voltage 800V
7, 8Repetitive avalanche energy (limited by TJ = 150 °C)2mJ
7, 8Repetitive avalanche current (limited by TJ = 150 °C)1A
7, 8Pulse drain current (limited by TJ = 150 °C)2.5A
5Input pin voltage-0.33.5V
4Input pin voltage-0.34.8V
3Input pin voltage-0.32.4V
2Supply voltage-0.3
Self-
limited
2Input current 20mA
Power dissipation at TA < 40 °C (DIP-7)1W
Power dissipation at T
< 50 °C (SSO10)1W
A
Operating junction temperature range-40150°C
Storage temperature-55150°C
Unit
V
4.2 Thermal data
Table 4.Thermal data
SymbolParameter
R
R
R
1. When mounted on a standard single side FR4 board with 100 mm2 (0.155 sq in) of Cu (35 μm thick).
6/28Doc ID 022794 Rev 1
Thermal resistance junction pin
thJP
(dissipated power = 1 W)
Thermal resistance junction ambient
thJA
(dissipated power = 1 W)
Thermal resistance junction ambient
thJA
(dissipated power = 1 W)
(1)
Max value
SSO10
Max value
DIP-7
3540° C/W
100110° C/W
8090° C/W
Unit
VIPER06Electrical data
4.3 Electrical characteristics
(TJ = -25 to 125 °C, VDD = 14 V
Table 5.Power section
SymbolParameterTest conditionMin Typ Max Unit
V
BVDSS
I
OFF
R
DS(on)
C
OSS
Table 6.Supply section
SymbolParameterTest conditionMin Typ Max Unit
Vol tag e
Breakdown voltage
OFF state drain current
Drain-source on-state resistance
Effective (energy related) output capacitance V
(a)
unless otherwise specified).
I
= 1 mA,
DRAIN
V
= GND, TJ = 25 °C
COMP
V
V
I
I
= max rating,
DRAIN
= GND
COMP
= 0.2 A, TJ = 25 °C32Ω
DRAIN
= 0.2 A, TJ = 125 °C67Ω
DRAIN
= 0 to 640 V10pF
DRAIN
800V
60μA
V
_START
DRAIN
I
DDch1
I
DDch2
V
DD
V
DDclampVDD
V
DDon
V
DDCSon
V
DDoff
Current
I
DD0
I
DD1
I
DDoff
I
DDol
Drain-source startup voltage2545V
= 100 V to 640 V,
V
Startup charging current
Charging current during operation
DRAIN
= 4 V
V
DD
= 100 V to 640 V,
V
DRAIN
= 9 V falling edge
V
DD
-0.6-1.8mA
-7-14mA
Operating voltage range11.523.5V
clamp voltageIDD = 15 mA23.5V
VDD startup threshold121314V
VDD on internal high-voltage current
generator threshold
Figure 19. Flyback converter (isolated output without optocoupler)
Figure 20. Buck converter
14/28Doc ID 022794 Rev 1
VIPER06Power section
I
DD
V
DD
V
DRAIN
V
DDon
t
t
t
t
V
IN
V
DRAIN_START
t
t
Power-on
Power-off
Normal operat ion
regulation is lost here
VIN< V
DRAIN_START
HV startup is no more ac tivated
With internal self-supply
Without internal se lf-supply
V
DDCSon
V
DDoff
I
DDch1
I
DDch2
7 Power section
The power section is implemented with an N-channel power MOSFET with a breakdown
voltage of 800 V min. and a typical R
of 32 Ω. It includes a SenseFET structure to allow
DS(on)
virtually lossless current sensing and the thermal sensor.
The gate driver of the power MOSFET is designed to supply a controlled gate current during
both turn-ON and turn-OFF in order to minimize common-mode EMI. During UVLO
conditions, an internal pull-down circuit holds the gate low in order to ensure that the power
MOSFET cannot be turned ON accidentally.
8 High voltage current generator
The high-voltage current generator is supplied by the DRAIN pin. At the first startup of the
converter it is enabled when the voltage across the input bulk capacitor reaches the
V
DRAIN_START
voltage reaches the V
voltage current generator is turned OFF. The VIPER06 is powered by the energy stored in
the V
DD
In a steady-state condition, if the self-biasing function is used, the high-voltage current
generator is activated between V
I
, see Table 6 on page 7 to the VDD capacitor during the MOSFET off-time (see
DDch2
Figure 21).
threshold, sourcing a I
DDon
capacitor.
current (see Table 6 on page 7). As the VDD
DDch1
threshold, the power section starts switching and the high-
DDCSon
and V
(see Table 6 on page 7), delivering
DDon
The device can also be supplied through the auxiliary winding in which case the highvoltage current source is disabled during steady-state operation, provided that VDD is
above V
DDCSon
At converter power-down, the V
below the V
.
voltage drops and the converter activity stops as it falls
threshold (see Table 6 on page 7).
DDoff
DD
Figure 21. Power-on and power-off
Doc ID 022794 Rev 115/28
OscillatorVIPER06
9 Oscillator
The switching frequency is internally fixed at 30 kHz or 60 kHz or 115 kHz (respectively part
numbers VIPER06Xx, VIPER06Lx and VIPER06Hx).
The switching frequency is modulated by approximately ±3 kHz (30 kHz version) or ±4 kHz
(60 kHz version) or ±8 kHz (115 kHz version) at 230 Hz (typical) rate, so that the resulting
spread spectrum action distributes the energy of each harmonic of the switching frequency
over a number of sideband harmonics having the same energy on the whole, but smaller
amplitudes.
10 Soft startup
During the converter’s startup phase, the soft-start function progressively increases the
cycle-by-cycle drain current limit, up to the default value I
further limited and the output voltage is progressively increased, reducing the stress on the
secondary diode. The soft-start time is internally fixed to t
in Table 7 on page 8, and the function is activated for any attempt of converter startup and
after a fault event.
. In this way the drain current is
Dlim
, see typical value
SS
This function helps prevent saturation of the transformer during startup and short-circuit.
11 Adjustable current limit set point
The VIPER06 includes a current-mode PWM controller. The drain current is sensed cycleby-cycle through the integrated resistor R
inverting input of the PWM comparator, see Figure 2 on page 4. As soon as the sensed
voltage is equal to the voltage derived from the COMP pin, the power MOSFET is switched
OFF.
In parallel with the PWM operations, the comparator OCP, see Figure 2 on page 4, checks
the level of the drain current and switches OFF the power MOSFET in case the current is
higher than the threshold I
The level of the drain current limit I
, see Table 7 on page 8.
Dlim
can be reduced using a resistor R
Dlim
between the LIM and GND pins. Current is sunk from the LIM pin through the resistor R
and the setup of I
R
is shown inFigure 13 on page 11.
LIM
When the LIM pin is left open or if R
fixed to its default value, I
depends on the level of this current. The relation between I
Dlim
has a high value (i.e. > 80 kΩ), the current limit is
, as given in Table 7 on page 8.
Dlim
LIM
and the voltage is applied to the non-
SENSE
connected
LIM
Dlim
LIM
and
16/28Doc ID 022794 Rev 1
VIPER06FB pin and COMP pin
FB
COMP
Without Isolation:
switch open & E/A enabled
With Isolation:
switch closed & E/A disabled
No
Isolation
V
OUT
+
-
PWM stop
from R
SENSE
R
Isolation
R
L
nR
SW
V
REF
R
COMP
+
-
E/A
BUS
+
-
to PWM
V
COMPL
R
H
V
REF_FB
12 FB pin and COMP pin
The device can be used both in non-isolated and isolated topology. In non-isolated topology,
the feedback signal from the output voltage is applied directly to the FB pin as the inverting
input of the internal error amplifier having the reference voltage, V
page 8.
REF_FB,
see Ta b le 7 o n
The output of the error amplifier sources and sinks the current, I
, respectively to and
COMP
from the compensation network connected on the COMP pin. This signal is then compared
in the PWM comparator with the signal coming from the SenseFET in order to switch off the
power MOSFET on a cycle-by-cycle basis. See the Figure 2 on page 4 andtheFigure 22.
When the power supply output voltage is equal to the error amplifier reference voltage,
V
REF_FB
, a single resistor has to be connected from the output to the FB pin. For higher
output voltages the external resistor divider is needed. If the voltage on the FB pin is
accidentally left floating, an internal pull-up protects the controller.
The output of the error amplifier is externally accessible through the COMP pin and it’s used
for the loop compensation, usually an RC network.
As shown in Figure 22, in case of an isolated power supply, the internal error amplifier has to
be disabled (FB pin shorted to GND). In this case an internal resistor is connected between
an internal reference voltage and the COMP pin, see Figure 22. The current loop has to be
closed on the COMP pin through the opto-transistor in parallel with the compensation
network. The V
dynamic range is between V
COMP
COMPL
and V
COMPH
shown in Figure 23 on
page 18.
When the voltage V
drops below the voltage threshold V
COMP
, the converter enters
COMPL
burst mode, see Section 13 on page 18.
When the voltage V
rises above the V
COMP
COMPH
threshold, the peak drain current, as well
as the deliverable output power, will reach its limit.
Figure 22. Feedback circuit
Doc ID 022794 Rev 117/28
Burst modeVIPER06
AM01095v1
V
COMPH
V
COMPL
I
Dlim_bm
I
Dlim
I
DRAIN
V
COMP
time
time
time
V
COMP
V
COMPL+VCOMPL_HYS
V
COMPL
I
DD1
I
DD0
I
DD
I
DRAIN
I
Dlim_bm
Burst Mode
Figure 23. COMP pin voltage versus I
13 Burst mode
When the voltage V
the OFF state and the consumption is reduced to the I
page 7. In reaction to the loss of energy, the V
exceeds the threshold V
level of consumption equal to the I
“burst mode” and shown in Figure 24 on page 18, reduces the average frequency, which can
go down even to a few hundreds hertz, thus minimizing all frequency-related losses and
making it easier to comply with energy-saving regulations. During burst mode, the drain
current limit is reduced to the value I
audible noise issue.
DRAIN
drops below the threshold, V
COMP
+ V
COMPL
COMPL_HYS
current. This ON-OFF operation mode, referred to as
VIPER06Automatic auto-restart after overload or short-circuit
time
time
V
DD
V
DDon
V
DDCSon
I
DRAIN
I
Dlim_bm
t
1
*
* The time t1 can be lower or equal to the time t
OVL
t
RESTART
t
SS
t
OVL
t
RESTART
t
SS
t
OVL
t
RESTART
t
SS
SHORT CIRCUIT
OCCURS HERE
SHORT CIRCUIT
REMOVED HERE
time
time
V
DD
V
DDon
V
DDCSon
I
DRAIN
I
Dlim_bm
t
1
*
* The time t1can be lower t han or equal to the time t
OVL
t
RESTART
t
SS
t
OVL
t
RESTART
t
SS
t
OVL
t
RESTART
t
SS
SHORT CIRCUIT
OCCURS HERE
SHORT CIRCUIT
REMOVED HERE
14 Automatic auto-restart after overload or short-circuit
The overload protection is implemented automatically using the integrated up-down counter.
Every cycle, it is incremented or decremented depending upon the current logic detection of
the limit condition or not. The limit condition is the peak drain current, I
on page 8 or the one set by the user through the R
resistor, shown in Figure 13 on
LIM
page 11. After the reset of the counter, if the peak drain current is continuously equal to the
level I
, the counter will be incremented until the fixed time, t
Dlim
, at which point the power
OVL
MOSFET switch ON will be disabled. It will be activated again through the soft-start after the
t
RESTART
time (see Figure 25 and Figure 26 on page 19) and the time values mentioned in
Table 7 on page 8.
For overload or short-circuit events, the power MOSFET switching will be stopped after a
period of time dependent upon the counter with a maximum equal to t
sequence continues until the overload condition is removed, see Figure 25 and Figure 26.
This protection ensures a low repetition rate of restart attempts of the converter, so that it
works safely with extremely low power throughput and avoids overheating the IC in case of
repeated overload events. If the overload is removed before the protection tripping, the
counter will be decremented cycle-by-cycle down to zero and the IC will not be stopped.
If the power supply has been designed using flyback topology and the VIPER06 is supplied
by an auxiliary winding, as shown in Figure 27 and Figure 28 on page 21, the converter is
protected against feedback loop failure or accidental disconnections of the winding.
The following description is applicable for the schematics of Figure 27 and Figure 28 on
page 21, respectively the non-isolated flyback and the isolated flyback.
If R
is open or RL is shorted, the VIPER06 works at its drain current limitation. The output
H
voltage, V
output through the secondary-to-auxiliary turns ratio.
, will increase as does the auxiliary voltage, V
OUT
, which is coupled with the
AUX
As the auxiliary voltage increases up to the internal V
active clamp, V
DD
DDclamp
(the value is
given inTable 7 on page 8) and the clamp current injected on the VDD pin exceeds the latch
threshold, I
(the value is given in Table 7 on page 8), a fault signal is internally
DDol
generated.
In order to distinguish an actual malfunction from a bad auxiliary winding design, both the
above conditions (drain current equal to the drain current limitation and current higher than
I
through the VDD clamp) have to be verified to reveal the fault.
DDol
If R
is open or RH is shorted, the output voltage, V
L
voltage V
REF_FB
(for non-isolated flyback) or to the external TL voltage reference (for
, will be clamped to the reference
OUT
isolated flyback).
Figure 27. FB pin connection for non-isolated flyback
20/28Doc ID 022794 Rev 1
VIPER06Open-loop failure protection
V
REF_FB
R
H
C
COMP
+
-
PWM st op
R
3
R
TL
R
AUX
R
COMP
C
VDD
-
COMP
+
-
E/A
nR
R
L
V
REF
C
C
U5
Disabled
V
AUX
V
OUT
+
-
to PWM
SW
FB
R
OPTO
BUS
D
AUX
V
COMPL
from R
SENSE
R
C
Figure 28. FB pin connection for isolated flyback
Doc ID 022794 Rev 121/28
Package mechanical dataVIPER06
16 Package mechanical data
In order to meet environmental requirements, ST offers these devices in different grades of
®
ECOPACK
specifications, grade definitions and product status are available at: www.st.com.
ECOPACK
Table 8.DIP-7 mechanical data
packages, depending on their level of environmental compliance. ECOPACK®
®
is an ST trademark.
mm
Dim.
TypMinMax
A 5.33
A1 0.38
A2 3.30 2.92 4.95
b 0.46 0.36 0.56
b2 1.52 1.14 1.78
c 0.25 0.20 0.36
D 9.27 9.02 10.16
E 7.87 7.62 8.26
E1 6.35 6.10 7.11
e 2.54
eA 7.62
eB 10.92
L 3.30 2.92 3.81
(1)(2)
M
N 0.50 0.40 0.60
N1 0.60
(2)(3)
O
1. Creepage distance > 800 V.
2. Creepage distance as given in the 664-1 CEI / IEC standard.
3. Creepage distance 250 V.
2.508
0.548
Note:1The lead size includes the thickness of the lead finishing material.
2Dimensions do not include mold protrusion, not to exceed 0.25 mm in total (both sides).
3Package outline exclusive of metal burr dimensions.
4Datum plane “H” coincident with the bottom of lead, where lead exits body (refer to
Figure 29 on page 23).
22/28Doc ID 022794 Rev 1
VIPER06Package mechanical data
Figure 29. DIP-7 package dimensions
Doc ID 022794 Rev 123/28
Package mechanical dataVIPER06
Table 9.SSO10 mechanical data
Databook (mm.)
Dim.
TypMin.Max
A 1.75
A1 0.10 0.25
A2 1.25
b 0.31 0.51
c 0.17 0.25
D 4.90 4.80 5
E 6 5.80 6.20
E1 3.90 3.80 4
e 1
h 0.25 0.50
L 0.40 0.90
K 0° 8°
24/28Doc ID 022794 Rev 1
VIPER06Package mechanical data
8140761 rev. A
Figure 30. SSO10 package dimensions
Doc ID 022794 Rev 125/28
Order codesVIPER06
17 Order codes
Table 10.Ordering information
Order codePackagePackaging
VIPER06XN
DIP-7TubeVIPER06LN
VIPER06HN
VIPER06XS
VIPER06XSTRTape and reel
VIPER06LSTube
SSO10
VIPER06LSTRTape and reel
VIPER06HSTube
VIPER06HSTRTape and reel
Tube
26/28Doc ID 022794 Rev 1
VIPER06Revision history
18 Revision history
s
Table 11.Document revision history
DateRevisionChanges
08-Mar-20121Initial release.
Doc ID 022794 Rev 127/28
VIPER06
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