ST TS613 User Manual

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DUAL WIDE BAND OPERATIONAL AMPLIFIER

■ LOW NOISE : 3nV/√Hz, 1.2pA/√Hz

■ HIGH OUTPUT CURRENT : 200mA

■ VERY LOW HARMONIC AND INTERMODU-

LATION DISTORTION

■ HIGH SLEW RATE : 40V/µs

TS613

WITH HIGH OUTPUT CURRENT

■ SPECIFIED FOR 25Ω LOAD

DESCRIPTION

The TS613 is a dual operational amplifier featur­ing a high output current (200mA min.), large
gain-bandwidth product (130MHz) and capable of
driving a 25Ω load with a 160mA output current at
±6V power supply.

This device is particularly intended for applications
where multiple carriers must be amplified simulta­neously with very low intermodulation products.

The TS613 is housed in a SO8 package.

APPLICATION

■ UPSTREAM line driver for Assymetric Digital

Subscriber Line (ADSL) (NT).

ORDER CODE

Package

Part Number Temperature Range

D

TS613ID -40, +85°C •

D

SO-8

(Plastic Micropackage)

PIN CONNECTIONS (top view)

D=Small Outline Package (SO) - also available in Tape & Reel (DT)

May 2000

1/9

TS613

ABSOLUTE MAXIMUM RATINGS

Symbol Parameter Value Unit

V

T

T

R
R

P

Supply voltage

CC

V

Differential Input Voltage

id

V

in Input Voltage Range

Operating Free Air Temperature Range TS612ID -40 to + 85 °C

oper

Storage Temperature -65 to +150 °C

std

T

Maximum Junction Temperature 150 °C

j

Thermal Resistance Junction to Case 28 °C/W

thjc

Thermal Resistance Junction to Ambient Area 175 °C/W

tha

Maximum Power Dissipation (@25°C) 715 mW

max.

Output Short Circuit Duration

1. All voltages values, except differential voltage are with respect to network terminal.

2. Differential voltages are non-inverting input terminal with respect to the inverting input terminal.

3. The magnitude of input and output voltages must never exceed V

4. An output current limitation protects the circuit from transient currents. Short-circuits can cause excessive heating.
Destructive dissipation can result from short circuit on amplifiers.

OPERATING CONDITIONS

Symbol Parameter Value Unit

V

V

Supply Voltage ±2.5 to ±6V

CC

Common Mode Input Voltage

icm

1)

2)

3)

+0.3V.

CC

(V

±7V
±2V
±6V

4)

)+2to(V

CC

CC

+

)-1

V

2/9

TS613

ELECTRICAL CHARACTERISTICS. VCC= ±6V, T

=25°C (unless otherwise specified).

amb

Symbol Parameter Test Condition Min. Typ. Max Unit

DC PERFORMANCE

V

Input Offset Voltage

io

∆V

Differential Input Offset Voltage

io

I

Input Offset Current

io

I

Input Bias Current

ib

CMR Common Mode Rejection Ratio

SVR Supply Voltage Rejection Ratio

I

TotalSupply Current per Operator

CC

T

amb

T

min.<Tamb<Tmax.

T

=25°C

amb

T

amb

T

min.<Tamb<Tmax.

T

amb

T

min.<Tamb<Tmax.

V

=2Vto2V,T

ic

T

min.<Tamb<Tmax.

V

= ±6V to ±4V, T

ic

T

min.<Tamb<Tmax.

No load, V

out

=0

amb

amb

-6 -1 6
10

6mV

0.2 3
5

515

30
90 108
70
70 88
50

11 15 mA

DYNAMIC PERFORMANCE

V

High Level Output Voltage

OH

V

Low Level Output Voltage

OL

A

Large Signal Voltage Gain

VD

GBP Gain Bandwidth Product

SR Slew Rate

I

Output Short Circuit Current ±320 mA

out

I

Output Sink Current

sink

I

source

ΦM14

ΦM6

Output Source Current
Phase Margin at A

Phase Margin at A

VCL
VCL

= 14dB RL=25Ω//15pF
= 6dB RL=25Ω//15pF

I

= 160mA, RLto GND

out

I

= 160mA, RLto GND

out

= 7V peak

V

out

=25Ω,T

R

L

T

min.<Tamb<Tmax.

A

VCL

= 100Ω

R

L

A

VCL

= ±6V, T

V

ic

T

min.<Tamb<Tmax.

= ±6V, T

V

ic

T

min.<Tamb<Tmax.

amb

= +11, f = 20MHz

= +7, RL=50Ω

amb

amb

4 4.5 V

-4.5 -4 V

6500 11000
5000

80 130 MHz
23 40 V/µs

+200
+180

-200

-180
60 °
40 °

NOISE AND DISTORTION

en Equivalent Input Noise Voltage f = 100kHz 3 nV/√Hz

in Equivalent Input Noise Current f = 100kHz 1.2 pA/√Hz

V

= 4Vpp, f = 100kHz

out

= -10

THD TotalHarmonic Distorsion

HD2

HD2

HD3

IM2

IM3

2nd Harmonic Distorsion

-10

2nd Harmonic Distorsion

+2

3rd Harmonic Distorsion

+2

2nd Order Intermodulation Product

-10

3rd Order Intermodulation Product

-10

A

VCL

=25Ω//15pF

R

L

V

= 4Vpp, f = 100kHz

out

= -10

A

VCL

Load =25Ω//15pF
V

= 4Vpp, f = 100kHz

out

=+2

A

VCL

Load =25Ω//15pF
V

= 4Vpp, f = 100kHz

out

=+2

A

VCL

Load =25Ω//15pF
F1 = 80kHz, F2 = 70kHz

V

= 8Vpp, A

out

VCL

= -10
Load = 25Ω//15pF
F1 = 80kHz, F2 = 70kHz

V

= 8Vpp, A

out

VCL

= -10
Load = 25Ω//15pF

-69 dB

-70 dBc

-74 dBc

-79 dBc

-77 dBc

-77 dBc

mV

µA

µA

dB

dB

V/V

mA

mA

3/9

TS613

INTERMODULATION DISTORTION

The curves shown below are the measurementsresults of a single operatorwired as an adder with a gain
of 15dB.
The operational amplifier is supplied by a symmetric ±6V and is loaded with 25Ω.
Two synthesizers (Rhode & Schwartz SME) generate two frequencies (tones) (70 & 80kHz ; 180 &
280kHz).
An HP3585 spectrum analyzer measures the spurious level at different frequencies.
The curves are traced for different output levels (the value in the Xax is the value of each tone).
The output levels of the two tones are the same.
The generators and spectrum analyzer are phase locked to enhance measurement precision.

3rd ORDER INTERMODULATION

Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 70kHz/
80kHz

0

-10

-20

-30

-40

-50

-60

IM3 (dBc)

-70

-80

-90

-100

90kHz

230kHz

60kHz

220kHz

1 1,5 2 2,5 3 3,5 4 4,5

Vout peak (V)

2nd ORDER INTERMODULATION

Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 180kHz/
280kHz, Spurious measurement @100kHz

3rd ORDER INTERMODULATION

Gain=15dB, Vcc=±6V, RL=25Ω, 2 tones 180kHz/
280kHz

0

-10

-20

-30

-40

-50

-60

IM3 (dBc)

-70

-80

-90

-100

80kHz

380kHz

640kHz

740kHz

1 1,5 2 2,5 3 3,5 4 4,5

Voutpeak (V)

-55

-60

IM2 (dBc)

-65

-70
1,5 2 2,5 3 3,5 4 4,5

Voutpeak (V)

4/9

TS613

Closed Loop Gain and Phase vs. Frequency

Gain=+2, Vcc=±6V, RL=25Ω

10

Gain

0

Phase

-10

Gain (dB)

-20

-30

10kHz 100kHz 1MHz 10MHz 100MHz

Frequency

Closed Loop Gain and Phase vs. Frequency

Gain=+11, Vcc=±6V, RL=25Ω

30

Gain

20

10

Phase

0

Gain (dB)

-10

-20

200

100

0

-100

-200

200

100

0

Phase (degrees)

-100

Closed Loop Gain and Phase vs. Frequency

Gain=+6, Vcc=±6V, RL=25Ω

20

Gain

15

10

5

Phase

0

Gain (dB)

Phase (degrees)

-5

-10

-15

-20

10kHz 100kHz 1MHz 10MHz 100MHz

Frequency

Equivalent Input Voltage Noise

Gain=+100, Vcc=±6V, no load

20

15

10

en (nV/VHz)

5

100

200

100

0

Phase (degrees)

-100

-200

+

_

10k

-30

10kHz 100kHz 1MHz 10MHz 100MHz

Frequency

Maximum Output Swing

Vcc=±6V, RL=25Ω

5
4
3
2

1

0

-1

swing (V)

-2

-3

-4

-5
0246810

input

Time (µs)

5/9

output

-200

0

100Hz 1kHz 10kHz 100kHz 1MHz

Frequency

Channel Separation (Xtalk) vs. Frequency

XTalk=20Log(V2/V1), Vcc=±6V, RL=25Ω

-20

VIN

+

49.9Ω

_

-30

-40

-50

Xtalk (dB)

-60

-70

-80

100Ω

49.9Ω

100Ω

10kHz

V1

1kΩ

25Ω

+
_

V2

1kΩ

25Ω

100kHz 1MHz 10MHz

Frequency

TYPICAL APPLICATION : TS613 AS DRIVER

FOR ADSL LINE INTERFACES

A SINGLE SUPPLY IMPLEMENTATION WITH PASSIVE

OR ACTIVE IMPEDANCE MATCHING

by C. PRUGNE

ADSL CONCEPT

Asymmetric Digital Subscriber Line (ADSL), is a
new modem technology, which converts the exist­ing twisted-pair telephone lines into access paths
for multimedia and high speed data communica­tions.

ADSL transmits more than 8 Mbps to asubscriber,
and can reach 1Mbps from the subscriber to the
central office. ADSL can literally transform the ac­tual public information network by bringing mov­ies, television, video catalogs, remote CD-ROMs,
LANs, and the Internet into homes.

An ADSL modem is connected to a twisted-pair
telephone line, creating three information chan­nels: a high speed downstream channel (up to

1.1MHz) depending on the implementation of the
ADSL architecture, a medium speed upstream
channel (up to 130kHz) and a POTS (Plain Old
Telephone Service), split off from the modem by
filters.

THE LINE INTERFACE - ADSL Remote
Terminal (RT):

The TS613 is used as a dual line driver for the up­stream signal.
For the remote terminal it is required to create an
ADSL modemeasy toplug in a PC. In such an ap­plication, the driver should be implemented with a
+12 voltssingle power supply. This +12Vsupply is
available on PCI connector of purchase.
The figure 2 shows a single +12V supply circuit
that uses the TS613 as a remote terminal trans­mitter in differential mode.

Figure 2 : TS613 as a differential line driver with

a +12V singlesupply

100n

+12V

1k

Vi

Vi Vo

100n

10µ 100n

1k

GND

47k

47k

8

3

+12V

+

_

1

2

R2

R1

R3

_

6

7

5

+

GND

4

12.5

12.5

1µ

10n

Vo

1:2

Hybrid
&

25Ω100Ω

Transformer

The Figure1 shows a typical analog line interface
used for ADSL. The upstream and downstream
signals are separated from the telephone line by
using an hybrid circuit and a line transformer. On
this note, the accent will bemade on the emission
path.

Figure 1 : Typical ADSL Line Interface

highoutput
current

upstream

impedance
matching

downstream

HYBRID

CIRCUIT

twisted-pair
telephone
line

6/9

digital to
analog

digital
treatment

analogto
digital

emission
(analog)

reception
(analog)

LPfilter

TS613
LineDriver

reception
circuits

The driver is biased with a mid supply (nominaly
+6V), in order to maintain the DC component of
the signal at +6V. This allows the maximum dy­namic range between 0 and +12 V. Several op­tions are possibleto provide this bias supply (such
as a virtual ground using anoperational amplifier),
such as a two-resistance divider which is the
cheapest solution. A high resistance value is re­quired to limit the current consumption. On the
other hand, the current must be high enough to
bias theinverting input of the TS613. If weconsid­er this bias current (5µA) as the 1% of the current
through the resistance divider (500µA) to keep a
stable mid supply, two 47kΩ resistances can be
used.

The input provides two high pass filters with a
break frequency of about 1.6kHz which is neces­sary toremove the DC componentof the input sig­nal. To avoid DC current flowing in the primary of
the transformer, an output capacitor is used. The

TS613

1µF capacitance provides a path for low frequen­cies, the 10nF capacitance provides a path for
high end of the spectrum.

In differential mode the TS613 is able to deliver a
typical amplitude signal of 18V peak to peak.

The dynamic line impedance is 100Ω. The typical
value of the amplitude signal required on the line
is up to 12.4V peak to peak. By using a 1:2 trans­former ratio the reflected impedance back to the
primary will be a quarter (25Ω) and therefore the
amplitude of the signal required with this imped­ance will be the half (6.2 V peak to peak). Assum­ing the 25Ω series resistance (12.5Ω for both out­puts) necessary for impedance matching, the out­put signal amplitude required is 12.4 V peak to
peak. This value is acceptable for the TS613. In
this case theload impedance is 25Ω for each driv­er.

For the ADSL upstream path, a lowpass filter is
absolutely necessary to cutoff the higher frequen­cies from the DAC analog output. In this simple
non-inverting amplification configuration, it will be
easy to implement a Sallen-Key lowpass filter by
using the TS613. For ADSL over POTS, a maxi­mum frequency of 135kHz is reached. For ADSL
over ISDN, the maximum frequency will be
276kHz.

INCREASING THE LINE LEVEL BY USING AN
ACTIVE IMPEDANCE MATCHING

With passive matching, the output signal ampli­tude of the driver must be twice the amplitude on
the load. To go beyond this limitation an active
maching impedance can be used. With this tech­nique it is possible to keep good impedance
matching with an amplitude on the load higher
than the half of the ouput driver amplitude. This
concept is shown infigure3 for a differential line.

Figure 3 : TS613 as a differential line driver with

an active impedance matching

100n

+12V

1k

Vi

Vi Vo

100n

10µ 100n

1k

GND

47k

47k

8

3

+12V

+

_

2

R2

R3

R1

R5

R4

_

6

5

+

4

GND

12.5

1

Vo°

Vo°

12.5

7

1µ

10n

Vo

Hybrid
&

25Ω 100Ω

Transformer

1:2

Component calculation:

Let us consider the equivalent circuit for a single
ended configuration, figure4.

Figure 4 : Single ended equivalent circuit

+

Rs1

Vi

1/2

Let us consider the unloaded system. Assuming
the currents through R1, R2 and R3
as respectively:

As Vo° equals Vo without load, the gain in this
case becomes :

The gain, for the loaded system will be (1):

GL

As shown in figure5, this system is an ideal gener­ator with a synthesized impedance as the internal
impedance of the system. From this, the output
voltage becomes:

with Ro the synthesized impedance and Iout the
output current. On the other hand Vo can be ex­pressed as:

Vo

_

R2

R1

G

R3

2Vi

Vi Vo°–()

---------

--------------------------

,

R1

Vo nol oad()

------------------------------ -

Vo withload()

------------------------------------

R2

Vi

Vi

Vo ViG()RoIout()–= 2(),

2R2



Vi 1

---------- -



---------------------------------------------- -

R1

R2

1

--- ----–

R3

Vo°

-1

Vi Vo+()

----------------------- -

and

2 R 2

1

---------- -

R 1

---------------------------------- -==

1

2R 2

1

---------- -

1

R 1

---

---------------------------------- -

2

1

R 2

-------++

R 3

Rs1Iout

---------------------

1

Vo

R3

R 2

-------++

R 3

R2

-------–

R3

R 2

-------++

R 3

R2

-------–

R3

3(),–=

R2

-------–

R3

1/2

RL

1(),==

7/9

By identification of both equations (2) and (3), the
synthesized impedance is, with Rs1=Rs2=Rs:

Ro

1

R2

-------–

R3

4(),=

Rs

---------------- -

Figure 5 : Equivalent schematic. Ro is the syn-

thesized impedance

Ro

Vi.Gi

Iout

1/2

RL

Unlike the level Vo° required for a passive imped­ance, Vo°will be smaller than 2Vo in our case. Let
us write Vo°=kVo with k the matching factor vary­ing between 1 and 2. Assuming that the current
through R3 is negligeable, it comes the following
resistance divider:

Ro

kVoRL

---------------------------=

RL 2Rs1+

After choosing thek factor, Rs will equal to
1/2RL(k-1).
A good impedance matching assumes:

1

---

Ro

RL 5(),=

2

From (4) and (5) it becomes:

R2

------- 1
R3

2 Rs

--------- -

RL

6(),–=

By fixing an arbitrary value for R2, (6) gives:

-------------------=

1

R2

2Rs

--------- -–

RL

R3

Finally, the values of R2 andR3 allow usto extract
R1 from (1), and it comes:

---------------------------------------------------------

R 1

21

2 R 2

R2



-------–

R3

GL 1–



R2

------ -–

R3

7(),=

TS613

GL (gain for the
loaded system)

R1 2R2/[2(1-R2/R3)GL-1-R2/R3]
R2 (=R4) Abritrary fixed
R3 (=R5) R2/(1-Rs/0.5RL)

Rs 0.5RL(k-1)

CAPABILITIES

The table below shows the calculated compo­nents for different values of k. In this case
R2=1000Ω and the gain=16dB. The last column
displays the maximum amplitude level on the line
regarding the TS613 maximum output capabilities
(18Vpp diff.) and a 1:2 line transformer ratio.

Active matching

R1

k

(Ω)R3(Ω)Rs(Ω)

1.3 820 1500 3.9 8 27.5

1.4 490 1600 5.1 8.7 25.7

1.5 360 2200 6.2 9.3 25.3

1.6 270 2400 7.5 9.9 23.7

1.7 240 3300 9.1 10.5 22.3
Passive matching 12.4 18

MEASUREMENT OF THE POWER
CONSUMPTION IN THE ADSL APPLICATION

Conditions:

Passive impedance matching
Transformer turns ratio: 2
Maximun level required on the line: 12.4Vpp
Maximum output level of the driver: 12.4Vpp
Crest factor: 5.3 (Vp/Vrms)
The TS613 power consumption during emission
on 900 and 4550 meter twisted pair telephone
lines: 360mW

GL is fixed for the application requirements
GL=Vo/Vi=0.5(1+2R2/R1+R2/R3)/(1-R2/R3)

TS613 Output

Level to get

12.4Vpp on
the line

(Vpp diff)

Maximum
Line level

(Vpp diff)

with GL the required gain.

8/9

TS613

PACKAGE MECHANICAL DATA

8 PINS - PLASTIC MICROPACKAGE (SO)

Dim.

Millimeters Inches

Min. Typ. Max. Min. Typ. Max.

A 1.75 0.069
a1 0.1 0.25 0.004 0.010
a2 1.65 0.065
a3 0.65 0.85 0.026 0.033

b 0.35 0.48 0.014 0.019

b1 0.19 0.25 0.007 0.010

C 0.25 0.5 0.010 0.020
c1 45° (typ.)

D 4.8 5.0 0.189 0.197

E 5.8 6.2 0.228 0.244

e 1.27 0.050

e3 3.81 0.150

F 3.8 4.0 0.150 0.157

L 0.4 1.27 0.016 0.050
M 0.6 0.024
S8°(max.)

Information furnished is believed to be accurate and reliable. However, STMicroelectronics assumes no responsibility for the
consequences of use of such information nor for any infringement of patents or other rights of third parties which may result from
its use. No license is granted by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications
mentioned in this publication are subject to change without notice. This publication supersedes and replaces all information
previously supplied. STMicroelectronics products are not authorized for use as critical components in life suppo rt devices or
systems withou texpress written approval of STMicroelectronics.

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