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AN1948 |
® |
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- APPLICATION NOTE |
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DVD Combo Power Supply with VIPer53 |
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A. Bailly - S. Luciano |
Despite the strong growth of the DVD readers, the VCR ones are still present on the market. A lot of equipment now includes both types of media in the same case. This paper proposes a typical solution to efficiently supply such applications and other equipment where logic, DC motor drive and LCD display are to be implemented together in the 35W power range and suite any input voltage standard (85Vac to 265Vac).
Key features for this application are high efficiency, low standby consumption and cost effective solutions to fit the high volume consumer market needs.
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The specification can be summarized as shown in the following table: |
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Voltage |
Maximum Current |
Output Power |
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Product(s) |
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MaximumPower |
Board Size |
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+/-5% |
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L x W x H |
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Output 1 |
3.3V |
1.5A |
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4.95W |
Normal Operation: |
170x 70 x 40 |
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Output 2 |
5V Stand-by |
100mA |
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500mW |
35W max utput |
(mm) |
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Output 3 |
5V Power |
1.5A |
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7.5W |
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power |
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Output 4 |
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Obsolete |
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12V Power |
1.5A |
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18W |
S and-by Operation: |
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Output 5 |
12V Audio |
200mA |
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2.4W |
750mW max input |
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Output 6 |
-12V Power |
15mA |
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180mW |
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power |
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Output 7 |
-25V |
25mA |
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625mW |
With 40mA on the |
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Output 8 |
4.2V Display |
50mA |
- |
210mW |
5VStandby output |
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Obsolete |
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April 2004 |
1/17 |
AN1948 - APPLICATION NOTE
1. VIPer53 DESCRIPTION
VIPer53, the first multichip device of the VIPer family has been chosen to fulfill the requirements. It features very low Rdson of 1Ω allowing to deliver up to 35W in wide range in a standard DIP-8 package without a heatsink, answering the need for higher efficiency and reduced space thanks to a lower power dissipation.
1.1 General features
The block diagram is given in figure 1. An adjustable oscillator drives a current controlled PWM at a fixed switching frequency. The peak drain current is set for each cycle by the voltage present on the COMP pin. The useful range of the COMP pin extends from 0.5V to 4.5V, with a corresponding drain current range from 0A to 2A.
This COMP pin can be either used as an input when working in secondary feedback configuration, or as an output when the internal error amplifier connected on the VDD pin operates in primary feedback to regulate the VDD voltage to 15V.
The VDD undervoltage comparator drives a high voltage startup current source, which is switched off during the normal operation of the device. This feature together with the burst mode capability allows to
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reach very low level of input power in standby mode, when the converter is lightly loaded. |
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Figure 1: VIPer53 block diagram |
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Obsolete |
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DRAIN |
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OSC |
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ON/OFF |
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OSCILLATOR |
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- |
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PWM |
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OVERTEMP. |
LATCH |
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DETECTOR |
R1 |
FF |
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SELECTION |
1V |
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R2 |
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R3 |
R4 |
R5 |
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UVLO |
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0.5V |
HCOMP |
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COMPARATOR |
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VDD |
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150/400ns |
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BLANKING |
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CURRENT |
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8.4/ |
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PWM |
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AMPLIFIER |
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11.5V |
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STANDBY |
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COMPARATOR |
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COMPARATOR |
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0.5V |
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4V |
8V |
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Obsolete |
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125k |
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15V |
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ERROR |
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AMPLIFIER |
4.35V |
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OVERLOAD |
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COMPARATOR |
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OVERVOLTAGE |
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COMPARATOR |
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18V |
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4.5V |
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TOVL |
COMP |
SOURCE |
2/17
AN1948 - APPLICATION NOTE
1.2 Overload protection
A threshold of 4.35V typical has been implemented on the COMP pin. This overload threshold is 150mV below the clamping voltage of 4.5V which corresponds to the current limitation of the device. In case of a COMP voltage exceeding the overload threshold, the pull up resistor on the TOVL pin is released and the external capacitor connected on this pin begins to charge. When a value of 4V typical is reached, the device stops switching and remains in this state until the VDD voltage reaches VDDoff, or resumes normal operation if the COMP voltage returns to a value below the overload threshold. The drain current that the device is able to deliver without triggering the overload threshold is called "current capability", specified as IDmax in the datasheet. This value must be used to correctly size the converter versus its maximum output power.
When an overload occurs on secondary side of the converter, the output power is first limited by the current limitation of the device. If this overload lasts for more than a time constant defined by a capacitor connected on the TOVL pin, the device is reset, and a new restarting sequence is initiated by turning on the startup current source. The capacitors on the VDD pin and on the TOVL pin will be defined together in order to insure a correct startup and a low restart duty cycle in overload or short circuit operation. Here are the typical corresponding formulas:
COVL > 12.5 × 10– 6 × tss |
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COVL × IDDch2 |
Product(s) |
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C |
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– 4 |
× |
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1 |
ö |
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> 8 × 10 |
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---------------- |
– 1 |
× ------------------------------------------- |
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VDD |
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èDRST |
ø |
VDDhyst |
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CVDD |
IDD1 × tss |
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> --------------------------- |
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VDDhyst |
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Where tss and DRST are respectively the time needed for the output voltages to pass from 0V to their |
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value. |
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Obsolete |
nominal values at startup, and the restart duty cycle in overload or short circuit condition. A typical value of 10% is generally set for this last parameter, as it insures that the output diodes and the transformer don’t overheat. The other parameters can be found in the datasheet of the device.
As the VDD capacitor has to respect two conditions, the maximum value will be retained to define its
- 1.3 Stand-by operationProduct(s)
On the opposite load configuration, the converter is lightly loaded and the COMP voltage decreases until it reaches the shutdown threshold typically at 0.5V. At this point, the switching is disabled and no more energy is passed on secondary side. So, the output voltage decreases and the regulation loop rises again above the shutdown threshold, thus resuming the normal switching operation. A burst mode with pulse skipping takes place, as long as the output power is below the one corresponding to the minimum
turn on of the device. As the COMP voltage works around 0.5V, the peak drain current is very low (it is Obsoleteactually defined by the minimum turn on time of the device, and by the primary inductance of the
transformer) and no audible noise is generated.
In addition, the minimum turn on time depends on the COMP voltage. Below 1V (VCOMPbl), the blanking time increases to 400ns, whereas it is 150ns for higher voltages. The minimum turn on times resulting from these values are respectively 600ns and 350ns, when taking into account the internal propagation time. This feature brings the following benefits:
-this brutal change induces an hysteresis between normal operation and burst mode which is reached sooner when the output power is decreased.
-a short value in normal operation insures a good drain current control in case of short circuit on secondary side.
-long value in standby operation reinforces the burst mode by skipping more switching cycles, thus decreasing switching losses.
More details regarding the standby operation can be found in the datasheet.
3/17
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Obsolete |
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J2-1 |
schematicsFigure2: |
.2 figure in presented is schematics overall The .modeconsumptionstandby in |
power low a providing voltages, output the of most dropout to allows whichtransformerdesign |
specific a on based feature, management standby smart a by achieved is This .outputprovides5Va |
only one standby the and voltages output different 8 delivers one normal The .modesoperatingofferstwo |
board The .70kHz of frequency switching fixed a at working flyback line off an is topologypowerThe |
Schematics21. |
SUPPLY POWERCOMBODVD02. |
NOTE APPLICATIONAN1948- |
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D4 |
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R7 |
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C13 |
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-4.2V / 50mA |
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BAT43 |
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C9 |
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DZ2 |
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150 |
100nF |
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BZX79C5.1 |
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J1-1 |
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2.2nF |
T1 |
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C11 |
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1kV |
25707870P1 |
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C12 |
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180µF |
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R8 |
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OREGA |
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100nF |
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10V |
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R9 |
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33k |
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DB1 |
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C14 |
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C1 |
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100nF |
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100nF |
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L1 |
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400V |
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J2-2 |
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18mH |
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D5 |
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+4.2V / 50mA |
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0.5A |
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BAV21 |
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L2 |
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J2-3 |
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C2 |
C8 |
R2 |
DZ3 |
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-25V / 25mA |
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68µF |
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BZT03C |
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100µH |
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IN |
<0 T |
VR1 |
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R10 |
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R11 |
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450V |
fitted |
fitted |
200 |
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910 |
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910 |
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C15 |
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39µF |
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-12V / 15mA |
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35V |
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35V |
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F1 |
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D1 |
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R12 |
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1A |
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1k |
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1N4947GP |
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250V |
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35V |
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D6 |
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J1-2 |
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STPS8H100D |
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L3 |
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+12V audio / 0.2A |
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47µH |
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L4 |
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D8 |
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+12V power / 1.5A |
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10µH |
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STPS5L60 |
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L6 |
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J2-7 |
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D2 |
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10µH |
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+5V / 1.5A |
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1N4148 |
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JP1 |
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D7 |
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STPS5L40 |
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L5 |
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10µH |
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+3.3V / 1.5A |
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R3 |
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C21 |
C23 |
C18 |
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C22 |
C25 |
C19 |
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C20 |
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47 |
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1200µF |
1200µF |
820µF |
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180µF |
180µF |
120µF |
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120µF |
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6.3V |
6.3V |
25V |
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R4 |
D3 |
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10V |
10V |
25V |
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25V |
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0 |
BYT01-400 |
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Q1 |
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IC1 |
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2N5551 |
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D10 |
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VIPer53 |
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R13 |
Q3 |
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1N5818 |
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R1 |
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VDD |
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DRAIN |
R5 |
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5.6k |
PN2222A |
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10k |
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18k |
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L7 |
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J2-10 |
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0.66W |
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+5V standby / 100mA |
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OSC |
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D9 |
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10µH |
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BAV21 |
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15V |
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C24 |
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D11 |
Q2 |
R14 |
R18 |
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39µF |
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1N4148 |
MPS2907A |
1K |
100 |
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35V |
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TOVL |
COMP |
SOURCE |
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Obsolete |
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C30 |
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6.8nF |
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C28 |
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R21 |
180µF |
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10V |
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4.99k |
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R15 |
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D12 |
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R19 |
R20 |
C29 |
1% |
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C26 |
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1N4148 |
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1k |
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1k |
4.7k |
10nF |
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100nF |
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R6 |
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IC2 |
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2.2k |
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PC817 |
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R23 |
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C3 |
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C4 |
C5 |
C6 |
DZ1 |
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4.7k |
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47µF |
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BZX79C |
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C10 |
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C27 |
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2.2nF |
100nF |
10nF |
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16V |
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10 |
4.7µF |
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100nF |
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4/17 |
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C7 |
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250V |
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1µF |
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IC3 |
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63V |
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Q4 |
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R16 |
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R17 |
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TL431LP |
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PN2222A |
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R22 |
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J2-6 |
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18k |
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18k |
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4.7k |
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GND |
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1% |
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Product(s) |
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J2-11 |
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R24 |
Standby |
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18k |
J2-12 |
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AN1948 - APPLICATION NOTE
2.1.1 Normal operation mode
In this mode, the Standby input is driven low, Q4 and Q2 are blocked and Q3 conductis. All the output voltages are delivered to the loads and both 5V and 5VStandby outputs are provided.
The transformer turn ratio leads to a voltage of about 30V across C24. This voltage is blocked by Q2, and the 5VStandby output is derived from the main 5V output through Q3. In the case where no load is connected on the 5VStandby output, R14 allows to absorb the Q3 base current delivered by R13.
The same applies at primary side for the auxiliary supply of IC1. In normal operation, the VDD pin energy is delivered by the standard auxiliary winding though D2. The corresponding voltage is higher than the one developed by the zener diode DZ1 on the base of Q1, and this transistor is blocked. In the mean time, the second auxiliary winding delivers five times more voltage than the one needed in standby mode (see section 2.1.2), and values as high as 130V can be observed across C10. As a consequence, C10, D3 and Q1 are high voltage type, and R5 may dissipate up to 1W.
2.1.2 Stand-by mode
All the output voltages are dropped down, except the 5VStandby one which is typically used to supply an infrared receiver and its decoding circuit, and also to maintain the Standby input in the high state, which
makes Q4 and Q2 conducting, and disables Q3 thanks to D11. Product(s)
As Q2 is conducting, the 5VStandby output is supplied through D9 and the corresponding winding of the main transformer. This winding therefore reduces its voltage by a ratio of about 5, because the regulation loop still maintains the value of 5V on this output. Since all the outputs are coupled together on the same transformer core, they are all divided by a ratio of about 5. This is sufficient to insure a reduced consumption mode, as the loads are now supplied with a much lower voltage.
D11 is needed in this mode to efficiently turn off Q3. Otherwise, its base remains high as it is supplied by R13 connected to a voltage of about 5V, and some reverse current flows from the 5VStandby output to the main 5V one.
On primary side, the standard auxiliary winding doesn’t provide a sufficient voltage, and Q1 acts as a
serial regulator with the voltage delivered by the second auxiliary winding, maintaining the VDD pin of
IC1 at higher level than the disabling threshold VDDoff. R14 on the 5VStandby output provides a
Obsolete
minimum consumption in this mode to insure -a suitable voltage for Q1.
The transition betweenProduct(s)the normal mode and the standby mode has been slowed down by C26. This is
mandatory to avoid any underor overvoltage on the outputs during this event. See also the following section.
the DC operating point from the 5VStandby output through R21 and R22. Note that it implement a split regulation, as the other outputs operate with a different value when
Obsoletein standby mode.
Some AC signals are also introduced into the regulation loop to insure stability. The conventional path is done through R18 connected to the 5VStandby output, but another AC component has been added thanks to C30 and R23 connected on the 12V power output. This is needed to prevent any instability in situations where the 5VStandby output is lightly loaded versus the 12V one. In order to transmit this signal, a resistance R20 has also been added in series with the conventional capacitive feedback C27 at the level of IC3.
The bandwidth of this regulation loop has been set at a few kHz in order to insure a good dynamic response when submitted to load variations, or during the transitions between the normal mode and the standby mode.
C29 on secondary side and C6 on primary side cancel any switching noise which may produce subharmonic operation.
5/17
AN1948 - APPLICATION NOTE
2.1.4 Drain voltage clamping
The board comes with a zener (DZ3) clamp type on the drain of the VIPer53 device. Provision is made to also use an R-C type clamping network to replace this zener. The corresponding components R2 and C8 are to be populated according to the bill of material. See par. 2.3.1.
2.1.5 Short circuit protection
This paragraph only deals with the main outputs (i.e. all the 5V, 12V and 3.3V outputs). The following section deals with the plasma ones.
When in normal mode, all these outputs are protected against a permanent short circuit. When the short circuit is applied on the 5VStandby, the short circuit current flows into D10 which bypasses Q3, thus avoiding its destruction. The protection is done through the overload feature of the VIPer53 device, which leads to hiccup mode when the COMP voltage remains high for a too long time. This time is adjusted by the capacitor on the TOVL pin, and is needed at startup for authorizing a temporary overload during the charge of the output capacitors.
In standby mode, only the 5VStandby output is protected thanks to D12 which forces the standby signal |
||||
in the low state, and the converter returns to the normal mode where Q2 is off. This is mandatory to avoid |
||||
the destruction of Q2 and D9 in this condition. The other outputs are not protected against a permanent |
||||
short circuit, because the converter can still regulate correctly the 5VStandby output even if one of the |
||||
others is short circuited. This is due to the high turn ratio existing between the 5VStandby winding and |
||||
the other ones, and to the low consumption on this output. Nevertheless, the user will adopt one of the |
||||
following options: |
|
|
|
|
- these outputs can withstand a short circuit for a few seconds. If this time is too long, the corresponding |
||||
rectifying diode may blow up, and the converter will enter into hiccup mode because of the short circuit |
||||
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|
Product(s) |
presented by the blown diode on secondary side of the transformer. |
||||
- additional diodes similar to D12 can be implemented on the other outputs to force the converter to the |
||||
normal mode, where it can withstand permanent short circuit on the main outputs. |
||||
2.1.6 Plasma display outputs |
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A whole set of outputs are dedicated to the driving of a plasma display in front of the equipment: Negative |
||||
|
|
Obsolete |
||
25V and 12V outputs, together with a symmetrical- |
+/-4.2V |
centered 5V higher than the -25V output |
||
voltage. |
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|
Please note that these outputs are not protected against short circuits or overloads. For instance, the |
||||
short circuit of the 4.2V outputs to ground leads to the destruction of R7 or R9. Also, the rectifying diodes |
||||
chosen for these outputs don’t withstand a permanent short circuit. |
||||
Figure 3: startup in normal mode |
|
Figure 4: startup in standby mode |
||
|
Product(s) |
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Ch1 : 12V out |
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Ch2 : 5Vstby out |
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Ch2 : 5Vstby out |
Obsolete |
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Ch3 : 5V out |
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Ch4 : 3.3V out |
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Ch1 : 12V out |
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Ch3 : 5V out |
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Ch4 : 3.3V out |
1 |
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1 |
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2 |
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2 |
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3 |
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3 |
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4 |
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4 |
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6/17