AN1842
APPLICATION NOTE
60W WIDE-RANGE POWER SUPPLY
FOR LCD MONITOR OR TV, USING THE L5991
by Claudio Spini
This document describes a reference design for a 60W Switch Mode Power Supply dedicated to LCD
TV sets or monitors. The board accepts full range input voltage (90 to 265Vrms) and delivers 5V and
12V. It has good efficiency and very good standby performance, able to meet the most stringent
standby rules.
Introduction
The LCD monitors and TVs are growing very fast, so to support this kind of applications, a dedicated reference design has been developed, taking into account all the requirements that are needed.
The proposed reference design can supply an LCD monitor or an LCD-TV as well, up to 22" panels, together with multimedia functions like audio. The SMPS accepts a full range input voltage and delivers 2
output voltages, a 5V dedicated to the scaler and µP, and a 12V dedicated to the backlight and audio. The
required standby power consumption is 0.8W at 230Vac, in order to satisfy the worldwide power saving
rules. The circuit is also fully protected against faults like output short circuit or over voltage. The market
cost pressure has requested a design approach with particular attention to the solution cost. The board
technology used is the standard thru-hole, but it can be changed very easily in SMT because most of components are available also in this technology. The circuit has been tested deeply in all the most salient
aspects with positive results and it has been integrated with a 22" LCD-TV application without showing
any problem.
Main characteristics
INPUT VOLTAGE: 90 ÷ 265 Vrms - 45-66 Hz
OUTPUT VOLTAGES: 5.1V±2% - @2A Dedicated to panel and digital circuitry for scaling
12V±10% - @4A Dedicated to backlight lamp inverters, audio and SCART
STANDBY Input power less than 0.8W @230Vac, delivering 30mA on 5.1V
FAULT PROTECTIONS: Short circuit on each output with auto-restart at short removal, Open loop
Safety&EMC: Safety: Acc. to EN60950, creepage and clearance minimum distance 6.4mm
PCB TYPE & SIZE: Cu Single Side 70 µm, CEM-1, 180 x 89 mm
EMC: According to EN50022 Class-B
January 2004
1/17
AN1842 APPLICATION NOTE
Figure 1. Electrical Diagram
2/17
AN1842 APPLICATION NOTE
The converter topology of this SMPS is the standard fly back, working in discontinuous and continuous
current mode. The operating frequency of the circuit (~50 kHz) has been chosen in order to obtain a compromise between the transformer size and the input filter complexity. Hence, the input EMI filter is a simple
Pi-filter, 1-cell only, for differential and common mode noise, using a 4-sectors coil filter. A NTC limits the
inrush current at plug-in. The transformer is a slot type, manufactured by PULSE-ELDOR designed according to the EN60950. Ferrite size is ETD34, the reflected voltage is ~95V providing enough room for
the leakage inductance voltage spike with still margin for reliability.
The reflected voltage, the switching frequency and the primary inductance have been chosen to allow the
continuous current operation of the transformer at full load, all over the input voltage range. This helps to
decrease the output capacitor size thanks to the better ratio between the rms and peak current. The network D10, C14, R5 clamps the peak of the leakage inductance voltage spike ensuring reliable operation
of the PowerMOS, while C21, D11 and R19 limit the dv/dt of the drain voltage.
The PowerMOS is a low cost STP5NK80ZFP, offering a good trade-off between the V
and the equivalent C
, housed in standard TO-220 or TO-220FP packages. In this design, the TO-
OSS
(BR)DSS
220FP (TO-220 insulated) has been used, mounted on a heat sink and fixed by a spring. Core of this design is the current mode primary controller, the L5991 integrating all the required blocks to manage the
control and protection of an SMPS. It is available in either DIP-16 (L5991) or in SO-16 (L5991D) packages.
The switching frequency is programmable by means of a an RC network (R11, R12, C15): during normal
operation R11 and R12 are connected in parallel by an internal switch (pin 16); when a light load is detected by the controller this internal switch is opened and the resulting frequency becomes lower, programmed only from C15 and R11.
If the load is further decreased the network D4, D5, R23 provides an additional frequency reduction, proportional to the load, allowing very low power consumption from the mains. Pins 15 and 3 are set in order
to allow the full duty-cycle operation and so the use of most of the energy stored in the bulk capacitor during hold-up operations. Because of the current mode control and the possibility for the duty cycle to exceed
50%, a slope compensation circuitry has been added.
A latched, over voltage protection has been implemented by using the pin 14 and a simple resistor network: in case of loop failure the circuit senses the Vcc and, when the voltage at that pin exceeds the internal threshold, the controller stops the operation until its Vcc drops below the UVLO voltage. The startup is done using a non-dissipative charge pump circuit to save power during standby.
The output rectifiers have been chosen in accordance with the maximum reverse voltage and their power
dissipation. The 5V rectifier is Schottky barrier type STPS5L40, a 5A-40V axial rectifier that thanks to the
low-forward voltage drop is housed in a DO-201 package.
The 12V rectifier is an STPS8H100, an high voltage Schottky rectifier offering a good trade-off between
the forward voltage drop and the maximum operating junction temperature. It is available from STM in 5
different package versions. For this design, the ISOWATT220AC (similar to a standard insulated TO-220)
has been used, mounted on a heat sink and fixed by a spring.
On both outputs, an LC filter has been added in order to filter out the high frequency ripple without increasing the output capacitors size or quality. The output voltage regulation is performed by the secondary feedback monitoring the 5.1V output. The feedback network is the typical one that uses a TL431 driving an
optocoupler, in this case an SFH617A-2, to ensure the required insulation between primary and secondary. The opto-transistor drives directly the COMP pin of the L5991. Here following some waveforms during
the normal operation at full load:
, the RDS(on)
3/17
AN1842 APPLICATION NOTE
Figure 2. Drain voltage & current @115 VAC -
60Hz - full load
CH1: VQ4 - Drain
CH2: V
CH4: V
Figure 3. Drain voltage & current @230 V
(Vcc)
PIN8
(Drain Current)
R16
AC
50Hz - full load
ing the worst operating condition and they are indicated on the right of figure 5. The margin, with
respect to the maximum voltage withstood by each
diode, ensures safe operating conditions for these
devices.
Figure 4. Drain voltage & current @265 V
AC
-
50Hz - full load
-
CH1: VQ4 - Drain
CH2: V
CH4: V
(Vcc)
PIN8
(Drain Current)
R16
CH1: VQ4 - Drain
CH2: V
CH4: V
(Vcc)
PIN8
(Drain Current)
R16
The pictures here above show the drain voltage
and current at the nominal input mains voltage
during normal operation at full load. As visible, the
circuit works in CCM both at nominal high and low
mains.
The figure 4 shows the measurement of the drain
peak voltage at full load and maximum input mains
voltage. The measured voltage of 672V, ensures
a reliable operation of the MOSFET with a good
margin against the maximum BV
. Even the
DSS
maximum rectifiers PIV have been measured dur-
Figure 5. Maximum rectifiers PIV @Vin = 265
V
- 50 Hz and full load
AC
CH3: +5V RECTIFIER: Anode voltage
CH4: +12V RECTIFIER: Anode voltage
Here following the most salient controller IC signals are shown. In both pictures it is possible to
distinguish clean waveforms free of hard spikes or
noise that could affect the controller correct operation.
4/17
AN1842 APPLICATION NOTE
Figure 6. Drain voltage & current @115 VAC -
60Hz - full load
CH2: V
CH3: V
CH4: V
PIN10
PIN6
PIN2
(Out)
(Comp)
(RCT)
Figure 7. Drain voltage & current @230 VAC -
50Hz - full load
CH2: V
CH3: V
CH4: V
PIN10
PIN6
PIN2
(Out)
(Comp)
(RCT)
Cross regulation
In the following tables it has been reported the output voltage cross regulation measurements with static
loads. The overall efficiency of the converter is also calculated at the nominal input voltages.
To check the application circuit it has been tested keeping constant the current on the 5V and varying the
12V load. As visible in both tables, the voltages are within their tolerance at any load condition and the
circuit efficiency is good
.
5V ± 2% 12V ± 10%
Vout
[V]
@Iout
[A]
Vout
[V]
@Iout
[A]
TOLERANCE
Pout
[W]
TOT
Pin
[W]
115 Vac
Efficiency
Vaux
[V]
fs
[KHz]
5.106 2 12.11 4 OK 58.65 71.7 81.8% 18.3 51
5.107 2 12.23 3 OK 46.90 56.6 82.9% 17.4 51
5.108 2 12.40 2 OK 35.02 42.1 83.2% 16.7 51
5.110 2 12.72 1 OK 22.94 27.7 82.8% 16.5 51
5.110 2 13.11 0.5 OK 16.78 20.7 81.0% 16.6 51
5.108 1 11.85 4 OK 52.51 63.9 82.2% 17.5 51
5.108 1 12.00 3 OK 41.11 49.4 83.2% 16.7 51
5.110 1 12.15 2 OK 29.41 35.0 84.0% 16.2 51
5.112 1 12.39 1 OK 17.50 21.0 83.3% 15.9 51
5.112 1 12.66 0.5 OK 11.44 14.0 81.7% 15.9 51
5/17
AN1842 APPLICATION NOTE
5V ± 2% 12V ± 10%
Vout
[V]
5.106 2 12.09 4 OK 58.57 69.3 84.5% 17.7 51
5.107 2 12.23 3 OK 46.90 55.3 84.8% 17.3 51
5.109 2 12.40 2 OK 35.02 41.2 85.0% 16.9 51
5.110 2 12.74 1 OK 22.96 27.6 83.2% 16.6 51
5.110 2 13.12 0.5 OK 16.78 20.8 80.7% 16.6 51
5.108 1 11.85 4 OK 52.51 63.9 82.2% 17.5 51
5.108 1 12.00 3 OK 41.11 49.4 83.2% 16.7 51
5.110 1 12.15 2 OK 29.41 35.0 84.0% 16.2 51
5.112 1 12.39 1 OK 17.50 21.0 83.3% 15.9 51
5.112 1 12.66 0.5 OK 11.44 14.0 81.7% 15.9 51
@Iout
[A]
Vout
[V]
@Iout
[A]
TOLERANCE
Pout
[W]
TOT
Pin
[W]
230 Vac
Efficiency
Vau x
[V]
fs
[KHz]
Standby operation
Like in the previous section, the output voltages and the efficiency have been checked, and the input power has been measured. It is clearly visible that with the required standby load (5V@30mA, 12V@0mA)
the input power consumption is well below 800mW at both the input voltage ranges. Besides, the circuit has been characterised at both the nominal input voltage values for different output load and the efficiency is high in all conditions. In the fig. 8, it is shown the output voltage variation as a function of the 5V
current.
During the standby operation the circuit works at reduced frequency, according to load and input voltage
therefore, thanks to this function, the switching losses are minimized. This allows reaching very low standby consumption because in a power switch the switching and the capacitive losses are directly proportional to the working frequency.
5V 115 Vac
Vout [V] @Iout [mA]
5.11 20 0.102 0.433 23.6%
5.11 30 0.153 0.515 29.8%
5.11 40 0.204 0.593 34.5%
5.11 50 0.256 0.667 38.3%
5.11 60 0.307 0.745 41.1%
5.11 80 0.409 0.881 46.4%
5.11 100 0.511 1.021 50.1%
5V 230Vac
5.11 20 0.102 0.493 20.7%
5.11 30 0.153 0.582 26.3%
5.11 40 0.204 0.672 30.4%
5.11 50 0.256 0.755 33.8%
5.11 60 0.307 0.842 36.4%
5.11 80 0.409 1.008 40.6%
5.11 100 0.511 1.168 43.8%
6/17
Pout
TOT [W]
Pin [W] Efficiency
AN1842 APPLICATION NOTE
Figure 8. INPUT POWER @LOW LOAD
1.200
1.000
0.800
0.600
Pin @Stand-by
0.400
0.200
0.000
20 30 40 50 60 80 100
Pin @115Vac
Pin@220Vac
Iout +5V [mA]
Here following, in figures 9 ad 10 some waveforms
during standby are shown:
Figure 9. Standby @115 V
- 60Hz 5V @50mA
AC
load
Output voltage ripple @full load
Figure 11. Output voltage ripple @Vin = 115
Vac - 60 Hz and full load
CH3: +5V Output voltage
CH4: +12V Output voltage
In figure 11 the output voltage ripples at switching
frequency are measured. As shown, the ripple
and the spikes are very low thanks to the additional LC filters added on both output and avoiding the
use of bigger or expensive output capacitors.
The residual line frequency modulation is very low
at any input voltage.
CH1: VQ4 - Drain
CH2: V
CH4: V
PIN8
PIN6
(Vcc)
(Comp)
Figure 10. Standby @230 V
50mA load
CH1: VQ4 - Drain
CH2: V
CH4: V
PIN8
PIN6
(Vcc)
(Comp)
- 50Hz 5V @
AC
Dynamic Load Tests
Figure 12 shows the output voltage regulation for
a dynamic load variation of the 5V output. As
shown in the picture the voltage variation and the
response time are very good showing a good loop
behaviour. In fact, the 5V voltage variation is less
than 20mV (0,4%), and the spikes during the load
transition, due to the filter inductor on the output,
are only 75mV beyond the steady state (1,5%).
The measured recovery time is few tens of microseconds. The variations induced on the 12V output have been also checked without showing any
abnormal variation. Besides, the circuit response
has been verified at minimum, nominal and maximum input voltage, showing no significant change.
7/17
AN1842 APPLICATION NOTE
Figure 12.
CH3: +5 Vout
CH4: +12 Vout
+5V Dynamic load 1.5 ÷ 2A, 70Hz
+12V: FULL LOAD - @115 V
AC
- 60Hz
In Figure 13 it is reported the response of the output voltages for a load variation of the 12V output
as detailed on top of the picture. The measurement has been done varying the 12V load from
50% to 100% load: the voltage variation is around
340mV and the 5V output is almost unaffected.
Therefore, the conclusion is that there is no abnormal behaviour of the SMPS generated by a load
change, allowing a good confidence for the integration of the SMPS in the equipment.
Figure 13. +12V Dynamic load 2 ÷ 4A, 70Hz
+5V: FULL LOAD - @115 V
- 60Hz
AC
starts to operate and the output voltages begin to
rise up to the nominal value, where the control
loop provides for the regulation. The wake-up time
at 115Vac is 1.2 s, which is a quite typical time for
this kind of Power Supplies. Besides, on the picture it is clearly visible that no any overshoot, undershoot, dip or lost of control happens during the
power supply start-up phase.
Figure 14. Wake-up time @115 V
CH1: VQ4 - Drain
CH2: V
CH3: +5 Vout
CH4: +12 Vout
PIN8
(VCC)
- 60Hz
AC
Figure 15. Start-Up Behaviours @full load -
@90 V
- 60Hz
AC
CH3: +5 Vout
CH4: +12 Vout
Start-Up Behaviour @full load and Wake-up time
In figure14 the wake-up time is measured at the
lower nominal input mains and the controller startup sequence is shown. The Vcc capacitor is
charged by the charge pump circuit and when its
voltage reaches the start-up threshold the device
8/17
CH3: +5 Vout
CH4: +12 Vout
In the above picture the rising slopes at full load of
the output voltages at minimum input mains voltage are captured and the rise time is measured.
As shown in the pictures, the rising time is monotonic and it is almost constant overall the input
mains range. No any overshoot or abnormal behaviour is present overall the input main range.
AN1842 APPLICATION NOTE
Turn-Off and Hold-up time
In figure 16 the most salient waveforms at turn-off
are shown. Even at turn off the transition is clean,
without abnormal behaviour like restarting attempts or loss of control by the loop. The Hold-up
time, in evidence between the vertical lines, is 13.6
ms at 115Vac-50Hz, full load and becomes around
67ms at 230Vac.
Figure 16. Hold-up @115 V
CH1: V
CH3: +12V Vout
CH4: +5V Vout
C13
-50Hz - full load
AC
Figure 17. Short circuit on 5V @90 V
full load
CH1: VQ4 - Drain
CH2: VPIN8 (Vcc)
CH4: +5V short circuit current
Figure 18. Short circuit on 5V @265 V
- full load
- 60Hz -
AC
- 50Hz
AC
Short-Circuit Tests at Full Load
The short circuit tests have been done under several conditions, all over the input mains range. To
avoid any catastrophic failure of the circuit due to
overstress, a deep check of component stress has
been done. The main circuit parameters that have
been checked are the Mosfet drain voltage and the
mean value of the output current. The drain voltage is an important parameter to be monitored
during short circuits because an excessive increase due to the transformer leakage inductance
and the overcurrent flowing in the primary can
cause the MOSFET BV
to be exceeded. In the
DSS
proposed circuit, thanks to the low leakage inductance of the transformer and to the start-up component correct dimensioning, in case any output is
shorted, the MOSFET drain voltage is below its
and the mean value of the output current is
BV
DSS
low too, thus preventing component overheating
because of the excessive power dissipation. In this
case the reliability against long term-shorts is not
affected even at 264Vrms. The auto-restart at
short removal has been also checked and it is correct in all conditions.
CH1: VQ4 - Drain
CH2: VPIN8 (Vcc)
CH4: +5V short circuit current
As clearly indicated by the waveforms in figure 17
and 18, the circuit works in hiccup mode, keeping
the mean value of the current at levels compatible
with the component rating. As visible the circuit
working time is constant because it depends only
on the auxiliary capacitor value, while the dead
time is inversely proportional to the input mains
voltage. In the following figures 19 and 20 the
waveforms relevant to the 12V output in short circuit at both the nominal input mains voltage are reported: as visible, the circuit protects itself and the
load.
9/17
AN1842 APPLICATION NOTE
Figure 19. Short circuit on 12V @90 VAC - 60Hz
- full load
CH1: VQ4 - Drain
CH2: V
CH4: +12V short circuit current
Figure 20.
(Vcc)
PIN8
Short circuit on 12V @265 VAC - 50Hz
- full load
tions of the equipment, with a consumption halved
with respect to the maximum output power levels
(I
+12V
= 2A, I
+5V
= 1A).
– At Vin = 90Vac: shorting each output the over
current protection works correctly, providing for
the hiccup mode.
– At Vin = 265Vac: the circuit behaves correctly.
Figure 21. Short circuit on 5V @265 V
- half load
- 50Hz
AC
CH1: VQ4 - Drain
CH2: V
CH4: +12V short circuit current
PIN8
(Vcc)
Short Circuit Protection @ Low Load
After the full load tests, some checks on the short
circuit protection with reduced loads have been
done, as reported here following. The tests have
been done even at minimum and maximum input
voltage with the same results, as the previous
tests.
@Half Load
The waveforms of figure 21 are relevant to a short
circuit test simulating a fault during normal opera-
CH1: VQ4 - Drain
CH2: V
CH4: +5V short circuit current
PIN8
(Vcc)
@Reduced Load
This condition simulates a fault during an operating transition of the equipment, with the backlight
off and a reduced consumption of the other output
(I
+12V
= 0A, I
= 0.5A).
+5V
– At Vin = 90Vac: shorting each output the over
current protection works correctly, providing for
the hiccup working mode.
– At Vin = 265Vac: the behaviour of the circuit is
correct like at 90Vac.
–
@Standby
This condition simulates a fault during the standby
operation of the equipment, with the backlight and
the scaler off, and the µP working with a reduced
consumption (I
+12V
= 0A, I
= 33mA).
+5V
– At Vin = 90Vac: shorting each output the over-
current protection works correctly, providing for
the hiccup working mode.
– At Vin = 265Vac: the behaviour of the circuit is
correct like at 115Vac.
10/17
AN1842 APPLICATION NOTE
Figure 22. Short circuit on 5V @265 VAC - 50Hz
- standby load
CH1: VQ4 - Drain
CH2: V
CH4: +5V current in short circuit
Figure 23. Short circuit on 12V @265 V
PIN8
(Vcc)
AC
-
50Hz - standby load
turn-off, preventing the hiccup mode. To avoid
this, the circuit around Q2 and Q3 has been added, providing the hiccup mode anyway. As visible
in the pictures, the SMPS is always protected even
in this very critical load condition.
Over Voltage Protection
The open-loop operation is a very dangerous
event that could happen in case of a feedback circuitry failure. In this case, the SMPS output voltages can increase up to dangerous values,
depending on the load by each output and the
transformer coupling between the windings. Thus,
if the circuit is not properly protected, the rectifiers
and the output capacitors can be overstressed and
be destroyed or even worse, to catch light. To
avoid this, the safety rules ask that the SMPS have
a protection against the mentioned safety risks. In
the proposed circuit, in case of a control loop failure, a L5991 internal comparator stops the controller operation when the voltage at pin 14 (DIS)
reaches 2.5V and remains latched until the Vcc
voltage decreases below the UVLO threshold. So,
a very safe protection with the L5991 is realized
just by means of few passive components.
The circuit has been tested opening the loop, the
output voltages have been measured giving the
following results overall the mains input voltage
range:
230Vac – 50Hz
@FULL LOAD
5V @ 2A 12V @ 4A 5V @ 0.03A 12V @0A
V
: 5.7V V
5V
13.5V V5V: 6.24V V
12V:
230Vac – 50Hz
@STANDBY
: 15.8V
12V
CH1: VQ4 - Drain
CH2: V
CH4: +5V current in short circuit
PIN8
(Vcc)
The main circuit parameter measurements have
been done also during the test at reduced load or
standby. In detail, during standby short it is possible to check the perfect functionality of the protection. This load condition in fact, is critical because
all the power available from the converter can be
delivered to one output only, because the others
are lightly loaded or unloaded, and this can bring
to the destruction of the rectifier of the shorted output. Besides, during standby operation, the transformer coupling and the leakage inductance may
be capable of supplying the controller charging the
V
capacitor by the spikes generated at Mosfet
DD
As shown in the table, in both conditions the measured voltages are not critical for the circuitry.
Conducted Noise Measurements (Pre-Compliance Test)
The following pictures are the peak conducted
noise measurements at full load and nominal
mains voltages. The limits shown on the diagrams
are those specified by the EN55022 CLASS-B,
which is the most widely used for Information
Technology Equipment intended for domestic use,
in the bandwidth 150KHz 30MHz. The filter configuration used is the 2-wires one, without the ground
connection at mains plug, suitable for domestic
equipment like LCD-TVs. As visible on the diagrams, there is a good margin between the peak
measures with respect to the AVG limits (lower
ones), and this assures that the QP and Average
measures will be within their respective limits.
11/17
AN1842 APPLICATION NOTE
Figure 24. EN55022 Class-B Peak Measure
@115 V
- 60Hz - FULL LOAD
AC
Figure 25. EN55022 Class-B Peak Measure 230
VAC - 50Hz - FULL LOAD
Thermal measures
In order to check the reliability of the design a thermal mapping by means of an IR camera has been done.
In the table here below the temperature of some salient components is reported at 115Vac and 230Vac
input voltage, at ambient temperature (24°C).
@115Vac @230Vac
Point Reference Description Temperature Temperature
A D9 BRIDGE RECTIFIER 74°C54°C
B L2 FILTER COIL 56°C40°C
CQ4 POWERMOS 70°C58°C
D T1 POWER TRANSF. 53°C56°C
E D16 +5V RECTIFIER 61°C60°C
F D13 +12V RECTIFIER 64°C64°C
As visible in the above table there are not component working at a temperature level that can be considered critical for their reliability.
12/17
Board lay-out
Figure 26. Board silk-screen and bottom plane (not in scale)
AN1842 APPLICATION NOTE
■ Original size: 89x180mm
■ Copper thickness: 70µm
■ Material: CEM-1
Conclusions
An SMPS for LCD monitors or LCD-TV sets has been completely designed, assembled and tested using
the L5991. All the different aspects (Component Electrical Stress, Functions, Protections, Conducted
EMI, Thermal Stress) have been checked, giving positive results. The design meets also low-cost and lowcomplexity requirements, key factors in the Consumer Electronic market.
13/17
AN1842 APPLICATION NOTE
References
[1] "L5991 Data Sheet"
[2] "AN1537: A simple trick enhances L5991's standby function"
ANNEX1: Transformer spec
Transformer General Description
APPLICATION TYPE: Consumer, Home Appliance
TRANSFORMER TYPE: Open, Varnished only
WINDING TYPE Slot
COIL FORMER: Vertical type, 7+7 pins
MAX. TEMP. RISE: 45°C
MAX. OPERATING AMB. TEMP. : 60°C
MAINS INSULATION: ACC. WITH EN60065 - EN60950
Electrical Characteristics
CORE TYPE/GRADE: ETD34 - 3C90 or equivalent
PRIMARY INDUCTANCE: 825 µH ±10% @1KHz - 0.25V
LEAKAGE INDUCTANCE: 15 µH MAX @ 10KHz - 0.25V [1]
PEAK PRIMARY CURRENT: 2 Apk
[1]: Measured between pins 3-7 with all secondary shorted
PROVIDED BY PULSE-ELDOR P/N: 2074.5056C
Figure 27. Electrical Diagram
3
PRIM.
7
11
AUX
13
12
10
2-
6-
+5V
PINS:
7-3 PRIMARY 0.84 A
2/4-6/8 5V 2.6 A
12-10 12V 5.3 A
11-13 15V (AUX) 0.05 A
PRIMARY SECONDARY
DC OUTPUT
VO LTAG E:
RMS
CURRENT:
RMS
RMS
RMS
RMS
NUMBER OF
TURNS:
53
3
7
9
14/17
AN1842 APPLICATION NOTE
ANNEX2:
Part List
Designator
C1 RES NOT MOUNTED
C10 220N - 50V CERCAP AVX
C101 (D17) 47N-400V POLIESTER FILM CAP MKT R66 - ARCOTRONICS
C102 220P - 50V CERCAP AVX
C11 100N - 50V CERCAP AVX
C12 220N - 50V CERCAP AVX
C13 100uF-400V ALUMINIUM ELCAP LP4 SERIES - ELNA
C14 2N2-1KV HR HV CERCAP DEHR33A222K - MURATA
C15 4N7 - 50V CERCAP AVX
C16 4N7 - 50V CERCAP AVX
C17 4N7 - 50V CERCAP AVX
C18 330P - 50V CERCAP AVX
C19 22uF-25V ALUMINIUM ELCAP RUBYCON
C2 RES NOT MOUNTED
C20 22uF-25V ALUMINIUM ELCAP RUBYCON
C21 220PF-2KV HR HV CERCAP DEHR33A221K - MURATA
C22 1N0 - Y1 Y1 SAFETY CAP. DE1E3KX102M - MURATA
C23 1N0 - Y1 Y1 SAFETY CAP. DE1E3KX102M - MURATA
C24 2200uF-16V YXF ALUMINIUM ELCAP RUBYCON
C25 1000uF-35V YXF ALUMINIUM ELCAP RUBYCON
C26 1000uF-35V YXF ALUMINIUM ELCAP RUBYCON
C27 470uF-10V YXF ALUMINIUM ELCAP RUBYCON
C28 100uF-50V YXF ALUMINIUM ELCAP RUBYCON
C29 22N - 50V CERCAP AVX
C3 RES NOT MOUNTED
C30 N68 - 50V CERCAP AVX
C31 3N3 - 50V CERCAP AVX
C32 47uF-25V YXF ALUMINIUM ELCAP RUBYCON
C33 10N - 50V CERCAP AVX
C4 RES NOT MOUNTED
C5 RES NOT MOUNTED
C6 RES NOT MOUNTED
C7 470PF - 50V CERCAP AVX
C8 220N-X2 X2 FILM CAPACITOR
C9 220N-X2 X2 FILM CAPACITOR
D10 STTH1L06 FAST REC. RECTIFIER STMicroelectronics
D101 1N4148 GEN. PURPOSE DIODE WISHAY
D102 (R13) 1N4148 GEN. PURPOSE DIODE WISHAY
D11 STTH1L06 FAST REC. RECTIFIER STMicroelectronics
D12 RES NOT MOUNTED
D13 STPS8H100CF POWER SCHOTTKY RECT. STMicroelectronics
D14 1N4007 RECTIFIER DIODE WISHAY
Part Type/
Part Value
Description Supplier
R46-KI 3220 00 L2M - ARCOTRONICS
R46-KI 3220 00 L2M - ARCOTRONICS
15/17
AN1842 APPLICATION NOTE
Part List (continued)
Designator
D15 1N4007 RECTIFIER DIODE WISHAY
D16 STPS5L40 POWER SCHOTTKY RECT. STMicroelectronics
D2 1N4148 GEN. PURPOSE DIODE WISHAY
D3 BAV21 GEN. PURPOSE DIODE WISHAY
D4 1N4148 GEN. PURPOSE DIODE WISHAY
D5 1N4148 GEN. PURPOSE DIODE WISHAY
D6 BAV21 GEN. PURPOSE DIODE WISHAY
D7 1N4148 GEN. PURPOSE DIODE WISHAY
D8 1N4148 GEN. PURPOSE DIODE WISHAY
D9 2KBP06M BRIDGE RECTIFIER WISHAY
F1 FUSE T2A FUSE 2 AMP. TIME DELAY WICKMANN
J1 INPUT CONNECTOR, 2/3 POLES, 7.5MM MOLEX
J2
JP1 JUMPER WIRE JUMPER
JP2 RES NOT MOUNTED
L1 RES NOT MOUNTED
L2 253Y1R2 25mH-1.2A - CM FILTER INDUCTOR TDK
L3 2uH-4A 2uH-4A AXIAL FILTER INDUCTOR B82111 SERIES - EPCOS
L4 10uH RF AXIAL CHOKE B78108-S1103-K - EPCOS
L5 2.7uH DRUM COIL 2.7uH-4A ELC08D SERIES - PANASONIC
Q1 BC547A SMALL SIGNAL NPN BJT STMicroelectronics
Q2 BC547A SMALL SIGNAL NPN BJT STMicroelectronics
Q3 BC547A SMALL SIGNAL NPN BJT STMicroelectronics
Q4 STP5NK80ZFP POWER MOSFET STMicroelectronics
R1 RES NOT MOUNTED
R10 4K7 - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R101 (D1) 100R - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R11 10K - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R12 12K - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R14 1K0 - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R15 47R - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R16 1R2 - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R17 1R2 - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R18 1R2 - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R19 4K7 - 2W - 5% POWER RESISTOR 2W BEYSCHLAG
R2 NTC_10R S236 NTC THERMISTOR EPCOS
R20 RES NOT MOUNTED
R21 8K2 - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R22 3K9 - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R23 6K2 - 1/4W - 1% METAL FILM RESISTOR BEYSCHLAG
R24 2K0 - 1/4W - 1% METAL FILM RESISTOR BEYSCHLAG
R25 12K - 1/4W - 1% METAL FILM RESISTOR BEYSCHLAG
R26 1K5 - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
Part Type/
Part Value
Description Supplier
OUTPUT CONNECTOR, 9 POLES, 2.54MM
MOLEX
16/17
AN1842 APPLICATION NOTE
Part List (continued)
Designator
R27 10R - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R28 82K - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R29 2K43 - 1/4W - 1% METAL FILM RESISTOR BEYSCHLAG
R3 470K - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R30 2K43 - 1/4W - 1% METAL FILM RESISTOR BEYSCHLAG
R31 1K0 - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R32 47K - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R33 12K - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R34 3K3 - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R35 10K - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R4 470K - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R5 150K - 2W - 5% POWER RESISTOR 2W BEYSCHLAG
R6 33R - 1/4W - 5% STANDARD FILM RESISTOR BEYSCHLAG
R7 RES NOT MOUNTED
R8 RES NOT MOUNTED
R9 RES NOT MOUNTED
T1 2074.5056C POWER TRANSFORMER PULSE-ELDOR
U1 L5991 PRIMARY CONTROLLER WITH STANDBY STMicroelectronics
U2 SFH617A-2 OPTOCOUPLER INFINEON
U3 TL431ACZ SHUNT REGULATOR STMicroelectronics
Part Type/
Part Value
HEAT SINK FOR Q4
HEAT SINK FOR D13
Rth
Rth
Description Supplier
= 15°C/W P/N 6098B THERMALLOY WITH
HS-AMB
CLAMP
= 10°C/W P/N 6099B THERMALLOY WITH
HS-AMB
CLAMP
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of use of such information nor for any infringement of patents or other rights of third parties which may result from its use. No license is granted
by implication or otherwise under any patent or patent rights of STMicroelectronics. Specifications mentioned in this publication are subject
to change without notice. This publication supersedes and replaces all information previously supplied. STMicroelectronics products are not
authorized for use as critical components in life support devices or systems without express written approval of STMicroelectronics.
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17/17
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