SGS-THOMSON TDA2030A Technical data

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18W Hi-Fi AMPLIFIER AND 35W DRIVER

DESCRIPTION

The TDA2030Ais a monolithic IC in Pentawatt 
package intended for use as low frequency class
AB amplifier.

With V
reliable applications without regulated supply and
for 35W driver circuitsusing low-cost complemen­tary pairs.

The TDA2030A provides high output current and
hasvery low harmonic and cross-overdistortion.

Furtherthe deviceincorporatesa short circuitpro­tection system comprising an arrangement for
automaticallylimitingthe dissipatedpowersoas to
keep the working point of the output transistors
within their safe operating area. A conventional
thermalshut-downsystem is also included.

= 44V itis particularlysuited for more

S max

TDA2030A

PENTAWATT

ORDERING NUMBERS : TDA2030AH

TDA2030AV

TYPICALAPPLICATION

March 1995

1/15

TDA2030A

PIN CONNECTION (Topview)

TESTCIRCUIT

THERMAL DATA

Symbol Parameter Value Unit

R

2/15

th (j-case)

Thermal Resistance Junction-case Max 3

°C/W

TDA2030A

ABSOLUTE MAXIMUMRATINGS

Symbol Parameter Value Unit

V

V
V

P

T

stg,Tj

ELECTRICALCHARACTERISTICS

(Refer to thetest circuit,V

Symbol Parameter Test Conditions Min. Typ. Max. Unit

V

V

I

P

BW Power Bandwidth

SR Slew Rate 8

G
G

d

d

e

S/N Signal to Noise Ratio

R

SVR Supply Voltage Rejection

T

Supply Voltage

s

Input Voltage V

i

Differential Input Voltage

i

I

Peak Output Current (internallylimited) 3.5 A

o

Total Power Dissipation at T

tot

case

=90°C

± 22

s

± 15

20 W

Storage and Junction Temperature – 40 to + 150 °

= ± 16V,T

S

Supply Voltage

s

I

Quiescent Drain Current 50 80 mA

d

Input Bias Current

I

b

Input Offset Voltage

os

Input Offset Current ±

os

Output Power d = 0.5%, Gv= 26dB

O

Open Loop Voltage Gain f = 1kHz 80 dB

v

Closed Loop Voltage Gain f = 1kHz 25.5 26 26.5 dB

v

d Total Harmonic Distortion

Second Order CCIF Intermodulation

2

Distortion
Third Order CCIF Intermodulation

3

Distortion
Input Noise Voltage B = Curve A

N

Input Noise Current B = Curve A

i

N

Input Resistance (pin 1) (open loop) f = 1kHz 0.5 5

i

Thermal Shut-down Junction

j

Temperature

=25oC unless otherwise specified)

amb

= ± 22V

V

S

= ± 22V ± 2 ± 20

V

S

f = 40 to 15000Hz

R

L

R

V

=±19V RL=8Ω

S

= 15W RL=4Ω 100 kHz

P

o

= 0.1 to 14W RL=4Ω

P

o

f = 40 to 15 000Hz f = 1kHz

= 0.1 to 9W, f = 40 to 15 000Hz

P

o

= 4W, f2–f1= 1kHz, RL=4Ω 0.03 %

P

O

L

R

L

f1= 14kHz, f2= 15kHz

= 13kHz

2f

1–f2

B = 22Hz to 22kHz

B = 22Hz to 22kHz

=4Ω,Rg= 10kΩ, B = Curve A

R

L

= 15W

P

O

=1W

P

O

=4Ω,Rg= 22kΩ

R

L

= 26dB, f = 100 Hz

G

v

=4Ω
=8Ω

=8Ω

± 6 ± 22

0.2 2

20 ± 200

15

18

10

12

13

16

0.08

0.03

0.5

0.08 %

2
310

50
80 200pApA

106

94

54 dB

145 °C

V/µsec

V

V

C

V

µA

mV

nA

W

%
%

%

µV
µV

dB
dB

MΩ

3/15

TDA2030A

Figure1 :SingleSupply Amplifier

Figure2 : OpenLoop-frequencyResponse

Figure4 : TotalHarmonic Distortion versus

OutputPower (test using rise filters)

Figure 3 : Output Powerversus Supply Voltage

Figure 5 : Two ToneCCIF Intremodulation

Distortion

4/15

TDA2030A

Figure6 : LargeSignal Frequency Response Figure 7 : MaximumAllowable Power Dissipation

versusAmbientTemperature

Figure8 : OutputPower versus Supply Voltage

Figure 9 : Total HarmonicDistortion versus

OutputPower

Figure10 : OutputPower versus Input Level Figure 11 : Power DissipationversusOutput

Power

5/15

TDA2030A

Figure12 : SingleSupply HighPower Amplifier (TDA2030A+ BD907/BD908)

Figure13 : P.C.Board and Component Layout for the Circuit of Figure 12 (1:1 scale)

6/15

TDA2030A

TYPICALPERFORMANCEOF THE CIRCUIT OF FIGURE 12

Symbol Parameter Test Conditions Min. Typ. Max. Unit

V

P

G

SR Slew Rate 8

V

S/N Signal to Noise Ratio

Figure14 : TypicalAmplifierwith SpiltPower Supply

Supply Voltage 36 44 V

s

Quiescent Drain Current Vs= 36V 50 mA

I

d

o

Output Power

d = 0.5%, R

d = 10%, R

Voltage Gain f = 1kHz 19.5 20 20.5 dB

v

d Total Harmonic Distortion f = 1kHz

= 20W f = 40Hz to 15kHz

P

o

Input Sensitivity

i

= 20dB, f = 1kHz, Po= 20W, RL=4Ω 890 mV

G

v

=4Ω,Rg= 10kΩ, B = Curve A

R

L

=4Ω, f = 40 z to 15Hz

L

=4Ω, f = 1kHz

L

V

s

V

s

V

s

V

s

P

o

P

o

= 39V
= 36V

= 39V
= 36V

= 25W
=4W

35
28

44
35

0.02

0.05

108
100

V/µsec

W
W

W
W

%
%

dB

Figure15 : P.C.Board and Component Layout for the Circuit of Figure 14 (1:1 scale)

7/15

TDA2030A

Figure16 : BridgeAmplifier with SplitPower Supply (PO= 34W, VS= ± 16V)

Figure17 : P.C.Boardand ComponentLayout for theCircuit of Figure16 (1:1 scale)

MULTIWAY SPEAKERSYSTEMSAND ACTIVE
BOXES

Multiway loudspeaker systems provide the best
possible acoustic performance since each loud­speaker is specially designed and optimized to
handle a limited range of frequencies.Commonly,
these loudspeaker systems divide theaudio spec­trum intotwo or three bands.
To maintainaflat frequencyresponseovertheHi-Fi
audio range the bands covered by each loud­speakermust overlap slightly. Imbalance between
the loudspeakers produces unacceptable results

therefore it is important to ensure that each unit
generates the correct amount of acoustic energy
for its segmento of the audio spectrum. In this
respect it is also important to know the energy
distributionofthe music spectrumto determinethe
cutoff frequenciesof the crossoverfilters (seeFig­ure 18).As an example a 100Wthree-way system
with crossover frequencies of 400Hz and 3kHz
would require 50W for the woofer, 35W for the
midrange unit and 15W for thetweeter.

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TDA2030A

Figure18 : Power Distribution versus Frequency

Both active and passive filters can be used for
crossoversbut today activefilters cost significantly
less than a good passive filter using air cored
inductors and non-electrolyticcapacitors. In addi­tion, active filters do not suffer from the typical
defectsof passive filters:

- powerless

- increased impedance seen by the loudspeaker
(lowerdamping)

- difficulty of precise design due to variable loud­speaker impedance.

Obviously, activecrossovers can only be used if a
poweramplifieris provided for each drive unit.This
makes it particularlyinteresting and economically
soundto use monolithicpower amplifiers.

In someapplications, complex filters are not really
necessaryand simple RC low-passand high-pass
networks(6dB/octave)can be recommended.

The result obtained are excellent because this is
the best type of audio filter and the only one free
from phaseand transientdistortion.

The rather poor out of band attenuation of single
RC filters means that the loudspeaker must oper­ate linearlywell beyondthe crossoverfrequencyto
avoid distortion.

A more effective solution, named ”Active Power
Filter” by SGS-THOMSONis shownin Figure 19.

Figure 19 : ActivePower Filter

The proposed circuit can realizecombined power
amplifiers and 12dB/octaveor 18dB/octavehigh­pass orlow-pass filters.

In practice, at the input pins of the amplifier two
equal and in-phase voltages are available, as re­quired for the active filteroperation.

Theimpedanceat thepin(-) is of theorderof100Ω,
while that of thepin (+) isvery high, which is also
whatwas wanted.

The component values calculated for f

= 900Hz

c

using a Bessek3rd orderSallen and Keystructure
are :

C1=C2=C

22nF

3

R

1

8.2kΩ 5.6kΩ 33kΩ

R

2

R

3

Usingthistypeof crossoverfilter,a complete3-way
60W active loudspeaker system is shown in Fig­ure 20.

It employs 2nd order Buttherworth filters with the
crossoverfrequenciesequal to 300Hz and 3kHz.
The midrangesection consistsof twofilters, a high
pass circuit followed by a low pass network. With
V

=36V theoutput power deliveredto thewoofer

S

is 25W at d = 0.06% (30Wat d = 0.5%).
The power delivered to the midrange and the

tweeter can be optimized in the design phase
taking in account the loudspeaker efficiency and
impedance(R

=4Ωto 8Ω).

L

It is quite common that midrange and tweeter
speakers have an efficiency 3dB higher than­woofers.

9/15

TDA2030A

Figure20 : 3 Way60W ActiveLoudspeakerSystem(VS=36V)

10/15

TDA2030A

MUSICALINSTRUMENTS AMPLIFIERS

Another important field of application for active
systemsis music.
In this area the use of several medium power
amplifiers is more convenient than a single high
poweramplifier, and it isalso morerealiable.
A typical example (see Figure 21) consist of four
amplifiers each driving a low-cost, 12 inch loud­speaker. This application can supply 80 to

RMS

.

160W
Figure21 : HighPower Active Box

for Musical Instrument

TRANSIENT INTERMODULATION DISTOR­TION (TIM)

Transientintermodulation distortion is an unfortu­nate phenomen associated with negative-feed­back amplifiers. When a feedback amplifier
receives an input signal which rises very steeply,
i.e.containshigh-frequencycomponents,the feed­back can arrive too late so that the amplifiers
overloadsanda burst of intermodulationdistortion
will be produced as in Figure22. Sincetransients
occur frequently in musicthis obviouslya problem
for the designer of audio amplifiers.Unfortunately,
heavy negative feedbackis frequencyused to re­duce the total harmonic distortion of an amplifier,
which tends to aggravate the transientintermodu­lation (TIM situation. The best known method for
the measurement of TIM consists of feeding sine
waves superimposed onto square waves, into the
amplifier under test. The outputspectrum is then
examined using a spectrum analyser and com­paredto theinput.Thismethodsuffersfromserious
disadvantages: the accuracy islimited, the meas­urement is a ratherdelicate operation and an ex­pensive spectrum analyser is essential. A new
approach (see Technical Note 143) applied by
SGS-THOMSONtomonolithicamplifiersmeasure­mentis fast cheap-itrequiresnothingmoresophis­ticatedthanan oscilloscope- and sensitive - and it

can be useddownto the valuesas low as 0.002%
in highpower amplifiers.

Figure 22 : OvershootPhenomenonin Feedback

Amplifiers

The ”inverting-sawtooh” method of measurement
isbasedon theresponseofanamplifier to a 20kHz
sawtoothwaveform.The amplifierhas no difficulty
followingthe slow ramp but itcannotfollowthefast
edge. The output will follow the upper line in Fig­ure 23cutting ofthe shadedarea and thusincreas­ing themeanlevel. If this outputsignal isfilteredto
removethesawtooth,directvoltageremainswhich
indicates the amountof TIMdistortion, although it
is difficult to measure because it is indistinguish­able fromthe DC offset of the amplifier. Thisprob­lem is neatly avoided in the IS-TIM method by
periodically inverting the sawtooth waveformat a
low audiofrequencyas shown in Figure24.

Figure 23 : 20kHz SawtoothWaveform

Figure 24 : Inverting SawtoothWaveform

11/15

TDA2030A

In the case of the sawtooth in Figure25 the mean
level was increased by the TIM distortion, for a
sawtoothin the otherdirectionthe oppositeis true.

The result is an AC signal at the output whole
peak-to-peakvalue is the TIM voltage, which can
be measured easily with an oscilloscope. If the
peak-to-peakvalue of the signal and the peak-to­peak of the invertingsawtooth are measured, the
TIMcan be found verysimply from:

V

OUT

TIM=

V

sawtooth

⋅ 100

In Figure25 the experimentalresults are shownfor
the 30Wamplifierusing the TDA2030Aas adriver
and a low-cost complementarypair. A simple RC
filter on the input of the amplifier to limit the maxi­mumsignalslope(SS)isaneffectivewaytoreduce
TIM.

Figure25 : TIMDistortion versus Output Power

Figure 26 : TIM DesignDiagram (f

= 30kHz)

C

POWERSUPPLY

Usingmonolithicaudioamplifierwithnon-regulated
supply voltage it is importantto designthe power
supply correctly. In any working case it must pro­videa supply voltageless than themaximumvalue
fixed by the IC break-downvoltage.

It is essential to take into account all the working
conditions,inparticularmainsfluctuationsand sup­ply voltage variations with and without load. The
TDA2030A(V

=44V) isparticularlysuitablefor

Smax

substitution of the standard IC power amplifiers
(with V

= 36V) for more reliable applications.

S max

An example, using a simple full-wave rectifier fol­lowed by a capacitor filter, is shown in the table 1
and in the diagramof Figure27.

The diagram of Figure 26 originated by SGS­THOMSONcanbeused to findthe Slew-Rate(SR)
requiredfor a givenoutput poweror voltageand a
TIMdesign target.
For example if an anti-TIM filter with a cutoff at
30kHz is used and the max. peak-to-peak output
voltage is 20V then, referring to the diagram, a

Slew-Rateof 6V/µs is necessaryfor 0.1%TIM.
As shown Slew-Rates of above 10V/µs do not
contributeto a furtherreductionin TIM.
Slew-Ratesof 100/µs arenotonlyuselessbutalso
a disadvantage in Hi-Fi audio amplifiers because
they tend to turnthe amplifierinto a radioreceiver.

12/15

Figure27 : DCCharacteristicsof

50W Non-regulated Supply

TDA2030A

Table 1

Mains
(220V)

+ 20% 28.8V 43.2V 42V 37.5V
+ 15% 27.6V 41.4V 40.3V 35.8V
+ 10% 26.4V 39.6V 38.5V 34.2V

– 10% 21.6V 32.4V 31.5V 27.8V
– 15% 20.4V 30.6V 29.8V 26V
– 20% 19.2V 28.8V 28V 24.3V

Secondary

Voltage

– 24V 36.2V 35V 31V

DC OutputVoltage (V

I

=0 Io= 0.1A Io=1A

o

)

o

Aregulatedsupplyisnot usuallyusedfor thepower
outputstagesbecauseof its dimensioningmust be
donetakingintoaccountthe power tosupplyinthe
signal peaks.They are only a smallpercentage of
the total music signal, with consequently large
overdimensioningof the circuit.

Evenifwitha regulatedsupplyhigheroutputpower
canbeobtained(V

isconstantin allworkingcondi-

S

tions), the additionalcostand power dissipationdo
notusuallyjustify its use. Usingnon-regulatedsup­plies, there are fewer designe restriction. In fact,
when signal peaks are present, the capacitorfilter
actsasa flywheelsupplyingthe requiredenergy.

In average conditions, the continuouspower sup­pliedis lower. The music power/continuouspower
ratio is greater in this case than for the case of
regulated supplied, with space saving and cost
reduction.

APPLICATION SUGGESTION

The recommendedvalues of the componentsare
those shown on application circuit of Figure 14.
Differentvaluescan be used.The Table2 canhelp
the designer.

SHORT CIRCUIT PROTECTION

The TDA2030Ahas an original circuit which limits
the current of the output transistors. This function
can be considered as being peak power limiting
rather than simple current limiting. It reduces the
possibilitythat the device gets damaged duringan
accidentalshort circuitfrom AC output to ground.

THERMALSHUT-DOWN

The presenceof a thermallimiting circuitoffersthe
followingadvantages:

1. An overload on the output (even if it is
permanent), or an above limit ambient
temperaturecan beeasilysupported since the
T

cannotbe higher than150oC.

j

2. The heatsink can have a smaller factor of
safety compared with that of a conventional
circuit.Thereisnopossibility ofdevicedamage
due to high junction temperature. If for any
reason, the junctiontemperatureincreasesup
to 150

o

C, the thermal shut-down simply
reduces the power dissipation and the current
consumption.

Table 2

Comp.

R1
R2
R3
R4

R5

C1

C2

C3, C4
C5, C6

C7
C8

D1, D2 1N4001 To protect the device against output voltage spikes

(*) The value of closed loop gain must behigher than 24dB.

Recom.

Value

22kΩ Closed loop gain setting Increase of gain Decrease of gain

680Ω Closed loop gain setting Decrease of gain (*) Increase of gain

22kΩ Non inverting input biasing Increase of input impedance Decrease of input impedance

1Ω Frequency Stability Danger of oscillation at high

≅ 3R2

1µF

22µF

0.1µF

100µF

0.22µF

≈

2

πBR1

Upper Frequency Cut-off Poor High Frequencies

Input DC Decoupling Increase of low frequencies

Inverting DC Decoupling Increase of low frequencies
Supply Voltage Bypass Danger of Oscillation

Supply Voltage Bypass Danger of Oscillation
Frequency Stability Larger Bandwidth

1

Upper Frequency Cut-off Smaller Bandwidth Larger Bandwidth

Purpose

frequencies with inductive
loads

Attenuation

Larger than

Recommended Value

Smaller than

Recommended Value

Danger of Oscillation

cut-off

cut-off

13/15

TDA2030A

PENTAWATT PACKAGE MECHANICAL DATA

DIM.

MIN. TYP. MAX. MIN. TYP. MAX.

mm inch

A 4.8 0.189
C 1.37 0.054
D 2.4 2.8 0.094 0.110

D1 1.2 1.35 0.047 0.053

E 0.35 0.55 0.014 0.022

F 0.8 1.05 0.031 0.041

F1 1 1.4 0.039 0.055

G 3.4 0.126 0.134 0.142

G1 6.8 0.260 0.268 0.276
H2 10.4 0.409
H3 10.05 10.4 0.396 0.409

L 17.85 0.703

L1 15.75 0.620
L2 21.4 0.843
L3 22.5 0.886
L5 2.6 3 0.102 0.118
L6 15.1 15.8 0.594 0.622
L7 6 6.6 0.236 0.260

M 4.5 0.177

M1 4 0.157

Dia 3.65 3.85 0.144 0.152

A

H3

L

L1

C

D1

L5

Dia.

L7

L6

L2
L3

D

F1

H2

E

MM1

G1

G

F

14/15

TDA2030A

Information furnishedis believed to be accurate and reliable. However, SGS-THOMSON Microelectronics assumes no responsibility for the
consequences of use of such information nor for any infringementof patents or other rights of thirdparties which may result from its use. No
license is granted by implication or otherwise under any patentor patent rights of SGS-THOMSON Microelectronics. Specifications mentioned
in this publication are subject to change without notice. This publication supersedes and replaces all information previously supplied.
SGS-THOMSON Microelectronics products are notauthorized for useas critical components inlife supportdevices or systems withoutexpress
written approval of SGS-THOMSON Microelectronics.

 1995 SGS-THOMSON Microelectronics - All Rights Reserved

PENTAWATTis a RegisteredTrademark of SGS-THOMSON Microelectronics

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SGS-THOMSON Microelectronics GROUP OF COMPANIES

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