Single-chip Type with Built-in FET Switching Regulators
Flexible Step-down
Switching Regulator
with Built-in Power MOSFET
BD9673EFJ
●Description
Output 1.5A and below High Efficiency Rate Step-down Switching Regulator Power MOSFET Internal Type BD9673EFJ
mainly used as secondary side Power supply, for example from fixed Power supply of 12V, 24V etc, Step-down Output of
1.2V/1.8V/3.3V/5V, etc, can be produced. This IC has external Coil/Capacitor down-sizing through 300 kHz Frequency
operation, inside Nch-FET SW for 45V “withstand-pressure” commutation and also, high speed load response through
Current Mode Control is a simple external setting phase compensation system, through a wide range external constant, a
compact Power supply can be produced easily.
●Features
1) Internal 200 mΩ Nch MOSFET
2) Output Current 1.5A
3) Oscillation Frequency 300kHz
4) Synchronizes to External Clock ( 200kHz~500kHz )
5) Feedback Voltage 1.0V±1.0%
6) Internal Soft Start Function
7) Internal Over Current Protect Circuit, Low Input Error Prevention Circuit, Heat Protect Circuit
8) ON/OFF Control through EN Pin (Standby Current 0 A Typ.)
9) Package: HTSOP-J8 Package
●Applications
For Household machines in general that have 12V/24V Lines, etc.
●Absolute Maximum Rating
Parameter SymbolRatings Unit
No.12027ECT57
VCC-GND Supply Voltage
BST-GND Voltage
BST-Lx Voltage
EN-GND Voltage
Lx-GND Voltage
FB-GND Voltage
VC-GND Voltage
SYNC-GND Voltage
High-side FET Drain Current
Power Dissipation
Operating Temperature
Storage Temperature
Junction Temperature
(*1)During mounting of 70×70×1.6t mm 4layer board (Copper area:70mm×70mm).Reduce by 30.08mW for every 1℃ increase. (Above 25℃)
●Operating Conditions (Ta=25℃)
Parameter Symbol
Power Supply Voltage VCC 7 - 42 V
Output Voltage VOUT 1.0
1. Reference
This block generates Error Amp standard voltage.
Standard voltage is 1.0V.
2. REG
This is a Gate Drive Voltage Generator and 5V Low saturation regulator for internal circuit power supply.
3. OSC
This is a precise wave oscillation circuit with operation frequency fixed to 300 kHz fixed (self-running mode).
To implement the synchronization feature connect a square wave (Hi Level: higher than 2V, Low Level: lower than
0.8V )to the SYNC pin. The synchronization frequency range is 200 kHz to 500 kHz. After connecting the rising edge of
LX will be synchronized to the falling edge of SYNC pin signal after 3 counts. At the synchronization remove the
external clock, the device transitions self-running mode after 7 microseconds.
4. Soft Start
A circuit that does soft start to the output voltage of DC/DC comparator, and prevents rush current during start-up.
Soft start time is set at IC internal, after 10 ms from starting-up EN pin, standard voltage comes to 1.0V, and output
voltage becomes set voltage.
5. ERROR AMP
This is an Error amplifier what detects output signal, and outputs PWM control signal.
Internal Standard Voltage is set to 1.0V.
Also, C and R are connected between the output (VC) pin GND of Error Amp as Phase compensation elements.
(See p.11)
6. ICOMP
This is a Voltage-Pulse Width Converter that controls output voltage in response to input voltage.
This compares the Voltage added to the internal SLOPE waveform in response to the FET WS current with Error
amplifier output voltage, controls the width of output Pulse and outputs to driver.
7. Nch FET SW
This is an internal commutation SW that converts Coil Current of DC/DC Comparator.
It contains 45V” with stand pressure” 200mΩ SW.
Because the Current Rating of this FET is 2.0A included ripple current, please use at within 2.0A.
The device has the circuit of over current protection for protecting the FET from over current.
To detect OCP 2 times sequentially, the device will stop and after 13msec restart.
8. UVLO
This is a Low Voltage Error Prevention Circuit.
This prevents internal circuit error during increase of power supply voltage and during decline of power suppl y voltage.
It monitors VCC pin voltage and internal REG voltage, and when VCC voltage becomes 6.4V and below, it turns off all
output FET and turns off DC/DC comparator output and soft start circuit resets.
Now this threshold has hysteresis of 200mV.
9. TSD
This is a Heat Protect (Temperature Protect) Circuit.
When it detects an abnormal temperature exceeding Maximum Junction Temperature (Tj=150℃), it turns off all output
FET, and turns off DC/DC comparator output. When Temperature falls, it has/with hysteresis and automatically returns.
10. EN
With the Voltage applied to EN Pin (6pin), IC ON/OFF can be controlled.
When a Voltage of 2.0V or more is applied, it turns on, at open or 0V application, it turns off.
About 550 kΩ pull-down resistance is contained within the pin.
The SYNC pin can be used to synchronize the regulator to an exter nal system clock. To implement the synchronization
feature connect a square wave to SYNC pin. The square wave am plitude must transition lo wer than 0.8V and higher than
2.0V on the SYNC pin and have an on time greater than 100 ns and an off time greater than 100 ns. The synchronization
frequency range is 200 kHz to 500 kHz. The rising edge of the LX will be synchronized to the falling edge of SYNC pin
signal after SYNC input pulse 3 count. At the synchronization, the external clock is removed, the device transitions
self-running mode after 7 microseconds. If the function of the synchronization is not used, please connect SYNC pin to
ground.
SYNC
SYNC_LATCH
Set the latch for
synchronization
400nsec
Lx
about
7µsec
Fig.3 Timing chart at Synchronization
◇SOFT START
The soft start time of BD9763EFJ is determined by the DCDC operating frequency (self-run mode 300 kHz ⇒10ms).
If synchronization is used at the time of EN=ON, The soft start time is restricted by SYNC pin input pulse frequency.
SYNC pin input pulse frequency is fosc_ex kHz, the soft start time is expressed by below equation.
Tss = × 10 [ms]
300
fosc_ex
◇The case of not using the function of synchronization
Although the SYNC pin is pulled down by resistor in this
device, if the function of the synchronization is not used
, it is recommended to connect SYNC pin to ground.
Fig.4 the method to disposal the SYNC pin without synchronization
The device has the circuit of over current protection for protecting the FET from over current.
To detect OCP 2 times sequentially, the device will stop and after 13msec restart.
Layout is a critical portion of good power supply design. There are several signals paths that conduct fast changing currents
or voltages that can interact with stray inductance or parasitic capacitance to generate noise or degrade the power supplies
performance. To help eliminate these problems, the VCC pin should be bypassed to ground with a low ESR ceramic bypass
capacitor with B dielectric. Care should be taken to minimize the loop area formed by the bypass capacitor connections, the
VCC pin, and the anode of the catch diode. See Fig.28 for a PCB layout example. The GND pin should be tied directly to
the thermal pad under the IC and the thermal pad.
The thermal pad should be connected to any internal PCB ground planes using multiple VIAs directl y under the IC. The LX
pin should be routed to the cathode of the catch diode and to the output inductor. Since the LX connection is the switching
node, the catch diode and output inductor should be located close to the LX pins, and the area of the PCB conductor
minimized to prevent excessive capacitive coupling. For operation at full rated load, the top side ground area must provide
adequate heat dissipating area. The additional external components can be placed approximately as shown. It may be
possible to obtain acceptable performance with alternate PCB layouts; however this layout has be en shown to produce
good results and is meant as a guideline.
The following formulas show how to estimate the device power dissipation under continuous mode operations. They should
not be used if the device is working in the discontinuous conduction mode.
The device power dissipation includes:
1) Conduction loss: Pcon = IOUT
2) Switching loss: Psw = 1.25 × 10
3) Gate charge loss: Pgc = 22.8 × 10
4) Quiescent current loss: Pq = 1.0 × 10–3 × VCC
Where:
IOUT is the output current (A), RonH is the on-resistance of the high-side MOSFET(Ω), VOUT is the output voltage (V).
VCC is the input voltage (V), fsw is the switching frequency (Hz).
Therefore
Power dissipation of IC is the sum of above dissipation.
Pd = Pcon + Psw + Pgc + Pq
For given Tj, Tj =Ta + θja × Pd
Where:
Pd is the total device power dissipation (W), Ta is the ambient temperature (℃)
Tj is the junction temperature (℃), θjais the thermal resistance of the package (℃)
Something of the shield Type that Fulfills the Current Rating (Current value Ipeak below), with low DCR (Direct Current
Resistance element) is recommended.
Value of Inductor influences Inductor Ripple Current and becomes the cause of Output Ripple.
In the same way as the formula below, this Ripple Current can be made small for as big as the L value of Coil or as
high as the Switching Frequency.
For design value of Inductor Ripple Current, please carry out design tentatively with about 20%~50% of Maximum
Input Current.
※When current that exceeds Coil rating flows to the coil, the Coil causes a Magnetic Sat uration, and there are cases
wherein a decline in efficiency, oscillation of output happens. Please have sufficient margin and select so that Peak
Current does not exceed Rating Current of Coil.
(2) Output Capacitor
In order for capacitor to be used in output to reduce output ripple, Low ceramic capacitor of ESR is recommended.
Also, for capacitor rating, on top of putting into consideration DC Bias characteristics, please use something whose
maximum rating has sufficient margin with respect to the Output Voltage. Output ripple voltage is looked for using the
following formula. The actual value of the output capacitor is not critical, but some pr actical limits do exist. Consider th e
relationship between the crossover frequency of the design and LC corner frequency of the output filter. In gener al, it is
desirable to keep the crossover frequency at less than 1/5 of the switching frequency. With high switching frequenci es
such as the 600kHz frequency of this design, internal circuit limitations of the BD9675FJ limit the practical maximum
crossover frequency to about 30kHz. In general, the crossover freq uency should be higher than the corner frequency
determined by the load impedance and the output capacitor. This limits the minimum capacitor value for the output filter
to:
C
Where: Rl is the output load resistance and fc_max is the maximum crossover frequency. The output ripple voltage can
be estimated by:
.
Please design in a way that it is held within Capacity Ripple Voltage.
(3) Output Voltage Setting
ERROR AMP internal Standard Voltage is 1.0V. Output Voltage is determined as seen in (4) formula.
(4) Bootstrap Capacitor
Please connect from 4700pF to 22000pF (Laminate Ceramic Capacitor) between BST Pin and Lx Pin.
The BD9673EFJ is designed to operate using an externa l catch diode between Lx and GND. T he selected diode must
meet the absolute maximum ratings for the application: Reverse voltage must be higher t han the maximum voltage at
the Lx pin, which is VCCMAX + 0.5 V. Peak current must be greater than IOUTMAX plus on half the peak to peak
inductor current.
(6) Input Capacitor
The BD9673EFJ requires an input capacitor and depending on the application. Use low ESR capacitors for the best
performance. Ceramic capacitors are preferred, but low-ESR electrolytic capacitors may also suffice. The typical
recommended value for the decoupling capacitor is 10uF. Please place this capacitor as possible as close to the VCC
pin. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to
prevent excessive voltage ripple at input. The input voltage ripple caused by capacitance can be estimated by:
Since the input capacitor (CVCC) absorbs the input switching current it requires an adequate ripple current rating. The
RMS current in the input capacitor can be estimated by:
The worst case condition occurs at VCC = 2VOUT, where
(7) About Adjustment of DC/DC Comparator Frequency Characteristics
Role of Phase compensation element C1,C2,R3 (See P.7. Example of Reference Application Circuit)
Stability and Responsiveness of Loop are controlled through VC Pin which is the output of Error Amp.
The combination of zero and pole that determines Stability and Responsiveness is adjusted by the combination of
resistor and capacitor that are connected in series to the VC Pin.
DC Gain of Voltage Return Loop can be calculated for using the following formula.
Here, VFB is Feedback Voltage (1.0V).AEA is Voltage Gain of Error amplifier (typ: 77dB),
Gcs is the Trans-conductance of Current Detect (typ: 10A/V), and Rl is the Output Load Resistance value.
There are 2 important poles in the Control Loop of this DC/DC.
The first occurs with/ through the output resistance of Phase compensation Capacitor (C1) and Error amplifier.
The other one occurs with/through the Output Capacitor and Load Resistor.
These poles appear in the frequency written below.
Here, G
Here, in this Control Loop, one zero becomes important. With the zero which occurs because of Phase compensation
Capacitor C1 and Phase compensation Resistor R3, the Frequency below appears.
Also, if Output Capacitor is big, and that ESR (RESR) is big, in this Control Loop, there are cases when it has an
important, separate zero (ESR zero).
This ESR zero occurs due to ESR of Output Capacitor and Capacitance, and exists in the Frequency below.
(ESR zero)
VCC
CVCC
I
CVCC_max
is the trans-conductance of Error amplifier (typ: 220 µA/V).
In this case, the 3rd pole determined with the 2nd Phase compensation Capacitor (C2) and Phase Correction Resistor
(R3) is used in order to correct the ESR zero results in Loop Gain.
This pole exists in the frequency shown below.
(Pole that corrects ESR zero)
The target of Phase compensation design is to create a communication function in order to acquire necessary band
and Phase margin.
Cross-over Frequency (band) at which Loop gain of Return Loop becomes “0” is important.
When Cross-over Frequency becomes low, Power supply Fluctuation Response, Load Response, etc worsens.
On the other hand, when Cross-over Frequency is too high, instability of the Loop can occur.
Tentatively, Cross-over Frequency is targeted to be made 1/20 or below of Switching Frequency.
Selection method of Phase Compensation constant is shown below.
1. Phase Compensation Resistor (R3) is selected in order to set to the desired Cross-over Frequency.
Calculation of RC is done using the formula below.
Here, fc is the desired Cross-over Frequency. It is made about 1/20 and below of the Normal Sw itching Frequency (fs).
2. Phase compensation Capacitor (C1) is selected in order to achieve the desired phase margin.
In an application that has a representative Inductance value (about several µH~20µH), by matching zero of
compensation to 1/4 and below of the Cross-over Frequency, sufficient Phase margin can be acquired. C1 can be
calculated using the following formula.
RC is Phase compensation Resistor.
3. Examination whether the second Phase compensation Capacitor C2 is necessary or not is done.
If the ESR zero of Output Capacitor exists in a place that is smaller than half of the Switching Frequency, a second
Phase compensation Capacitor is necessary. In other words, it is the case wherein the formula below happens.
In this case, add the second Phase compensation Capacitor C2, and match the frequency of the third pole to the
Frequency fp3 of ESR zero.
When the absolute maximum ratings of application voltage, operating temperature range, etc. was exceeded, there is
possibility of deterioration and destruction. Also, the short Mode or open mode, etc. destruction condition cannot be
assumed. When the special mode where absolute maximum rating is exceeded is assumed, pleas e give consideration
to the physical safety countermeasure for the fuse, etc.
(2) About GND Electric Potential
In every state, please make the electr ic pot en tia l of GND Pi n into the minimum electrical potenti al. Also, i nclud e t he act u a l
excessive effect, and please do it such that the pins, excluding the GND Pin do not become the voltage below GND.
(3) About Heat Design
Consider the Power Dissipation (Pd) in actual state of use, and please make Heat Design with sufficient margin.
(4) About short circuit between pins and erroneous mounting
When installing to set board, please be mindful of the direction of the IC, phase difference, etc. If it is not installed
correctly, there is a chance that the IC will be destroyed. Also, if a foreign object enters the middle of output, the middle
of output and power supply GND, etc., even for the case where it is shorted, there is a change of destruction.
(5) About the operation inside a strong electro-magnetic field
When using inside a strong electro-magnetic field, there is a possibility of error, so please be careful.
(6) Temperature Protect Circuit (TSD Circuit)
Temperature Protect Circuit (TSD Circuit) is built-in in this IC. As for the Tem perature Protect Circuit (TSD Circuit),
because it a circuit that aims to block the IC from insistent careless runs, it is not aimed for protection and guarantee of
IC. Therefore, please do not assume the continuing use after operation of this circuit and the Temperature Protect
Circuit operation.
(7) About checking with Set boards
When doing examination with the set board, during connection of capacitor to the pin that has lo w impedance, there is
a possibility of stress in the IC, so for every 1 process, please make sure to do electric discharge. As a countermeasure
for static electricity, in the process of assembly, do grounding, and when transporting or storing please be careful. Also,
when doing connection to the jig in the examination process, please make sure to turn off the power supply, then
connect. After that, turn off the power supply then take it off.
(8) About common impedance
For the power supply and the wire of GND, lower the common impedance, then, as much as possible, make the ripple
smaller (as much as possible make the wire thick and short, and lower the ripple from L・C), etc., then and please
consider it sufficiently.
(9) In the application, when the mode where the VCC and each pin electrical potenti al becomes reversed exists, there is a
possibility that the internal circuit will become damaged. For example, during cases wherein the condition when charge
was given in the external capacitor, and the VCC was shorted to GND, it is recommended to insert the bypass diode
to the diode of the back current prevention in the VCC series or the middle of each Pin-VCC.
(10) About High-sid e Nch F ET
Please use within 2.0A contained ripple current, because the absolute maximum rating of high-side Nch FET is 2.0A.
(11) About over curr ent detection
The detecting current is the current flowing through high-side NchFET. Output current containing ripple current,
therefore the detecting current is the current of the output current containing ripple current
This IC is a Monolithic IC, and between each element, it has P+ isolation for element separation and P board. With the
N layer of each element and this, the P-N junction is formed, and the parasitic element of each type is composed.
For example, like the diagram below, when resistor and transistor is connected to Pin,
○When GND>(PinA) in Resistor, when GND>(PinA), when GND>(Pin B) in Transistor (NPN),
the P-N junction will operate as a parasitic diode.
○Also, during GND>(Pin B) in the Transistor (NPN), through the N layer of the other elements connected
to the above-mentioned parasitic diode , the parasitic NPN Transistor will operation.
On the composition of IC, depending on the electrical potential, the parasitic element will become necessary. Through
the operation of the parasitic element interference of circuit operation will arouse, and error, therefore destruction can
be caused. Therefore please be careful about the applying of voltage lower than the GND (P board) in I/O Pin, and the
way of using when parasitic element operating.
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