Rainbow Electronics MAX8668 User Manual

General Description

The MAX8667/MAX8668 dual step-down converters
with dual low-dropout (LDO) linear regulators are
intended to power low-voltage microprocessors or
DSPs in portable devices. They feature high efficiency
with small external component size. The step-down
converters are adjustable from 0.6V to 3.3V (MAX8668)
or factory preset (MAX8667) with guaranteed output
current of 600mA for OUT1 and 1200mA for OUT2. The

1.5MHz hysteretic-PWM control scheme allows for tiny
external components and reduces no-load operating
current to 100µA with all outputs enabled. Dual low-qui­escent-current, low-noise LDOs operate down to 1.7V
supply voltage. The MAX8667/MAX8668 have individ­ual enables for each output, maximizing flexibility.

The MAX8667/MAX8668 are available in the space­saving, 3mm x 3mm, 16-pin thin QFN package.

Applications

Cell Phones/Smartphones

PDA and Palmtop Computers

Portable MP3 and DVD Players

Digital Cameras, Camcorders

PCMCIA Cards

Handheld Instruments

Features

♦ Tiny, Thin QFN 3mm x 3mm Package
♦ Individual Enables
♦ Step-Down Converters

600mA Guaranteed Output Current on OUT1
1200mA Guaranteed Output Current on OUT2
Tiny Size 2.2µH Chip Inductor (0805)
Output Voltage from 0.6V to 3.3V (MAX8668)
Ultra-Fast Line and Load Transients
Low 25µA Supply Current Each

♦ LDOs

300mA Guaranteed
Low 1.7V Minimum Supply Voltage
Low Output Noise

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

________________________________________________________________

Maxim Integrated Products

1

Pin Configuration

IN34

LX2

LX1

OUT2

OUT1

2.6V TO 5.5V

OUT3

OUT4

REF

GND

IN12

300mA

300mA

EN1

EN2

EN3

EN4

600mA

1.2A

PGND1 PGND2

10μF 4.7μF

4.7μF

4.7μF

0.01μF

2.2μH

2.2μH

2.2μF

2.2μF

MAX8667

Typical Operating Circuit

19-0784; Rev 0; 4/07

For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at
1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com.

Ordering Information continued at the end of data sheet.

Selector Guide appears at the end of data sheet.

Ordering Information

Note: All MAX8667/MAX8668 parts are in a 16-pin, thin QFN,
3mm x 3mm package and operate in the -40°C to +85°C
extended temperature range.

+

Denotes a lead-free package.

PART PKG CODE TOP MARK

T1633-4 AEQ

T1633-4 AFI

T1633-4 AFM

T1633-4 AFN

MAX8667ETEAA+

MAX8667ETEAB+

MAX8667ETEAC+

MAX8667ETECQ+

TOP VIEW

13

PGND1

EN1

EN2

14

15

16

OUT1 (FB1)

( ) ARE FOR THE MAX8668

LX2

IN34

PGND2

8

7

6

5

4

OUT4

LX1

12 10 9

11

MAX8667
MAX8668

13

2

EN3

OUT3 IN12

THIN QFN

(3mm x 3mm)

OUT2 (FB2)

REF

GND

EN4

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

2 _______________________________________________________________________________________

ABSOLUTE MAXIMUM RATINGS

ELECTRICAL CHARACTERISTICS

(V

IN34

= V

IN12

= 3.6V, TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA= +25°C.) (Note 1)

Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.

IN12, IN34, FB1, FB2, EN1, EN2, EN3, EN4, OUT1,

OUT2, REF to GND............................................-0.3V to +6.0V

OUT3,

OUT4 to GND.....-0.3V to the lesser of + 6V or (V

IN34

+ 0.3V)

PGND1, PGND2 to GND .......................................-0.3V to +0.3V

LX1, LX2 Current ..........................................................1.5A RMS

LX1, LX2 to GND (Note 1) .......................-0.3V to (V

IN12

+ 0.3V)

Continuous Power Dissipation (TA= +70°C)

16-Pin, 3mm x 3mm Thin QFN

(derate 20.8mW/°C above +70°C).............................1667mW

Operating Temperature Range ...........................-40°C to +85°C

Junction Temperature..................................................... +150°C

Storage Temperature Range .............................-65°C to +150°C

Lead Temperature (soldering, 10s) .................................+300°C

Note 1: LX_ has internal clamp diodes to GND and IN12. Applications that forward bias these diodes should take care not to exceed

the IC’s package-dissipation limits.

IN34 Supply Range V

IN12 Supply Range MAX8668, V

IN12 Suppy Range MAX8667, V

Shutdown Supply Current,
I

IN12

No Load Supply Current,
I

IN12

UNDERVOLTAGE LOCKOUT

IN12 UVLO

IN34 UVLO

THERMAL SHUTDOWN

Threshold TA rising +160 °C

Hysteresis 15 °C

REFERENCE

Reference Bypass Output
Voltage

REF Supply Rejection 2.6V ≤ (V

LOGIC AND CONTROL INPUTS

EN_ Input Low Level

EN_ Input High Level

EN_ Input Leakage Current V

STEP-DOWN CONVERTERS

Minimum Adjustable Output
Voltage

PARAMETER CONDITIONS MIN TYP MAX UNITS

≥ V

IN12

IN34

≥ V

IN12

IN34

≥ V

IN12

IN34

V

+ I

+ I

IN34

IN34

= V

IN12

MAX8667ETEJS+, all regulators enabled 100 150 µA

V

rising 2.4 2.5 2.6 V

IN12

V

hysteresis 0.1 V

IN12

V

rising 1.5 1.6 1.7 V

IN34

V

hysteresis 0.1 V

IN34

1.7V ≤ V

2.6V ≤ V

1.7V ≤ V

2.6V ≤ V

= V

IN12

MAX8668 0.6 V

IN34

IN12

IN34

IN12

IN34

IN12

IN34

= 4.2V V

= V

≤ 5.5V
≤ 5.5V

≤ 5.5V
≤ 5.5V

= 5.5V

) ≤ 5.5V 0.15 mV/V

IN34

1.7 5.5 V

2.6 5.5 V

2.8 5.5 V

EN_

= 0V

TA = +25°C 1 µA

T

= +85°C 0.05 µA

A

0.591 0.600 0.609 V

1.44 V

TA = +25°C -1 +1

T

= +85°C 0.001

A

0.4 V

µA

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

_______________________________________________________________________________________ 3

Note 1: All devices are 100% production tested at TA= +25°C. Limits over the operating temperature range are guaranteed by design.

ELECTRICAL CHARACTERISTICS (continued)

(V

IN34

= V

IN12

= 3.6V, TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA= +25°C.) (Note 1)

Maximum Adjustable Output
Voltage

FB1, FB2 Regulation Voltage

OUT1, OUT2 Regulation Voltage

FB1, FB2 Line Regulation MAX8668, V

OUT1, OUT2 Line Regulation MAX8667, V

FB1, FB2 Bias Current

OUT1 Current Limit

OUT2 Current Limit

OUT1 On-Resistance

OUT2 On-Resistance

Rectifier-Off Current Threshold
(I

LXOFF

LX Leakage Current LX_ = 5.5V

Minimum On-Time 100 ns

Minimum Off-Time 50 ns

LDO REGULATORS

Supply Current Each LDO 20 µA

Output-Voltage Accuracy

Line Regulation V

Dropout Voltage V

Current Limit V

Soft-Start Ramp Time To 90% of final value 0.1 ms

Output Noise 100Hz to 100kHz, 30mA load, V

Power-Supply Rejection Ratio f < 1kHz, 30mA load 57 dB

Shutdown Output Resistance 1kΩ

TIMING (See Figure 2)

Power-On Time (t

Enable Time (tEN)

PARAMETER CONDITIONS MIN TYP MAX UNITS

MAX8668 3.3 V

MAX8668, no load,
V

falling

FB_

MAX8667ETEJS+, no load, V
falling

= 2.6V to 5.5V 0.01 %/V

IN12

= 2.8V to 5.5V 0.05 %/V

IN12

MAX8668, shutdown mode 0.1

MAX8668, V

pMOSFET switch (I

nMOSFET rectifier (valley current) 500 750 1000

pMOSFET switch (I

nMOSFET rectifier (valley current) 1200 1500 1800

pMOSFET switch, I

nMOSFET rectifier, I

pMOSFET switch, I

nMOSFET rectifier, I

)

1mA load, TA = +25°C -1.5 +1.5

1mA to 300mA load -3.0 +3.0

= 3.6V to 5.5V, 1mA load 0.003 %/V

IN34

= 1.8V, 300mA load 130 250 mV

IN34

, V

OUT3

PWRON

)

OUT1, OUT2 25

OUT3, OUT4 45

OUT1, OUT2 15

OUT3, OUT4 35

= 0.5V 0.01

FB1

) 700 900 1100

LIMP1

) 1333 1667 2000

LIMP2

= -400mA 0.3 0.6

LX1

= 400mA 0.3 0.6

LX1

= -400mA 0.12 0.27

LX2

= 400mA 0.12 0.27

LX2

90% of nominal value 375 420 465 mA

OUT4

TA = +25°C 0.588 0.600 0.612

T

= -40°C to +85°C 0.582 0.600 0.618

A

TA = +25°C 1.274 1.300 1.326

OUT_

T

= -40°C to +85°C 1.261 1.300 1.339

A

TA = +25°C -1 +1

T

= +85°C 0.1

A

OUT3

and V

= 2.8V 75 µV

OUT4

60 120 mA

V

V

µA

mA

mA

Ω

Ω

µA

%

RMS

µs

µs

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

4 _______________________________________________________________________________________

Typical Operating Characteristics

(V

IN12

= V

IN34

= 3.6V, circuit of Figure 4, V

OUT1

= 1.2V, V

OUT2

= 1.8V, V

OUT3

= 2.8V, V

OUT4

= 2.8V, TA = +25°C, unless otherwise noted.)

OUT1 EFFICIENCY vs. LOAD CURRENT

(V

OUT1

= 1.2V)

MAX8667/88 toc01

LOAD CURRENT (mA)

EFFICIENCY (%)

101

10

20

30

40

50

60

70

80

90

0

0.1 1000100

ONLY OUT1 ENABLED

OUT2 EFFICIENCY vs. LOAD CURRENT

(V

OUT2

= 1.8V)

MAX8667/88 toc02

LOAD CURRENT (mA)

EFFICIENCY (%)

1000100101

10

20

30

40

50

60

70

80

90

0

0.1 10000

ONLY OUT2 ENABLED

0.80

0.90

0.85

1.05

1.00

0.95

1.20

1.15

1.10

1.25

0 200100 300 400 500 600

OUT1 LOAD REGULATION

MAX8667/88 toc03

LOAD CURRENT (mA)

OUTPUT VOLTAGE (V)

1.20

1.40

1.30

1.60

1.50

1.80

1.70

1.90

0 400 600200 800 1000 1200

OUT2 LOAD REGULATION

MAX8667/88 toc04

LOAD CURRENT (mA)

OUTPUT VOLTAGE (V)

1.00

1.05

1.10

1.15

1.20

1.25

1.30

1.35

1.40

2.5 3.53.0 4.0 4.5 5.0 5.5

OUT1 OUTPUT VOLTAGE

vs. INPUT VOLTAGE (600mA LOAD)

MAX8667/88 toc05

INPUT VOLTAGE (V)

OUTPUT VOLTAGE (V)

1.60

1.65

1.70

1.75

1.80

1.85

1.90

1.95

2.00

2.5 3.53.0 4.0 4.5 5.0 5.5

OUT2 OUTPUT VOLTAGE

vs. INPUT VOLTAGE (1200mA LOAD)

MAX8667/88 toc06

INPUT VOLTAGE (V)

OUTPUT VOLTAGE (V)

0

1000

500

2000

1500

3000

2500

3500

0 600 900300 1200 1500 1800

SWITCHING FREQUENCY

vs. LOAD CURRENT

MAX8667/88 toc07

LOAD CURRENT (mA)

SWITCHING FREQUENCY (kHz)

OUT2

OUT1

0

20

40

60

80

100

120

1.5 2.52.0 3.0 3.5 4.0 4.5 5.0 5.5

NO-LOAD SUPPLY CURRENT vs. SUPPLY

VOLTAGE ALL REGULATOR ENABLED

MAX8667/88 toc08

SUPPLY VOLTAGE (V)

SUPPLY CURRENT (μA)

SUPPLY VOLTAGE
RISING

SUPPLY VOLTAGE
FALLING

0

20

40

60

80

100

120

1.5 2.52.0 3.0 3.5 4.0 4.5 5.0 5.5

NO-LOAD SUPPLY CURRENT

vs. SUPPLY VOLTAGE OUT1 AND OUT2 ONLY

MAX8667/88 toc09

SUPPLY VOLTAGE (V)

SUPPLY CURRENT (μA)

SUPPLY VOLTAGE
RISING

SUPPLY VOLTAGE
FALLING

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

_______________________________________________________________________________________

5

Typical Operating Characteristics (continued)

(V

IN12

= V

IN34

= 3.6V, circuit of Figure 4, V

OUT1

= 1.2V, V

OUT2

= 1.8V, V

OUT3

= 2.8V, V

OUT4

= 2.8V, TA = +25°C, unless otherwise noted.)

10μs/div

OUT1 LOAD TRANSIENT

V

OUT1

I

OUT1

100mV/div
(AC-COUPLED)

200mA/div

200mA/div

MAX8667/88 toc16

I

L1

300mA

10mA

10mA

NO-LOAD SUPPLY CURRENT vs. SUPPLY

VOLTAGE OUT3 AND OUT4 ONLY

120

100

80

(μA)

IN34

I

V

VOLTAGE

IN34

60

FALLING

40

V

VOLTAGE

20

0

012345

IN34

RISING

SUPPLY VOLTAGE (V)

SUPPLY CURRENT vs. SUPPLY VOLTAGE

1000

900

800

700

600

500

400

300

SUPPLY CURRENT (mA)

200

100

0

2.5 3.53.0 4.0 4.5 5.0 5.5

V

= 5.5V

IN12

SUPPLY VOLTAGE (V)

3.00

2.95

2.90

MAX8667/88 toc10

2.85

2.80

2.75

2.70

OUTPUT VOLTAGE (V)

2.65

2.60

2.55

2.50

IN12 = IN34

2.4Ω LOAD ON OUT1

3.6Ω LOAD ON OUT2
NO LOAD ON OUT3
NO LOAD ON OUT4

OUT3 OUTPUT VOLTAGE

vs. INPUT VOLTAGE (300mA LOAD)

2.5 3.53.0 4.0 4.5 5.0 5.5
INPUT VOLTAGE (V)

EN1/EN2/

I

IN12

EN3/EN4

V

OUT1

V

OUT2

V

OUT3

V

OUT4

+ I

IN34

I

L1

I

L2

MAX8667/88 toc13

OUT3 DROPOUT VOLTAGE

vs. LOAD CURRENT

80

70

MAX8667/88 toc11

60

50

40

30

DROPOUT VOLTAGE (mV)

20

10

0

0 100 200 300

LOAD CURRENT (mA)

ENABLE WAVEFORMS

40

μs/div

MAX8667/88 toc14

5V/div

2V/div

2V/div
2V/div

2V/div

2A/div

2A/div
2A/div

MAX8667/88 toc12

SHUTDOWN WAVEFORMS

EN1/EN2/

EN3/EN4

V

OUT1

V

OUT2

V

OUT3

V

OUT4

40μs/div

MAX8667/88 toc15

5V/div

1V/div

1V/div

1V/div

1V/div

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

6 _______________________________________________________________________________________

Typical Operating Characteristics (continued)

(V

IN12

= V

IN34

= 3.6V, circuit of Figure 4, V

OUT1

= 1.2V, V

OUT2

= 1.8V, V

OUT3

= 2.8V, V

OUT4

= 2.8V, TA = +25°C, unless otherwise noted.)

OUT2 LOAD TRANSIENT

MAX8667/88 toc17

OUT3 LOAD TRANSIENT

MAX8667/88 toc18

V

OUT2

600mA

I

OUT2

I

L2

10μs/div

10mA10mA

V

OUT4

I

OUT4

OUT4 LOAD TRANSIENT

300mA

0mA

10μs/div

MAX8667/88 toc19

0mA

200mV/div
(AC-COUPLED)

500mA/div

500mA/div

50mV/div
(AC-COUPLED)

200mA/div

V

I

OUT3

OUT3

V

300mA

0mA

OUT1 LIGHT-LOAD SWITCHING

WAVEFORMS

OUT1

V

LX1

I

L1

500μA LOAD

10μs/div

10μs/div

0mA

MAX8667/88 toc20

50mV/div
(AC-COUPLED)

200mA/div

20mV/div

2V/div

100mA/div

V

OUT2 LIGHT-LOAD SWITCHING

WAVEFORMS

OUT2

V

LX2

I

L2

500μA LOAD

40μs/div

MAX8667/88 toc21

20mV/div

2V/div

500mA/div

V

OUT1 HEAVY-LOAD SWITCHING

WAVEFORMS

OUT1

V

LX1

I

L1

500μA LOAD

MAX8667/88 toc22

400ns/div

20mV/div

2V/div

500mA/div

MAX8667/MAX8668

Typical Operating Characteristics (continued)

(V

IN12

= V

IN34

= 3.6V, circuit of Figure 4, V

OUT1

= 1.2V, V

OUT2

= 1.8V, V

OUT3

= 2.8V, V

OUT4

= 2.8V, TA = +25°C, unless otherwise noted.)

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

_______________________________________________________________________________________

7

V

OUT2

V

LX2

I

L2

OUT2 HEAVY-LOAD SWITCHING

WAVEFORMS

500mA LOAD

400ns/div

OUT3 NOISE

MAX8667/88 toc23

MAX8667/88 toc25

20mV/div

2V/div

500mA/div

100μV/div

PSRR (dB)

POWER-SUPPLY REJECTION RATIO

vs. FREQUENCY

70

60

50

40

30

20

10

0

0.01 10.1 10 100 1000
FREQUENCY (kHz)

OUT4 NOISE

V
I

LOAD

C

OUT3

OUT3

= 2.80V

= 100Ω

= 4.7μF

MAX8667/88 toc26

MAX8667/88 toc24

100μV/div

V

1ms/div

I

OUT3

LOAD

= 2.80V

= 100Ω

1ms/div

V
I

LOAD

OUT4

= 3.30V

= 100Ω

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

8 _______________________________________________________________________________________

Pin Description

PIN

MAX8667 MAX8668

1 EN3 EN3

2 OUT3 OUT3

3 IN34 IN34

4 OUT4 OUT4

5 EN4 EN4

6 GND GND Ground

7 REF REF Reference Output. Bypass REF with a 0.01µF ceramic capacitor to GND.

8 OUT2 — Feedback Input for Regulator 2. Connect OUT2 directly to the output of step-down regulator 2.

9 PGND2 PGND2 Power Ground for Step-Down Regulator 2

10 LX2 LX2 Inductor Connection for Regulator 2

11 IN12 IN12

12 LX1 LX1 Inductor Connection for Regulator 1

13 PGND1 PGND1 Power Ground for Step-Down Regulator 1

14 OUT1 — Feed b ack Inp ut for Reg ul ator 1. C onnect OU T1 d i r ectl y to the outp ut of step - d ow n r eg ul ator 1.

15 EN1 EN1

16 EN2 EN2

— EP EP Exposed Paddle. Connect to GND, PGND1, PGND2, and circuit ground.

NAME

— FB2

— FB1

Enable Input for Regulator 3. Drive EN3 high or connect to IN34 to turn on regulator 3. Drive low
to turn off regulator 3 and reduce input quiescent current.

Output of Regulator 3. Bypass OUT3 with a 4.7µF ceramic capacitor to GND. OUT3 is
discharged to GND through an internal 1kΩ in shutdown.

Input Voltage for LDO Regulators 3 and 4. Supply voltage range is from 1.7V to 5.5V. This
supply voltage must not exceed V
to ground.

Output of Regulator 4. Bypass OUT4 with a 4.7µF ceramic capacitor to GND. OUT4 is
discharged to GND through an internal 1kΩ in shutdown.

Enable Input for Regulator 4. Drive EN4 high or connect to IN34 to turn on regulator 4. Drive low
to turn off regulator 4 and reduce input quiescent current.

Feedback Input for Regulator 2. Connect FB2 to the center of a resistor feedback divider
between the output of regulator 2 and ground to set the output voltage. See the Setting the
Output Voltages and Voltage Positioning section.

Input Voltage for Step-Down Regulators 1 and 2. Supply voltage range is from 2.6V to 5.5V. This
supply voltage must not be less than V
IN12 to ground.

Feedback Input for Regulator 1. Connect FB1 to the center of a resistor feedback divider
between the output of regulator 1 and ground to set the output voltage. See the Setting the
Output Voltages and Voltage Positioning section.

E nab l e Inp ut for Reg ul ator 1. D r i ve E N 1 hi g h or connect to IN 12 to tur n on step - d ow n r eg ul ator 1.
D r i ve l ow to tur n off the r eg ul ator and r ed uce i np ut q ui escent cur r ent.

E nab l e Inp ut for Reg ul ator 2. D r i ve E N 2 hi g h or connect to IN 12 to tur n on step - d ow n r eg ul ator 2.
D r i ve l ow to tur n off the r eg ul ator and r ed uce i np ut q ui escent cur r ent.

FUNCTION

. Connect a 4.7µF or larger ceramic capacitor from IN34

IN12

. Connect a 10µF or larger ceramic capacitor from

IN34

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

_______________________________________________________________________________________ 9

Figure 1. Functional Diagram

REF

GND

IN34

1.7V TO 5.5V

UVLO

EN

REF AND BIAS

IN

EN

IN

REF

EN

STEP-DOWN

OUT1

GND

STEP-DOWN

OUT2

GND

IN12

2.8V TO 5.5V
(2.6V TO 5.5V)

LX1

FB

FB

OUT1
(FB1)

PGND1

LX2

OUT2
(FB2)

PGND2

EN1

EN2

EN3

EN4

PWRON LOGIC
AND ENABLES

() ARE FOR THE MAX8668

LDO

IN

EN

OUT3

GND

OUT

OUT3

LDO

OUT4

GND

OUT

OUT4

IN

EN

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

10 ______________________________________________________________________________________

Detailed Description

The MAX8667/MAX8668 dual step-down converters
with dual low-dropout (LDO) linear regulators are
intended to power low-voltage microprocessors or
DSPs in portable devices. They feature high efficiency
with small external component size. The step-down out­puts are adjustable from 0.6V to 3.3V (MAX8668) or
factory preset (MAX8667) with guaranteed output cur­rent of 600mA for OUT1 and 1200mA for OUT2. The

1.5MHz hysteretic-PWM control scheme allows for tiny
external components and reduces no-load operating
current to 100µA (typ) with all regulators enabled. Dual,
low-quiescent-current, low-noise LDOs operate down to

1.7V supply voltage. The MAX8667/MAX8668 have
individual enable inputs for each output to facilitate any
supply sequencing.

Step-Down DC-DC Regulators

(OUT1, OUT2)

Step-Down Regulator Architecture

The MAX8667/MAX8668 step-down regulators are opti­mized for high-efficiency voltage conversion over a
wide load range, while maintaining excellent transient
response, minimizing external component size, and
minimizing output voltage ripple. The DC-DC convert­ers (OUT1, OUT2) also feature an optimized on-resis­tance internal MOSFET switch and synchronous
rectifier to maximize efficiency. The MAX8667/
MAX8668 utilize a proprietary hysteretic-PWM control
scheme that switches with nearly fixed frequency at up
to 1.5MHz allowing for ultra-small external components.
The step-down converter output current is guaranteed
up to 600mA for OUT1 and 1200mA for OUT2.

When the step-down converter output voltage falls below
the regulation threshold, the error comparator begins a
switching cycle by turning the high-side p-channel
MOSFET switch on. This switch remains on until the mini­mum on-time (t

ON

) expires and the output voltage is in

regulation or the current-limit threshold (I

LIMP_

) is
exceeded. Once off, the high-side switch remains off
until the minimum off-time (t

OFF

) expires and the output
voltage again falls below the regulation threshold.
During this off period, the low-side synchronous rectifi­er turns on and remains on until either the high-side
switch turns on or the inductor current reduces to the
rectifier-off current threshold (I

LXOFF

= 60mA typ). The
internal synchronous rectifier eliminates the need for an
external Schottky diode.

Input Supply and Undervoltage Lockout

The input voltage range of step-down regulators OUT1
and OUT2 is 2.6V to 5.5V. This supply voltage must be
greater than or equal to the LDO supply voltage (V

IN34

).

A UVLO circuit prevents step-down regulators OUT1
and OUT2 from switching when the supply voltage is
too low to guarantee proper operation. When V

IN12

falls
below 2.4V (typ), OUT1 and OUT2 are shut down.
OUT1 and OUT2 turn on and begin soft-start when
V

IN12

rises above 2.5V (typ).

Soft-Start

When initially powered up, or enabled with EN_, the
step-down regulators soft-start by gradually ramping
up the output voltage. This reduces inrush current dur­ing startup. See the startup waveforms in the

Typical

Operating Characteristics

section.

Current Limit

The MAX8667/MAX8668 limit the peak inductor current
of the p-channel MOSFET (I

LIMP_

). A valley current limit
is used to protect the step-down regulators during
severe overload and output short-circuit conditions.
When the peak current limit is reached, the internal
p-channel MOSFET turns off and remains off until the
output drops below regulation, the inductor current falls
below the valley current-limit threshold, and the mini­mum off-time has expired.

Voltage Positioning

The OUT1 and OUT2 output voltages and voltage posi­tioning of the MAX8668 are set by a resistor network
connected to FB_. With this configuration, a portion of
the feedback signal is sensed on the switched side of
the inductor, and the output voltage droops slightly as
the load current is increased due to the DC resistance
of the inductor. This output voltage droop is known as
voltage positioning. Voltage positioning allows the load
regulation to be set to match the voltage droop during
a load transient, reducing the peak-to-peak output volt­age deviation during a load transient, and reducing the
output capacitance requirements.

Dropout

As the input voltage approaches the output voltage, the
duty cycle of the p-channel MOSFET reaches 100%. In
this state, the p-channel MOSFET is turned on con­stantly (not switching), and the dropout voltage is the
voltage drop due to the output current across the on­resistance of the internal p-channel MOSFET (R

PCH

)

and the inductor’s DC resistance (R

L

):

LDO Linear Regulators (OUT3, OUT4)

The MAX8667/MAX8668 contain two low-dropout linear
regulators (LDOs), OUT3 and OUT4. The LDO output
voltages are factory preset, and each LDO supplies

VI R R

=+

DO LOAD PCH L

()

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

______________________________________________________________________________________ 11

loads up to 300mA. The LDOs include an internal refer­ence, error amplifier, p-channel pass transistor, and
internal voltage-dividers. Each error amplifier compares
the reference voltage to the output voltage (divided by
the internal voltage-divider) and amplifies the differ­ence. If the divided feedback voltage is lower than the
reference voltage, the pass-transistor gate is pulled
lower, allowing more current to pass to the outputs and
increasing the output voltage. If the divided feedback
voltage is too high, the pass-transistor gate is pulled
up, allowing less current to pass to the output.

Input Supply and Undervoltage Lockout

The input voltage range of LDO regulators OUT3 and
OUT4 is 1.7V to 5.5V. This supply voltage must be less
than or equal to the voltage applied to IN12 (V

IN34

≤

V

IN12

).

An undervoltage lockout circuit turns off the LDO regula­tors when the input supply voltage is too low to guarantee
proper operation. When V

IN34

falls below 1.5V (typ),
OUT3 and OUT4 are shut down. OUT3 and OUT4 turn
on and begin soft-start when V

IN34

rises above 1.6V (typ).

Soft-Start

When initially powered up, or enabled with EN_, the
LDOs soft-start by gradually ramping up the output
voltage. This reduces inrush current during startup. The

soft-start ramp time is typically 100µs from the start of
the soft-start ramp to the output reaching its nominal
regulation voltage.

Current Limit

The OUT3 and OUT4 output current is limited to 375mA
(min). If the output current exceeds the current limit, the
corresponding LDO output voltage drops.

Dropout

The maximum dropout voltage for the linear regulators
is 250mV at 300mA load. To avoid dropout, make sure
the IN34 supply voltage is at least 250mV higher than
the highest LDO output voltage.

Thermal-Overload Protection

Thermal-overload protection limits the total power dissi­pation in the MAX8667/MAX8668. Thermal-protection
circuits monitor the die temperature. If the die tempera­ture exceeds +160°C, the IC is shut down, allowing the
IC to cool. Once the IC has cooled by 15°C, the IC is
enabled again. This results in a pulsed output during
continuous thermal-overload conditions. The thermal­overload protection protects the MAX8667/MAX8668 in
the event of fault conditions. For continuous operation,
do not exceed the absolute maximum junction temper­ature of +150°C. See the

Thermal Considerations

sec-

tion for more information.

Figure 2. Timing Diagram

IN12

ENx

OUTx

ENy

OUTy

t

IS THE PERIOD REQUIRED TO ENABLE FROM SHUTDOWN

PWRON

t

PWRON

tEN IS THE ENABLE TIME FOR SUBSEQUENT ENABLE
SIGNALS FOLLOWING THE FIRST ENABLE

t

EN

ENx, ENy ARE ANY COMBINATION OF EN1–EN4.

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

12 ______________________________________________________________________________________

Figure 3. MAX8667 Typical Application Circuit

Figure 4. MAX8668 Typical Application Circuit

C3

INPUT

2.8V TO 5.5V

10μF

0.01μF

C2

C1

EN1

EN2
REF

GND

IN12

IN34

1.7V TO 5.5V

EN3

EN4

OUT3

OUT4

4.7μF

4.7μF

300mA

300mA

C8

C9

4.7μF

MAX8667

OUT2

1.2A

2.2μF

L2

2.2μH

C7

LX2

OUT2

PGND2 PGND1

LX1

OUT1

L1

2.2μH

OUT1
600mA

C6

2.2μF

INPUT

2.6V TO 5.5V

OUT2

0.6V TO 3.3V, 1.2A

C7

2.2μF

10μF

0.01μF

C5

C2

C1

C10*

L2

2.2μH

R5*

IN34

IN12

EN1

EN2

REF

GND

MAX8668

LX2

R3

FB2

R4

PGND1 PGND2

*C10, R5, AND R6 ARE OPTIONAL

EN3

EN4

OUT3

OUT4

LX1

FB1

4.7μF

R1

R2

C8

L1

2.2μH

R6*

C4

OUT3, 300mA

OUT4, 300mA

C9

4.7μF

OUT1

0.6V TO 3.3V, 600mA

C6

2.2μF

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

______________________________________________________________________________________ 13

Applications Information

Setting the Output Voltages

and Voltage Positioning

The LDO output voltages of the MAX8667/MAX8668,
and the step-down outputs of the MAX8667 are factory
preset. See the

Selector Guide

to find the part number

corresponding to the desired output voltages.

The OUT1 and OUT2 output voltages of the MAX8668
are set by a resistor network connected to FB_ as
shown in Figure 5. With this configuration, a portion of
the feedback signal is sensed on the switched side of
the inductor (LX), and the output voltage droops slightly
as the load current is increased due to the DC resis­tance of the inductor (DCR). This allows the load regu­lation to be set to match the voltage droop during a
load transient (voltage positioning), reducing the peak­to-peak output-voltage deviation during a load tran­sient, and reducing the output capacitance
requirements.

For the simplest method of setting the output voltage,
R6 is not installed. Choose the value of R2 (a good
starting value is 100kΩ), and then calculate the value of
R1 as follows:

where VFBis the feedback regulation voltage (0.6V).

With the voltage set in this manner, the voltage posi­tioning depends only on the DCR, and the maximum
output voltage droop is:

Setting the Output Voltages with

Reduced Voltage Positioning

To obtain less voltage positioning than described in the
previous section, use the following procedure for set­ting the output voltages. The OUT1 and OUT2 output
voltages and voltage positioning of the MAX8668 are
set by a resistor network connected to FB_ as shown in
Figure 5.

To set the output voltage (V

OUT

), first select a value for
R2 (a good starting value is 100kΩ). Then calculate the
value of REQ(the equivalent parallel resistance of R1
and R6) as follows:

where VFBis the feedback-regulation voltage (0.6V).

Calculate the factor m based on the desired load-regu­lation improvement:

where I

OUT(MAX)

is the maximum output current, DCR is

the inductor series resistance, and ΔV

OUT(DESIRED)

is the
maximum allowable droop in the output voltage at full
load. The calculated value for m must be between 1.1 and
2; m = 2 results in a 2x improvement in load regulation.

Now calculate the values of R1 and R6 as follows:

The value of R1 should always be lower than the value
of R6.

Power-Supply Sequencing

The MAX8667/MAX8668 have individual enable inputs
for each regulator to allow complete control over the
power sequencing. When all EN_ inputs are low, the IC
is in low-power shutdown mode, reducing the supply
current to less than 1µA. After one of the EN_ inputs
asserts high, the corresponding regulator begins soft­start after a delay of tEN(see Figure 2). The first output
enabled from shutdown mode or initially powering up
the IC has a longer delay (t

PWRON

) as the IC exits the

low-power shutdown mode.

Inductor Selection

The MAX8667/MAX8668 step-down converters operate
with inductors between 2.2µH and 4.7µH. Low induc­tance values are physically smaller, but require faster
switching, resulting in some efficiency loss. The induc­tor’s DC current rating must be high enough to account

Figure 5. MAX8668 Feedback Network

RR

12 1=× −

ΔV DCR I

OUT MAX OUT MAX() ()

V

⎛

OUT

⎜
⎝

V

FB

⎞
⎟

⎠

=×

R1

R2

L1 DCR

C4

(OPTIONAL)

OUT

R6

ESR

C6

R

LOAD

LX_

FB_

I DCR

OUT MAX

m

=

V

Δ

OUT DESIRED

×

()

()

RR m

1

=×

EQ

RR

6

=×

EQ

m

m

1

−

R

V

⎛

OUT

=−

EQ

⎜
⎝

V

FB

⎞

×12

R

⎟
⎠

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

14 ______________________________________________________________________________________

for peak ripple current and load transients. The step­down converter’s unique architecture has minimal cur­rent overshoot during startup and load transients and in
most cases, an inductor capable of 1.3x the maximum
load current is acceptable.

For output voltages above 2V, when light-load efficiency
is important, the minimum recommended inductor is

2.2µH. For optimum voltage-positioning load transients,
choose an inductor with DC series resistance in the
50mΩ to 150mΩ range. For higher efficiency at heavy
loads (above 200mA) and minimal load regulation,
keep the inductor resistance as small as possible. For
light-load applications (up to 200mA), higher resistance
is acceptable with very little impact on performance.

Capacitor Selection

Input Capacitors

The input capacitor for the step-down converters (C2 in
Figures 3 and 4) reduces the current peaks drawn from
the battery or input power source and reduces switch­ing noise in the IC. The impedance of C2 at the switch­ing frequency should be very low. Surface-mount
ceramic capacitors are a good choice due to their
small size and low ESR. Make sure the capacitor main­tains its capacitance over temperature and DC bias.
Ceramic capacitors with X5R or X7R temperature char­acteristics generally perform well. A 10µF ceramic
capacitor is recommended.

A 4.7µF ceramic capacitor is recommended for the
LDO input capacitor (C3 in Figure 3).

Step-Down Output Capacitors

The step-down output capacitors (C6 and C7 in Figures
3 and 4) are required to keep the output-voltage ripple

small and to ensure regulation loop stability. These
capacitors must have low impedance at the switching
frequency. Surface-mount ceramic capacitors are a
good choice due to their small size and low ESR. Make
sure the capacitor maintains its capacitance over tem­perature and DC bias. Ceramic capacitors with X5R or
X7R temperature characteristics generally perform well.
The output capacitance can be very low. For most
applications, a 2.2µF ceramic capacitor is sufficient.
For optimum load-transient performance and very low
output ripple, the output capacitor value in µF should
be equal to or greater than the inductor value in µH.

Feed-Forward Capacitor

The feed-forward capacitors on the MAX8668 (C4 and
C5 in Figure 4) set the feedback loop response, control
the switching frequency, and are critical in obtaining
the best efficiency possible. Small X7R and C0G
ceramic capacitors are recommended.

For OUT1, calculate the value of C4 as follows:

C4 = 1.2 x 10-5(s/V) x (V

OUT

/ R1)

For OUT2, calculate the value of C5 and C10 as fol­lows:

Cff= 1.2 x 10-5(s/V) x (V

OUT

/ R3)

Cff= C5 + (C10 / 2)

(C10 / C5) + 1 = (V

OUT

/ VFB), where VFBis 0.6V.

Rearranging the formulas:

C10 = 2 x Cffx (V

OUT

- VFB)/(V

OUT

+ VFB)

C5 = Cff– (C10 / 2)

C10 is needed if V

OUT

> 1.5V or V

IN12

can be less than

V

OUT

/ 0.65.

Table 1. Recommended Inductors

MANUFACTURER INDUCTOR L (µH) RL (mΩ) CURRENT RATING (A) L x W x H (mm)

FDK MIPF2016 2.2 110 1.1 2.0 x 1.6 x 1.0

FDK MIPF2520D 2.2 80 1.3 2.5 x 2.0 x 1.0

Murata

Sumida CDRH2D09 2.2 120 0.44 3.2 x 3.2 x 1.0

TDK GLF251812T 2.2 200 0.6 2.5 x 1.8 x 1.35

TOKO D2812C 2.2 140 0.77 2.8 x 2.8 x 1.2

TOKO MDT2520-CR 2.2 80 0.7 2.5 x 2.0 x 1.0

Wurth

Taiyo Yuden CB2518T 2.2 90 0.51 2.5 x 1.8 x 2.0

LQH32CN2R2M5 2.2 97 0.79 3.2 x 2.5 x 1.55

LQM31P 2.2 220 0.9 3.2 x 1.6 x 0.95

TPC Series 2.2 55 1.8 4.0 x 4.0 x 1.1

TPC Series 4.7 124 1.35 4.0 x 4.0 x 1.1

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

______________________________________________________________________________________ 15

LDO Output Capacitor and Stability

Connect a 4.7µF ceramic capacitor between OUT3 and
GND, and a second 4.7µF ceramic capacitor from
OUT4 to GND. For a constant loading above 10mA, the
output capacitors can be reduced to 2.2µF. The equiv­alent series resistance (ESR) of the LDO output capaci­tors affects stability and output noise. Use output
capacitors with an ESR of 0.1Ω or less to ensure stable
operation and optimum transient response. Surface­mount ceramic capacitors have very low ESR and are
commonly available. Connect these capacitors as
close as possible to the IC’s pins to minimize PCB trace
inductance.

Thermal Considerations

The maximum package power dissipation of the
MAX8667/MAX8668 is 1667mW. Make sure the power
dissipated by the MAX8667/MAX8668 does not exceed
this rating. The total IC power dissipation is the sum of
the power dissipation of the four regulators:

Estimate the OUT1 and OUT2 power dissipations as
follows:

where RLis the inductor’s DC resistance, and η is the
efficiency (see the

Typical Operating Characteristics

section).

Calculate the OUT3 and OUT4 power dissipations as
follows:

The maximum junction temperature of the MAX8667/
MAX8668 is +150°C. The junction-to-case thermal
resistance (θ

JC

) of the MAX8667/MAX8668 is 6.9°C/W.

When mounted on a single-layer PCB, the junction to
ambient thermal resistance (θ

JA

) is about 64°C/W.

Mounted on a multilayer PCB, θJAis about 48°C/W.
Calculate the junction temperature of the
MAX8667/MAX8668 as follows:

where TAis the maximum ambient temperature. Make
sure the calculated value of TJdoes not exceed the
+150°C maximum.

PCB Layout

High switching frequencies and relatively large peak
currents make PCB layout a very important aspect of
design. Good design minimizes excessive EMI on the
feedback paths and voltage gradients in the ground
plane, both of which can result in instability or regula­tion errors. Connect the input capacitors as close as
possible to the IN_ and PGND_ pins. Connect the
inductor and output capacitors as close as possible to
the IC and keep the traces short, direct, and wide.

The feedback network traces are sensitive to inductor
magnetic field interference. Route these traces away
from the inductors and noisy traces such as LX. Keep
the feedback components close to the FB_ pin.

Connect GND and PGND_ to the ground plane.
Connect the exposed paddle to the ground plane with
one or more vias to help conduct heat away from the
IC.

Refer to the MAX8668 evaluation kit for a PCB layout
example.

PPPPP

=+++

DDDDD

1234

=× ×

PI V

D OUT OUT 11 1

=× ×

PI V

D OUT OUT 22 2

PI V V

=× −

D OUT IN OUT 3334 3

()

1

1

−η
η

−η

η

TTP

=+× θ

JADJA

PI V V

=×−

D OUT IN OUT 4434 4

()

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

16 ______________________________________________________________________________________

Chip Information

PROCESS: BiCMOS

Ordering Information (continued)

All MAX8667/MAX8668 parts are in a 16-pin, thin QFN, 3mm x
3mm package and operate in the -40°C to = +85°C extended
temperature range.

+

Denotes a lead-free package.

PART PKG CODE TOP MARK

T1633-4 AFJ

T1633-4 AFQ

T1633-4 AER

T1633-4 AFK

T1633-4 AFR

MAX8668ETET+ T1633-4 AFS

T1633-4 AFL

T1633-4 AFT

T1633-4 AFU

T1633-4 AFV

Selector Guide

PART

OUT1

(V)

OUT2

(V)

OUT3

(V)

OUT4

(V)

1.20 1.80 2.80 2.80

1.20 1.80 2.85 2.85

1.20 1.80 1.20 1.20

1.60 1.80 2.80 1.20

1.80 1.20 2.60 2.80

1.30 1.30 3.30 2.70

MAX8668ETEA+ ADJ ADJ 2.80 2.80

MAX8668ETEP+ ADJ ADJ 3.30 1.80

ADJ ADJ 2.80 1.20

MAX8668ETET+ ADJ ADJ 3.30 3.30

MAX8668ETEU+ ADJ ADJ 3.30 2.80

MAX8668ETEV+ ADJ ADJ 3.30 2.50

ADJ ADJ 3.30 3.00

MAX8668ETEX+ ADJ ADJ 2.80 1.80

MAX8667ETEHR+

MAX8667ETEJS+

MAX8668ETEA+

MAX8668ETEP+

MAX8668ETEQ+

MAX8668ETEU+

MAX8668ETEV+

MAX8668ETEW+

MAX8668ETEX+

MAX8667ETEAA+

MAX8667ETEAB+

MAX8667ETEAC+

MAX8667ETECQ+

MAX8667ETEHR+

MAX8667ETEJS+

MAX8668ETEQ+

MAX8668ETEW+

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

______________________________________________________________________________________ 17

Package Information

(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information
go to www.maxim-ic.com/packages

.)

MARKING

D/2

D

E

E/2

AAAA

C

L

0.10 C 0.08 C

A

A2

A1

(NE - 1) X e

(ND - 1) X e

C

L

L

e

k

L

C

L

e

E2/2

E2

D2/2

D2

b

0.10 M C A B

C
L

L

e

12x16L QFN THIN.EPS

PACKAGE OUTLINE
8, 12, 16L THIN QFN, 3x3x0.8mm

21-0136

1

I

2

MAX8667/MAX8668

1.5MHz Dual Step-Down DC-DC Converters
with Dual LDOs and Individual Enables

Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.

18

____________________Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600

© 2007 Maxim Integrated Products is a registered trademark of Maxim Integrated Products. Inc.

Package Information (continued)

(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information
go to www.maxim-ic.com/packages

.)

8L 3x3

PKG

REF. MIN.

MIN.

NOM. M

3.00 3.10

0.65 BSC.

0.55 0.75

8

2

2

0.02

0.20 REF

-

AX.

0.05

-

0.70 0.75 0.80

A

b

0.25 0.30 0.35

2.90

D

2.90 3.00 3.10

E

e

0.35

L

ND

NE

A1

A2

k

0.25

0

12L 3x3

NOM. MAX. NOM.

0.70

0.75

0.50 BSC.

0

0.20 REF

0.25

3.00

3.00

0.55

0.02

0.80

0.30

3.10

3.10

0.65

12N

3

3

0.05

-

-

0.20

2.90

2.90

0.45

0.25

16L 3x3

MIN. MAX.

0.70

0.75

0.25

3.00

3.00

0.50 BSC.

0.40

040.02

0.20 REF

0.80

0.30

3.10

3.10

0.50

16

4

0.05

-

0.20

2.90

2.90

0.30

0.25

EXPOSED PAD VARIATIONS

PKG.
CODES

TQ833-1 1.250.25 0.70 0.35 x 45° WEE C1.250.700.25

T1233-1

3

T1233-

T1233-4

T1633-2 0.9 5

T1633F-3

T1633FH-3 0.65 0.80 0.95

T1633-4 0.9 5

-

T1633-5 0.9 5

D2

MIN.

0.95

0.95

0.95

0.65

MAX.

NOM.

1.25

1.10

1.25

1.10

1.251.10

1.25

1.10

0.95

0.80

1.10 1.25 0.95 1.10

1.25

1.10

E2

NOM.

MIN.

0.95

0.95 1.10 0.35 x 45°1.25 WEED-1

0.95

0.65

0.65 0.80

1.10

1.100.95

1.10

0.80

1.10

MAX.

1.25

1.25

0.95

0.95

1.25

1.25

ID

PIN

0.35 x 45°

0.35 x 45°

0.35 x 45°

0.225 x 45°

0.225 x 45°

0.35 x 45°

0.35 x 45°

JEDEC

WEED-1

WEED-11.25

WEED-2

WEED-2

WEED-2

WEED-2

WEED-20.95

NOTES:

1. DIMENSIONING & TOLERANCING CONFORM TO ASME Y14.5M-1994.

2. ALL DIMENSIONS ARE IN MILLIMETERS. ANGLES ARE IN DEGREES.

3. N IS THE TOTAL NUMBER OF TERMINALS.

4. THE TERMINAL #1 IDENTIFIER AND TERMINAL NUMBERING CONVENTION SHALL CONFORM TO
JESD 95-1 SPP-012. DETAILS OF TERMINAL #1 IDENTIFIER ARE OPTIONAL, BUT MUST BE LOCATED
WITHIN THE ZONE INDICATED. THE TERMINAL #1 IDENTIFIER MAY BE EITHER A MOLD OR
MARKED FEATURE.

5. DIMENSION b APPLIES TO METALLIZED TERMINAL AND IS MEASURED BETWEEN 0.20 mm AND 0.25 mm
FROM TERMINAL TIP.

6. ND AND NE REFER TO THE NUMBER OF TERMINALS ON EACH D AND E SIDE RESPECTIVELY.

7. DEPOPULATION IS POSSIBLE IN A SYMMETRICAL FASHION.

8. COPLANARITY APPLIES TO THE EXPOSED HEAT SINK SLUG AS WELL AS THE TERMINALS.

9. DRAWING CONFORMS TO JEDEC MO220 REVISION C.

10. MARKING IS FOR PACKAGE ORIENTATION REFERENCE ONLY.

11. NUMBER OF LEADS SHOWN ARE FOR REFERENCE ONLY.

12. WARPAGE NOT TO EXCEED

0.10mm.
PACKAGE OUTLINE

8, 12, 16L THIN QFN, 3x3x0.8mm

21-0136

I

2

2