19-3105; Rev 2; 8/96
EVALUATION KIT MANUAL
FOLLOWS DATA SHEET
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
_______________General Description
The MAX742 DC-DC converter is a controller for dual-output power supplies in the 3W to 60W range. Relying on
simple two-terminal inductors rather than transformers, the
MAX742 regulates both outputs independently to within
±4% over all conditions of line voltage, temperature, and
load current.
The MAX742 has high efficiency (up to 92%) over a wide
range of output loading. Two independent PWM currentmode feedback loops provide tight regulation and operation free from subharmonic noise. The MAX742 can
operate at 100kHz or 200kHz, so it can be used with small
and lightweight external components. Also ripple and
noise are easy to filter. The MAX742 provides a regulated
output for inputs ranging from 4.2V to 10V (and higher with
additional components).
External power MOSFETs driven directly from the MAX742
are protected by cycle-by-cycle overcurrent sensing. The
MAX742 also features undervoltage lockout, thermal shutdown, and programmable soft-start.
If 3W of load power or less is needed, refer to the MAX743
data sheet for a device with internal power MOSFETs.
________________________Applications
DC-DC Converter Module Replacement
Distributed Power Systems
Computer Peripherals
__________________Pin Configuration
____________________________Features
♦ Specs Guaranteed for In-Circuit Performance
♦ Load Currents to ±2A
♦ 4.2V to 10V Input-Voltage Range
♦ Switches From ±15V to ±12V Under Logic Control
♦ ±4% Output Tolerance Max Over Temp, Line,
and Load
♦ 90% Typ Efficiency
♦ Low-Noise, Current-Mode Feedback
♦ Cycle-by-Cycle Current Limiting
♦ Undervoltage Lockout and Soft-Start
♦ 100kHz or 200kHz Operation
______________Ordering Information
PART
MAX742CPP
MAX742CWP
MAX742C/D 0°C to +70°C
MAX742EPP -40°C to +85°C 20 Plastic DIP
MAX742EWP
MAX742MJP -55°C to +125°C
* Contact factory for dice specifications
TEMP. RANGE PIN-PACKAGE
0°C to +70°C
0°C to +70°C
-40°C to +85°C 20 Wide SO
20 Plastic DIP
20 Wide SO
Dice*
20 CERDIP
__________Simplified Block Diagram
+5V
MAX742
CC-
INPUT
MAX742
TOP VIEW
R
FB+
1
CC+
2
AGND
3
AV
4
100/200
12/15
VREF
SS
CC-
FB-
________________________________________________________________
MAX742
5
6
7
8
9
10
DIP/SO
CSH+
20
CSL+
19
GND
18
EXT+
17
PUMP
16
PDRV
15
EXT-
14
V+
13
CSH-
12
CSL-
11
+2.0V
VREF
CC+
-SENSE
PWM
S
-DRIVE
OSC
+DRIVE
S
PWM
+SENSE
R
Maxim Integrated Products
P
N
-VO
+VO
1
For free samples & the latest literature: http://www.maxim-ic.com, or phone 1-800-998-8800
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
ABSOLUTE MAXIMUM RATINGS
V+, AV+ to AGND, GND.........................................-0.3V to +12V
PDRV to V+.............................................................+0.3V to -14V
FB+, FB- to GND..................................................................±25V
Input Voltage to GND
(CC+, CC-, CSH+, CSL+, CSH-, CSL-,
SS, 100/200
Output Voltage to GND
MAX742
(EXT+, PUMP) ..........................................-0.3V to (V+ + 0.3V)
EXT- to PDRV................................................-0.3V to (V+ + 0.3V)
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
, 12/15)..................................-0.3V to (V+ + 0.3V)
ELECTRICAL CHARACTERISTICS
(Circuit of Figure 2, +4.5V < V+ < +5.5V.)
Continuous Power Dissipation (any package)
up to +70°C.....................................................................500mW
derate above +70°C by ..........................................100mW/°C
Operating Temperature Ranges
MAX742C_ _ .......................................................0°C to +70°C
MAX742E_ _ ....................................................-40°C to +85°C
MAX742MJP ..................................................-55°C to +125°C
Storage Temperature Range.............................-65°C to +150°C
Lead Temperature (soldering, 10sec).............................+300°C
Output Voltage, ±15V Mode
(Notes 1, 2)
Output Voltage, ±12V Mode
(Notes 1, 2)
0mA < IL< 100mA,
12/15 = 0V
0mA < IL< 125mA,
12/15 = V+
ELECTRICAL CHARACTERISTICS
(Circuit of Figure 2, V+ = 5V, 100/200 = 12/15 = 0V; TA= T
V+ = 4.5V to 5.5V, PDRV from PUMP
I
Load Regulation (Note 2)
No-Load Supply Current
Oscillator Frequency
Positive Current-Limit Threshold
(CSH+ to CSL+)
Negative Current-Limit Threshold
(CSH- to CSL-)
f
OSC
= 0mA to 100mA
LOAD
No EXT- or PUMP load,
FB+ = FB- = open circuit
100/200 = 0V
100/200 = V+
EXT+ or EXTCSL+ = 0V, FB+ = open circuit
CSH- = V+, FB- = open circuit
CONDITIONS
to T
MIN
CONDITIONS
TA= +25°C
TA= T
TA= +25°C
TA= T
, unless otherwise noted.)
MAX
V+ = 5V
MIN
MIN
to T
to T
MAX
MAX
14.55 15.45
14.40 15.60
11.64 12.36
11.52 12.48
3
10V+ = 10V
170 200 230
75 100 125
/2PUMP Frequency
OSC
UNITSMIN TYP MAXSYMBOLPARAMETER
V
V
UNITSMIN TYP MAXSYMBOLPARAMETER
%/%0.01 0.05Line Regulation
mV30 100
mA
V3.8 4.2UVLOUndervoltage Lockout
V0.2Undervoltage Lockout Hysteresis
V2.0Reference Output Voltage
kHz
kHzf
%85 90Duty-Cycle Limit (Note 3)
mV150 225 300
mV150 225 300
2 _______________________________________________________________________________________
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
ELECTRICAL CHARACTERISTICS (continued)
(Circuit of Figure 2, V+ = 5V, 100/200 = 12/15 = 0V; TA= T
Output Voltage High
Output Voltage Low
Output Sink Current
Output Source Current
Output Rise/Fall Time
Note 1: Devices are 100% tested to these limits under 0mA to 100mA and to 125mA conditions using automatic test equipment.
The ability to drive loads up to 1A is guaranteed by the current-limit threshold, output swing, and the output current
source/sink tests. See Figures 2 and 3.
Note 2: Actual load capability of the circuit of Figure 2 is ±200mA in ±15V mode and ±250mA in ±12V mode. Load regulation is
tested at lower limits due to test equipment limitations.
Note 3: Guaranteed by design.
Note 4: Measured at Point A, circuit of Figure 2, with PDRV disconnected.
EXT+, EXT-, IL= 1mA, V+ = 4.5V, PDRV= -3V
OH
EXT+, EXT-, IL= -1mA, V+ = 4.5V, PDRV= -3V
OL
V+ = 4.5V, PDRV = -3V,
TA= +25°C
V+ = 4.5V, PDRV = -3V,
TA= +25°C
EXT+, C
LOAD
V+ = 4.5V, IL= -5mA, TA= +25°C
CC+, CC-
SS = 0V
V+ = 3.8V, SS = 2V
to T
MIN
MAX
CONDITIONS
= 2nF
LOAD
= 4nF, PDRV = -3V
, unless otherwise noted.)
EXT+ = 4.5V
EXT- = 4.5V
EXT+ = 0V
EXT- = -3V
100 200
200 350
-200 -100
-350 -200
70
100EXT-, C
MAX742
UNITSMIN TYP MAXSYMBOLPARAMETER
V4.3V
V-2.8V
mA
mA
ns
V-3PUMP Output Voltage (Note 4)
kΩ10Compensation Pin Impedance
°C190Thermal-Shutdown Threshold
µA37Soft-Start Source Current
mA-2 -0.5Soft-Start Sink Current
_______________________________________________________________________________________ 3
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
__________________________________________Typical Operating Characteristics
(Circuit of Figure 2, V+ = 5V, TA = +25°C, unless otherwise noted.)
UNDERVOLTAGE LOCKOUT HYSTERESIS
25
±15V MODE,
MAX742
QUIESCENT SUPPLY CURRENT (mA)
200kHz MODE
20
15
10
5
06
EFFICIENCY vs. LOAD CURRENT,
22W CIRCUIT, ±15V MODE
90
80
70
EFFICIENCY (%)
CIRCUIT OF FIGURE 3,
INDUCTORS = GOWANDA 121-AT2502
(MPP CORE),
60
Q2 = TWO IRF9Z30 IN PARALLEL
±15V MODE
50
0
LOCKOUT
ENABLED
23 51
SUPPLY VOLTAGE (V)
±400 ±600 ±1000±200
LOAD CURRENT (mA)
4
200kHz
±800
100kHz
CHARGE-PUMP LOAD REGULATION
-5.0
MAX742 -1
-4.5
-4.0
-3.5
-3.0
CHARGE-PUMP OUTPUT VOLTAGE (V)
-2.5
MEASURED AT POINT A
0
23 75 6 10 891
4
CHARGE-PUMP LOAD CURRENT (mA)
EFFICIENCY vs. LOAD CURRENT,
6W CIRCUIT, ±15V MODE
MAX742 -4
90
80
70
EFFICIENCY (%)
60
INDUCTORS = GOWANDA 050-AT1003
(MPP CORE)
50
0
±100 ±150 ±250±50
LOAD CURRENT (mA)
V+ = 4.5V
V+ = 5V
200kHz
±200
100kHz
6
MAX742 -2
5
4
3
2
PDRV CURRENT (mA)
1
MAX742 -5
90
80
70
EFFICIENCY (%)
60
50
PDRV CURRENT vs. C
PDRV FORCED TO -4V
PUMP DISCONNECTED
200kHz
100kHz
0
CAPACITANCE AT EXT- (nF)
231
EFFICIENCY vs. LOAD CURRENT,
6W CIRCUIT, ±12V MODE
200kHz
INDUCTORS = GOWANDA 050-AT1003
(MPP CORE)
0
±150 ±225±75
LOAD CURRENT (mA)
EXT-
MAX742 -3
4
MAX742 -6
100kHz
±300
PEAK INDUCTOR CURRENT vs.
LOAD CURRENT
1200
1100
1000
900
800
700
600
500
400
300
PEAK INDUCTOR CURRENT (mA)
200
100
0
MEASURED AT LX-,
±15V MODE
100 15050
LOAD CURRENT (mA)
100kHz
MAX742 -7
200
200kHz
150
100
CURRENT-LIMIT THRESHOLD (mV)
200
CURRENT-LIMIT THRESHOLD vs.
SOFT-START VOLTAGE
50
0
12
SOFT-START VOLTAGE (V)
4 _______________________________________________________________________________________
MAX742 -8
3
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
_____________________________Typical Operating Characteristics (continued)
(Circuit of Figure 2, I
A = GATE DRIVE, 5V/div
B = SWITCH VOLTAGE, 10V/div
C = SWITCH CURRENT, 0.2A/div
= 100mA, unless otherwise noted.)
LOAD
SWITCHING WAVEFORMS,
INVERTING SECTION
2µs/div
OUTPUT-VOLTAGE NOISE,
FILTERED AND UNFILTERED
SWITCHING WAVEFORMS,
STEP-UP SECTION
A
B
C
2µs/div
A = GATE DRIVE, 5V/div
B = SWITCH VOLTAGE, 10V/div
C = SWITCH CURRENT, 0.2A/div
LOAD-TRANSIENT RESPONSE
A
B
C
MAX742
A = NOISE WITH i FILTER, 1mV/div
B = NOISE WITHOUT FILTER, 20mV/div
MEASURED AT -V
V+ = 5V
BW = 5MHz
2µs/div
OUT
_______________________________________________________________________________________ 5
A
A
B
200µs/div
A = +VO, 20mV/div
B = -VO, 50mV/div
B
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
______________________________________________________________Pin Description
PIN
MAX742
Step-Up Feedback InputFB+1
Step-Up Compensation CapacitorCC+2
Analog GroundAGND3
Analog Supply Voltage Input (+5V)AV+4
Selects oscillator frequency. Ground for 200kHz, or tie to V+ for 100kHz.100/2005
Selects V
Reference Voltage Output (+2.00V). Force to GND or V+ to disable chip.VREF7
Soft-Start Timing Capacitor (sources 5µA)SS8
Inverting Compensation CapacitorCC-9
Inverting Section Feedback InputFB-10
Current-Sense Low (inverting section)CSL-11
Current-Sense High (inverting section)CSH-12
Supply Voltage Input (+5V)V+13
Push-Pull Output—drives external P-channel MOSFET.EXT-14
Voltage Input—negative supply for P-channel MOSFET driver.PDRV15
Charge-Pump Driver—clock output at 1/2 oscillator frequency.PUMP16
OUT
FUNCTIONNAME
. Ground for ±15V, or tie to V+ for ±12V.12/156
Push-Pull Output—drives external logic-level N-channel MOSFET.EXT+17
High-Current GroundGND18
Current-Sense Low (step-up section)CSL+19
Current-Sense High (step-up section)CSH+20
________________Operating Principle
Each current-mode controller consists of a summing
amplifier that adds three signals: the current waveform
from the power switch FET, an output-voltage error signal, and a ramp signal for AC compensation generated
by the oscillator. The output of the summing amplifier
resets a flip-flop, which in turn activates the power FET
driver stage (Figure 1).
Both external transistor switches are synchronized to
the oscillator and turn on simultaneously when the flipflop is set. The switches turn off individually when their
6 _______________________________________________________________________________________
source currents reach a trip threshold determined by
the output-voltage error signal. This creates a dutycycle modulated pulse train at the oscillator frequency,
where the on time is proportional to both the outputvoltage error signal and the peak inductor current. Low
peak currents or high output-voltage error signals result
in a high duty cycle (up to 90% maximum).
AC stability is enhanced by the internal ramp signal
applied to the error amplifier. This scheme eliminates
regenerative “staircasing” of the inductor current, which
is otherwise a problem when in continuous current
mode with greater than 50% duty cycle.
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
MAX742
AGND
VREF
12/15
VREF
CC+FB+
12/15
SELECT
∑
PULSE
RAMP
OSC
SQUARE
∑
AV+100/200
MAX742
SOFT-START
AND THERMAL
SHUTDOWN
RQ
S
TO V+
S
RQ
CSH+
CSL+
V+
EXT+
GND
SS
PUMP
EXTPDRV
CSH-
CSL-
CC-FB-
Figure1. MAX742 Detailed Block Diagram
_______________Detailed Description
100kHz/200kHz Oscillator
The MAX742 oscillator frequency is generated without
external components and can be set at 100kHz or
200kHz by pin strapping. Operating the device at
100kHz results in lower supply current and improved
efficiency, particularly with light loads. However, component stresses increase and noise becomes more difficult to filter. For a given inductor value, the lower
operating frequency results in slightly higher peak currents in the inductor and switch transistor (see
Operating Characteristics
, Peak Inductor Current vs.
Load Current graph). When the lower frequency is used
in conjunction with an LC-type output filter (optional
components in Figure 2), larger component values are
required for equivalent filtering.
_______________________________________________________________________________________ 7
Typical
Charge-Pump Voltage Inverter
The charge-pump (PUMP) output is a rail-to-rail square
wave at half the oscillator frequency. The square wave
drives an external diode-capacitor circuit to generate a
negative DC voltage (Point A in Figure 2), which in turn
biases the inverting-output drive stage via PDRV. The
charge pump thus increases the gate-source voltage
applied to the external P-channel FET. The low onresistance resulting from increased gate drive ensures
high efficiency and guarantees start-up under heavy
loads. If a -5V to -8V supply is already available, it can
be tied directly to PDRV and all of the charge-pump
components removed. For input voltages greater than
8V, ground PDRV to prevent overvoltage. Observe
PDRV absolute maximum ratings.
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
VIN
4.5V to 6V*
L1
R1
MAX742
100Ω
100µH
D1
Q1
150µF
L3
25µH
C8
150µF
C9
C14
2.2µF
+VO
C1
0.1µF
1
C2
3.3nF
J1
C3
10µF
C4
C5
3.3nF
FB+
CC+
AGND
AV+
100/200
12/15
VREF
SS
CC-
FB-
MAX742
CSH+
CSL+
GND
EXT+
PUMP
PDRV
EXT-
CSH-
CSL-
R2
0.16Ω
NOTES:
Q1 = Motorola MTP15N05L
Q2 = Motorola MTP12P05
L1, L2 = MAXL001
C6
1µF
V+
D3
1µF
D4
100µH
POINT
A
C10
150µF
R3
0.1Ω
Q2
D2
L2
C11
150µF
C7
C8–C12 = MAXC001
D1, D2 = 1N5817
D3, D4 = Fuji ERA82-004 or 1N5817
R2, R3 = RCD RSF 1A Metal Film ±3%
L3, L4 = Wilco MFB 250
C13
0.1µF
DISC CERAMIC
C12
150µF
OPTIONAL
L4
25µH
-VO
C15
2.2µF
OPTIONAL
* FOR HIGHER INPUT VOLTAGE, SEE
SUPPLY-VOLTAGE RANGE
SECTION.
Figure 2. Standard 6W Application Circuit
8 _______________________________________________________________________________________
VIN
4.5V to 6V*
100Ω
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
MAX742
C13
330µF
R1
25µH
L1
D1
1N5820
C8
Q1
1000µF
+VO
C9
1000µF
C1
0.1µF
1
C2
6.8nF
J1
C3
10µF
C4
2.2µF
C5
6.8nF
FB+
CC+
AGND
AV+
100/200
12/15
VREF
SS
CC-
FB-
MAX742
CSH+
CSL+
GND
EXT+
PUMP
PDRV
EXT-
CSH-
CSL-
R2
0.02Ω
C6
1µF
V+
1N914
D3
1N914
C7
1µF
D4
25µH
C10
1000µF
R3
10V
0.02Ω
Q2
D2
L2
1N5820
NOTES:
Q1 = Motorola MTP25N06L
Q2 = International Rectifier IRF9Z30
L1, L2 = Gowanda 121AT2502VC
R2, R3 = KRL LB4-1 ±3%
C8–C13 = Nichicon PL Series (25V or 35V)
C14
0.1µF
DISC CERAMIC
C11
1000µF
C12
-VO
1000µF
* FOR HIGHER INPUT VOLTAGE, SEE
SUPPLY-VOLTAGE RANGE
SECTION.
Figure 3. High-Power 22W Application Circuit
_______________________________________________________________________________________ 9
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
Supply-Voltage Range
Although designed for operation from a +5V logic
supply, the MAX742 works well from 4.2V (the upper
limit of the undervoltage lockout threshold) to +10V
(absolute maximum rating plus a safety margin). The
upper limit can be further increased by limiting the
voltage at V+ with a zener shunt or series regulator.
To ensure AC stability, the inductor value should be
MAX742
scaled linearly with the nominal input voltage. For
example, if Figure 3’s application circuit is powered
from a nominal 9V source, the inductor value should be
increased to 40µH or 50µH. At high input voltages
(>8V), the charge pump can cause overvoltage at
PDRV. If the input can exceed 8V, ground PDRV and
remove the capacitors and diodes associated with the
charge pump.
In-Circuit Testing for
Guaranteed Performance
Figure 2’s circuit has been tested at all extremes of line,
load, and temperature. Refer to the
Characteristics
table for guaranteed in-circuit specifica-
Electrical
tions. Successful use of this circuit requires no component calculations.
Soft-Start
A capacitor connected between Soft-Start (SS) and
ground limits surge currents at power-up. As shown in
the
Typical Operating Characteristics
, the peak switch
current limit is a function of the voltage at SS. SS is
internally connected to a 5µA current source and is
diode-clamped to 2.6V (Figure 8). Soft-start timing is
therefore set by the SS capacitor value. As the SS voltage ramps up, peak inductor currents rise until they
reach normal operating levels. Typical values for the SS
capacitor, when it is required at all, are in the range of
1µF to 10µF.
Fault Conditions Enabling SS Reset
In addition to power-up, the soft-start function is enabled
by a variety of fault conditions. Any of the following conditions will cause an internal pull-down transistor to discharge the SS capacitor, triggering a soft-start cycle:
Undervoltage lockout
Thermal shutdown
VREF shorted to ground or supply
VREF losing regulation
EXTERNAL
SS
CAPACITOR
Figure 4. Soft-Start Equivalent Circuit
__________________Design Procedure
An exact inductor value isn’t critical. The inductor value
can be varied in order to make tradeoffs between
noise, efficiency, and component sizes. Higher inductor
values result in continuous-conduction operation, which
maximizes efficiency and minimizes noise. Physically
smallest inductors (where E = 1/2 LI2is minimum) are
realized when operating at the crossover point between
continuous and discontinuous modes. Lowering the
inductor value further still results in discontinuous current even at full load, which minimizes the output
capacitor size required for AC stability by eliminating
the right-half-plane zero found in boost and inverting
topologies. Ideal current-mode slope compensation
where m = 2 x V/L is achieved if L (Henries) = R
(Ω) x 0.001, but again the exact value isn’t critical and
the inductor value can be adjusted freely to improve
AC performance. The following equations are given for
continuous-conduction operation since the MAX742 is
mainly intended for low-noise analog power supplies.
See Appendix A in Maxim’s
DC-DC Converter Circuit Collection
and discontinuous-mode equations.
Boost (positive) output:
L = ———————————————
Inverting (negative) output:
L = —————————————
+5V
SS
8
N
(VIN- VSW)2(V
(V
+ VD)2(I
OUT
(V
IN
(V
+ VD)(I
OUT
5µA
MAX742
+2V
REFERENCE
TO CURRENT–
LIMIT COMPARATOR
FAULT
Inductor Value
Battery Management and
for crossover point
+ VD- VIN)
OUT
)(F)(LIR)
LOAD
2
- VSW)
)(F)(LIR)
LOAD
SENSE
10 ______________________________________________________________________________________
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
where:
VSWis the voltage drop across the the switch transistor
and current-sense resistor in the on state (0.3V typ).
VDis the rectifier forward voltage drop (0.4V typ).
LIR is the ratio of peak-to-peak ripple current to DC
offset current in the inductor (0.5 typ).
Current-Sense Resistor Value
The current-sense resistor values are calculated according to the worst-case-low current-limit threshold voltage
from the
inductor current. The peak inductor current calculations
that follow are also useful for sizing the switches and
specifying the inductor current saturation ratings.
Electrical Characteristics
R
SENSE
+I
+I
PEAK
(boost) = ————————— +
PEAK
(VIN- VSW) (V
—————————————
(2)(F)(L)(V
(inverting) = ———————————— +
(VIN- VSW) (V
—————————————
(2)(F)(L) (V
150mV
= ————
I
PEAK
I
LOAD(VOUT
VIN- V
+ VD- VIN)
OUT
+ VD)
OUT
I
LOAD(VOUT
VIN- V
+ VD+ VIN)
OUT
+ VD)
OUT
table and the peak
+ VD)
SW
+ VD+ VIN)
SW
Filter Capacitor Value
The output filter capacitor values are generally determined by the effective series resistance (ESR) and voltage rating requirements rather than actual capacitance
requirements for loop stability. In other words, the
capacitor that meets the ESR requirement for noise purposes nearly always has much more output capacitance than is required for AC stability. Output voltage
noise is dominated by ESR and can be roughly calculated by an Ohm’s Law equation:
V
where V
Ensure the output capacitors selected meet the follow-
ing minimum capacitance requirements:
Minimum CF = 60µF per output or the following, whichev-
er is greater:
NOISE
CF = 0.015/R
CF = 0.01/R
(peak-to-peak) = I
NOISE
is typically 0.15V.
LOAD
LOAD
x R
PEAK
(in Farads, ±15V mode)
(in Farads, ±12V mode)
ESR
Compensation Capacitor (CC) Value
The compensation capacitors (CC+ and CC-) cancel
the zero introduced by the output filter capacitors’ ESR,
improving phase margin, and AC stability. The compensation poles set by CC+ and CC- should be set to
match the ESR zero frequencies of the output filter
capacitors according to the following:
R
x CF
CC (in Farads) = —————— (use 1000pF minimum)
ESR
10kΩ
Standard 6W Application
The 6W supply (Figure 2) generates ±200mA at ±15V,
or ±250mA at ±12V. Output capability is increased to
10W or more by heatsinking the power FETs, using
cores with higher current capability (such as Gowanda
#050AT1003), and using higher filter capacitance.
Ferrite and MPP inductor cores optimize efficiency and
size. Iron-power toroids designed for high frequencies
are economical, but larger.
Ripple is directly proportional to filter capacitor equivalent series resistance (ESR). In addition, about 250mV
transient noise occurs at the LX switch transitions. A
very short scope probe ground lead or a shielded
enclosure is need for making accurate measurements
of transient noise. Extra filtering, as shown in Figure 2,
reduces both noise components.
High-Power 22W Application
The 22W application circuit (Figure 3) generates ±15V
at ±750mA or ±12V at ±950mA. Noninductive wirewound resistors with Kelvin current-sensing connections replace the metal-film resistors of the previous
(6W) circuit. Gate drive for the P-channel FET is bootstrapped from the negative supply via diode D6. The
2.7V zener (D5) is required in 15V mode to prevent
overvoltage. The charge pump (D3, D4, and C6) may
not be necessary if the circuit is lightly loaded
(<100mA) on start-up. AIE part #415-0963 is a ferrite
pot-core inductor that can be used in place of a smaller, more expensive moly-permalloy toroid inductor (L1,
L2). Higher efficiencies can be achieved by adding
extra MOSFETs in parallel. Load levels above 10W
make it necessary to add heatsinks, especially to the Pchannel FET.
MAX742
______________________________________________________________________________________ 11
Switch-Mode Regulator with
+5V to ±12V or ±15V Dual Output
Table 1. Trouble-Shooting Chart
SYMPTOM CORRECTION
Unstable Output.
Noise or jitter on
output ripple
waveform. Scope
may not trigger
MAX742
correctly.
Noisy Output.
Switching is
steady, but large
inductive spikes
are seen at the
outputs.
Self-Destruction.
Transistors or IC
die on power-up.
Poor Efficiency.
Supply current is
high. Output will
not drive heavy
loads.
No Output. +VO
= 5V or less. -VO
= 0V.
No Switching.
±VO are correct,
but no waveform is
seen at LX+ or LX-.
Loop stability problem.
A. CC+ or CC- disconnected.
B. EMI: Move inductor away from IC or use
shielded inductors. Keep noise sources
away from CC- and CC+.
C. Grounding: Tie AGND directly to the filter
capacitor ground lead. Ensure that current spikes from GND do not cause noise
at AGND or compensation capacitor or
reference bypass ground leads. Use wide
PC traces or a ground plane.
D. Bypass: Tie 10µF or larger between AGND
and VREF. Use 150µF to bypass the input
right at AV+. If there is high source resistance, 1000µF or more may be required.
E. Current limiting: Reduce load currents.
Ensure that inductors are not saturating.
F. Slope compensation: Inductor value not
matched to sense resistor.
A. Ground noise: Probe ground is picking up
switching EMI. Reduce probe ground lead
length (use probe tip shield) or put circuit
in shielded enclosure.
B. Poor HF response: Add ceramic or
tantalum capacitors in parallel with output
filter capacitors.
A. Input overvoltage: Never apply more
than +12V.
B. FB+ or FB- disconnected or shorted. This
causes runaway and output overvoltage.
C. CC+ or CC- shorted.
D. Output filter capacitor disconnected.
A. Inductor saturation: Peak currents
exceed coil ratings.
B. MOSFET on-resistance too high.
C. Switching losses: Diode is slow or has high
forward voltage. Inductor has high DC resis-
tance. Excess capacitance at LX nodes.
D. Inductor core losses: Hysteresis losses
cause self-heating in some core materials.
E. Loop instability: See Unstable Output
above.
A. Check connections. VREF should be +2V.
B. When input voltage is less than +4.2V,
undervoltage lockout is enabled.
Output is unloaded. Apply ±30mA or
greater load to observe waveform.
___________________Chip Topography
CSH+ CSL+
FB-
0.080"
(2.03mm)
GND
EXT+
PUMP
0.135"
(3.45mm)
PDRV
EXT-
V+
CSH-
CSL- CC-
AV+
100/200
12/15
VREF
AGND
SS
CC+ FB+
TRANSISTOR COUNT: 375
SUBSTRATE CONNECTED TO V+
12 ______________________________________________________________________________________
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