Rainbow Electronics MAX1623 User Manual

MAX1623
3A, Low-Voltage, Step-Down Regulator with
Synchronous Rectification and Internal Switches
________________________________________________________________ Maxim Integrated Products 1
EVALUATION KIT MANUAL
AVAILABLE
General Description
The MAX1623 features constant-off-time, current-mode pulse-width-modulation (PWM) control with switching frequencies as high as 350kHz. An external resistor at the TOFF pin sets the off-time, allowing optimum design flexibility in terms of switching frequency, output switch­ing noise, and inductor size. This device is available in a space-saving 20-pin SSOP package.
________________________Applications
5V to 3.3V Conversion
Notebook Computer CPU I/O Supply
Desktop Computer Bus-Termination Supply
CPU Daughter Card Supply
DSP Supply
____________________________Features
±1% Output Accuracy, Including Line and Load
Regulation
94% Efficiency
Internal Switches
55mPMOS Power Switch 60mNMOS Synchronous-Rectifier Switch
Guaranteed 3A Load Capability
Minimal External Components
Pin-Selectable Fixed 3.3V, 2.5V, or
Adjustable (1.1V to 3.8V) Output Voltage
4.5V to 5.5V Input Voltage Range
400µA (typ) Supply Current
<1µA Shutdown Supply Current
Constant-Off-Time PWM Operation
Switching Frequencies Up to 350kHz
Idle ModeOperation at Light Loads
Thermal Shutdown ProtectionAvailable in 20-Pin SSOP
20
19
18
17
16
15
14
13
1
2
3
4
5
6
7
8
LX
PGND
LX
PGND
IN
LX
IN
LX
TOP VIEW
LX
PGND
V
CC
COMPFBSEL
IN
LX
12
11
9
10
REF
GNDFB
TOFF
MAX1623
SSOP
SHDN
Pin Configuration
5V
INPUT
MAX1623
2.5V
OUTPUT
IN LX
PGND
GND
FB
REFCOMP
FBSEL
V
CC
TOFF
SHDN
Typical Operating Circuit
19-1436; Rev 2; 3/02
PART
MAX1623EAP -40°C to +85°C
TEMP RANGE PIN-PACKAGE
20 SSOP
Ordering Information
Idle Mode is a trademark of Maxim Integrated Products.
For pricing, delivery, and ordering information, please contact Maxim/Dallas Direct! at 1-888-629-4642, or visit Maxim’s website at www.maxim-ic.com.
MAX1623
3A, Low-Voltage, Step-Down Regulator with Synchronous Rectification and Internal Switches
2 _______________________________________________________________________________________
ABSOLUTE MAXIMUM RATINGS
ELECTRICAL CHARACTERISTICS
(VIN= VCC= 5V, FBSEL unconnected, R
TOFF
= 110kΩ, TA= 0°C to +85°C, unless otherwise noted. Typical values are at
T
A
= +25°C.)
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
IN to PGND .....................................................................0V to 6V
V
CC
to GND ................................................................-0.3V to 6V
PGND to GND.....................................................................±0.5V
IN to V
CC
.............................................................................±0.5V
LX Current (Note 1).............................................................±5.5A
SHDN to GND .............................................................-0.3V to 6V
REF, FBSEL, COMP, FB, TOFF to GND .....-0.3V to (V
CC
+ 0.3V)
REF Short to GND ......................................................Continuous
Continuous Power Dissipation (T
A
= +70°C) (with part mounted on 1 sq. inch of one ounce copper)
20-Pin SSOP (derate 22mW/°C above +70°C) ................1.3W
Operating Temperature Range ...........................-40°C to +85°C
Storage Temperature Range .............................-65°C to +150°C
Lead Temperature (soldering, 10s) .................................+300°C
SHDN = GND or V
CC
FBSEL = REF
FBSEL = GND
VIN= 4.5V to 5.5V, I
LOAD
= 0 to 3A
(Note 2)
FBSEL = GND, adjustable output mode, VFB= 1.2V
VCCfalling, 100mV hysteresis
I
LOAD
1.5A (Note 2)
VIN= 4.5V
SHDN = GND
VIN= 4.5V
FBSEL = GND or REF (Note 2)
I
REF
= 0
Does not include switching losses
I
REF
= -1µA to 10µA
CONDITIONS
V0.8
SHDN Input Low Voltage
µA-1 0.03 1
SHDN Input Current
2
%
1
AC Output Load Regulation
µs0.85 1.00 1.15Off-Time Default Period
µs0.5 4Off-Time Adjustment Range
kHz500Error-Amplifier Gain Bandwidth
nA-25 25FB Input Bias Current
V4.1 4.2 4.3Undervoltage Lockout Threshold
°C145Thermal Shutdown Threshold
µA0.5 10Shutdown Supply Current
µA400 525No-Load Supply Current
A1 1.25 1.5Idle Mode Threshold (Note 3)
2.49 2.525 2.550
V
3.296 3.330 3.366
V4.5 5.5Input Voltage Range
Output Voltage
kHz350Maximum Switching Frequency
m60 100NMOS Switch On-Resistance
m55 100PMOS Switch On-Resistance
A3.65 4.65Current-Limit Threshold
1.089 1.100 1.110
VV
REF
3.80Output Adjustment Range
V1.089 1.100 1.110Reference Output Voltage
mV1Reference Load Regulation
UNITSMIN TYP MAXPARAMETER
FBSEL = unconnected
FBSEL = V
CC
FBSEL = GND or REF
V2
SHDN Input High Voltage
VIN= 5.5V, VLX= 5.5V or 0 µA±20LX Leakage Current
A3.65RMS LX Output Current
Note 1: LX has internal clamp diodes to PGND and IN. Applications that forward bias these diodes should take care not to exceed
the IC’s package power dissipation limits.
MAX1623
_______________________________________________________________________________________ 3
3A, Low-Voltage, Step-Down Regulator with
Synchronous Rectification and Internal Switches
ELECTRICAL CHARACTERISTICS
(VIN= VCC= 5V, FBSEL unconnected, R
TOFF
= 110k, TA= -40°C to +85°C, unless otherwise noted.) (Note 4)
Note 2: Guaranteed by design, not production tested. Note 3: Idle Mode threshold is defined as the transition point in the load-current range between Idle Mode and constant-off-time
operation.
Note 4: Specifications to -40°C are guaranteed by design, not production tested.
SHDN = GND or V
CC
VIN= 4.5V to 5.5V, I
LOAD
= 0 to 3A
FBSEL = GND, adjustable output mode, VFB= 1.2V
VCCfalling, 100mV hysteresis
VIN= 4.5V
VIN= 5.5V, VLX= 5.5V or 0
SHDN = GND
VIN= 4.5V
V
FBSEL = GND or REF (Note 2)
I
REF
= 0
Does not include switching losses
CONDITIONS
V0.8
FBSEL = unconnected
SHDN Input Low Voltage
µA-1 1
FBSEL = V
CC
SHDN Input Current
FBSEL = GND or REF
2.2
SHDN Input High Voltage
µs0.85 1.25Off-Time Default Period
µs0.55 4Off-Time Adjustment Range
nA-50 50FB Input Bias Current
V4.0 4.3Undervoltage Lockout Threshold
µA-20 20LX Leakage Current
µA10Shutdown Supply Current
µA600No-Load Supply Current
2.450 2.550
V
3.234 3.366
V4.5 5.5Input Voltage Range
Output Voltage
0.1NMOS Switch On-Resistance
0.1PMOS Switch On-Resistance
A3.5 4.75Current-Limit Threshold
1.075 1.110
VV
REF
3.8Output Adjustment Range
V1.075 1.110Reference Output Voltage
UNITSMIN TYP MAXPARAMETER
MAX1623
3A, Low-Voltage, Step-Down Regulator with Synchronous Rectification and Internal Switches
4 _______________________________________________________________________________________
__________________________________________Typical Operating Characteristics
(Circuit of Figure 2, TA = +25°C, unless otherwise noted.)
100
0
0.001 0.1 10.01 10
EFFICIENCY
vs. OUTPUT CURRENT
20
MAX1623 TOC01
OUTPUT CURRENT (A)
EFFICIENCY (%)
40
60
80
90
10
30
50
70
V
OUT
= 3.3V, R
TOFF
= 110k
V
OUT
= 1.1V, R
TOFF
= 280k
V
OUT
= 2.5V, R
TOFF
= 180k
0
1
3
2
4
5
0 200100 300 400 500 600
SWITCH OFF-TIME
vs. OFF-TIME RESISTANCE
MAX1623 TOC02
R
TOFF
(k)
t
OFF
(µs)
1000
100
10
1
0.1
0.01 0123
4
56
SUPPLY CURRENT
vs. INPUT VOLTAGE
MAX1623 TOC03
INPUT VOLTAGE (V)
SUPPLY CURRENT (µA)
SHDN = IN
SHDN = GND
0
150
50
100
250
200
350
300
0 1000 1500500 2000 2500 3000
SWITCHING FREQUENCY
vs. LOAD CURRENT
MAX1623 TOC04
LOAD CURRENT (mA)
SWITCHING FREQUENCY (kHz)
V
OUT
= 2.5V, R
TOFF
= 180k
V
OUT
= 3.3V, R
TOFF
= 110k
V
OUT
= 1.1V, R
TOFF
= 280k
0
200
150
100
50
300
250
350
400
4.5 4.94.7 5.1 5.3 5.5
SWITCHING FREQUENCY
vs. INPUT VOLTAGE
MAX1623 TOC05
INPUT VOLTAGE (V)
SWITCHING FREQUENCY (kHz)
VIN = 5V, V
OUT
= 3.3V,
R
TOFF
= 110k
VIN = 5V, V
OUT
= 2.5V,
R
TOFF
= 180k
0
-0.50
0.10.01 10.001 10
LOAD REGULATION ERROR
vs. LOAD CURRENT
-0.40
MAX1623 TOC07
LOAD CURRENT (A)
LOAD REGULATION ERROR (%)
-0.30
-0.20
-0.10
-0.35
-0.45
-0.25
-0.15
-0.05
V
OUT
= 2.5V, R
TOFF
= 180k
V
OUT
= 3.3V, R
TOFF
= 110k
-0.01
-0.02
-0.03
-0.04
-0.05
-0.06
0
0 5 10 15 20 25
REFERENCE LOAD REGULATION ERROR
vs. REFERENCE LOAD CURRENT
MAX1623 TOC06
REFERENCE LOAD CURRENT (µA)
REFERENCE LOAD REGULATION ERROR (%)
TA = +25°C
T
A
= -40°C
T
A
= +85°C
MAX1623
_______________________________________________________________________________________ 5
3A, Low-Voltage, Step-Down Regulator with
Synchronous Rectification and Internal Switches
B
C
A
1ms/div
START-UP AND SHUTDOWN TRANSIENT
MAX1623 TOC08
VIN = 5V, V
OUT
= 3.3V, I
LOAD
= 3A, WAVEFORM AVERAGED A: V
OUT
, 2V/div
B: I
IN
, 1A/div
C: V
SHDN
, 5V/div
LOAD-TRANSIENT RESPONSE
(FBSEL = REF)
MAX1623 TOC10
I
LOAD
0 to 3A
V
OUT
50mV
AC-COUPLED
f = 300kHz
20µs/div
LINE-TRANSIENT RESPONSE
MAX1623 TOC12
VIN = 4.5V
to 5.5V
AC-COUPLED
(1V/div)
V
OUT
= 3.3V
AC-COUPLED
I
OUT
= 1.5A
(20mV/div)
20µs/div
LOAD-TRANSIENT RESPONSE
(FBSEL = REF)
MAX1623 TOC11
I
LOAD
0 to 2A
V
OUT
50mV
AC-COUPLED
f = 300kHz
20µs/div
____________________________ Typical Operating Characteristics (continued)
(Circuit of Figure 2, TA = +25°C, unless otherwise noted.)
LINE-TRANSIENT RESPONSE
MAX1623 TOC13
VIN = 4.5V
to 5.5V
AC-COUPLED
(1V/div)
V
OUT
= 3.3V AC-COUPLED I
OUT
= 100mA
(20mV/div)
20µs/div
B
C
A
1ms/div
START-UP AND SHUTDOWN TRANSIENT
MAX1623 TOC09
VIN = 5V, V
OUT
= 3.3V, I
LOAD
= 2A, WAVEFORM AVERAGED A: V
OUT
, 2V/div
B: I
IN
, 1A/div
C: V
SHDN
, 5V/div
MAX1623
3A, Low-Voltage, Step-Down Regulator with Synchronous Rectification and Internal Switches
6 _______________________________________________________________________________________
General Description
The MAX1623 current-mode, PWM, DC-DC regulator is designed for 5V-input step-down applications. It fea­tures a 55m(typ) PMOS switch and a 60mΩ (typ) NMOS synchronous-rectifier switch. Simple constant-off­time control allows switching frequencies up to 350kHz. Adjust the off-time with an external resistor R
TOFF
to optimize performance trade-offs among efficiency, com­ponent size, output switching noise, and cost. Idle Mode operation enhances light-load efficiency by switching to a pulse-skipping mode that reduces transition and gate­charge losses. The power-switching circuit consists of the IC and an LC output filter. The output voltage is the average of the AC voltage at the switching node (LX). The MAX1623 regulates the output voltage by changing the PMOS switch on-time relative to the constant off­time, thereby adjusting the duty cycle.
The MAX1623 contains six major circuit blocks (Figure 1): a PWM comparator, a current-sense circuit, a PWM logic block, an internal feedback mux, an off-time con­trol block, and a 1.1V precision reference. The input supply directly powers the internal blocks.
Modes of Operation
The load current determines the mode of operation: Idle Mode (load currents less than 0.625A) or PWM mode for inductor currents of 1.25A (which corre­sponds to load currents greater than 0.625A). The PWM current limit is continuously adjusted by the PWM comparator and can vary from 0A to the maximum cur­rent limit (4A). If the inductor current falls below the Idle Mode threshold (1.25A), skip mode takes over. Whenever the P-channel switch turns on, it stays on until the sensed current reaches the active current limit. The PWM current limit automatically adjusts with the PMOS switch duty cycle required to generate the desired output voltage. When the active current limit is met, the PMOS switch turns off for the programmed minimum off-time, and the N-channel synchronous rec­tifier turns on. The synchronous rectifier stays on until the P-channel switch turns back on or until the inductor current reaches zero. At the end of the off-time, the P­channel switch turns on again if the output voltage indi­cates that energy is required at the output.
Pin Description
NAME FUNCTION
1, 3, 5,
16,18, 20
LX Connection to the internal power switches.
2, 4, 6 IN Power Input. Internally connected to the PMOS switch source. Connect to 5V.
PIN
7
SHDN
Active-Low Shutdown Input. Connect to VCCfor normal operation.
8 FBSEL Feedback Select Input. See Table 1.
12 REF Reference Output. Bypass with a minimum 0.1µF capacitor to GND. See the Internal Reference section.
11 GND Analog Ground
10 FB
Feedback input for both fixed-output and adjustable operating modes. Connect to the output directly for fixed-voltage operation or to a resistor-divider for adjustable operating modes.
9 TOFF
Off-Time Select Input. Connect a resistor from TOFF to GND to adjust the switch off-time, and there­fore the frequency: t
OFF
= . See the Typical Operating Characteristics.
15, 17, 19 PGND Power Ground. Internally connected to the NMOS synchronous rectifier source.
14 V
CC
Analog Supply-Voltage Input. Supplies internal analog circuitry. Connect to 5V. Bypass VCCwith 10 and 4.7µF (Figure 2).
13 COMP
Integrator Capacitor Connection. Connect a 470pF (470pF to 2000pF range) capacitor to GND to set the typical integration time-constant. See the Integrator Amplifier section.
R
110k
s)
TOFF
MAX1623
_______________________________________________________________________________________ 7
3A, Low-Voltage, Step-Down Regulator with
Synchronous Rectification and Internal Switches
Figure 1. Functional Diagram
Idle Mode
At light loads, the device goes into skip mode (because the load current is below the skip threshold), and Idle Mode operation (1.25A current limit) begins. This allows both switches to remain off at the end of the off-time, skipping cycles to reduce switching losses. At lighter loads, the inductor current is discontinuous because the inductor current reaches zero. In Idle Mode, the operating frequency varies with output load current. There is no major shift in circuit behavior as the PWM limit falls below the skip limit. The effective off­time simply increases, resulting in a seamless transition between PWM mode and Idle Mode.
PWM Mode
PWM operation occurs whenever the load current is greater than the skip threshold. In this mode, the PWM comparator adjusts the current limit to the desired out­put current, so that the P-channel turns on at the end of each off-time.
Three signals are resistively summed at the input of the PWM comparator (Figure 1): an output voltage error signal relative to the reference voltage, an integrated output voltage error correction signal, and the sensed
PMOS switch current. The integrated error signal is provided by a transconductance amplifier with an external capacitor at the COMP pin. This integrator pro­vides high DC accuracy without the need for a high­gain error amplifier. Connecting a capacitor at COMP modifies the overall loop response (see the Integrator Comparator section).
Setting the Output Voltage
There are two preset output voltages (2.525V and
3.33V), or the output voltage can be adjusted from the reference voltage (nominally 1.1V) up to 3.8V. For a preset output voltage (Figure 2), connect FB to the out­put voltage, and connect FBSEL to VCC(2.525V out­put) or leave it unconnected (3.33V output). For an adjustable output, connect FBSEL to GND or REF, and connect FB to the midpoint of a resistor divider between the output voltage and ground (Figure 3). Regulation is maintained when V
FB
equals V
REF
. Select
R1 in the 10kto 500krange. R2 is given by:
where V
REF
is typically 1.1V.
V
IN
4.5V TO
5.5V
FBSEL
FEEDBACK
SELECTION
IN
FB
COMP
V
IN
NOTE: HEAVY LINES DENOTE HIGH SWITCHING CURRENT PATHS.
V
SHDN
REF
CC
REF
G
m
REF
MAX1623
REF
GND
CURRENT
SENSE
SKIP
PWM LOGIC
AND
DRIVERS
LX
TIMER
TOFF
CURRENT
SENSE
PGND
R2 (R1)(V / V 1)
=−
OUT REF
MAX1623
3A, Low-Voltage, Step-Down Regulator with Synchronous Rectification and Internal Switches
8 _______________________________________________________________________________________
Setting the AC Loop Gain
The internal integrator amplifier effectively eliminates any long-term error within the time constant set by the Gmof the transconductance amplifier and the capacitor con­nected to COMP. However, there remains a short-term load-regulation error in response to load current changes. Proper FBSEL connection selects the relative level of current feedback to voltage feedback, which results in an AC load-regulation error of either 1% or 2% of the output voltage (Table 1). The 2% setting is auto­matically selected in preset output voltage mode (FBSEL connected to VCCor unconnected). This gain setting minimizes the size and cost of the output filter capacitor required. For extremely tight specifications that cannot tolerate 2% short-term errors, connect FBSEL to ground (adjustable mode) for 1% AC load regulation (see the Input and Output Filter Capacitors (C1, C2) section).
Synchronous Rectification
Synchronous rectification improves efficiency by 3% to 5% at heavy loads when compared to a conventional Schottky rectifier. To prevent cross-conduction or “shoot­through,” the synchronous rectifier turns on following a short delay (dead time) after the P-channel power MOS­FET turns off. In discontinuous (light-load) mode, the syn­chronous rectifier switch turns off as the inductor current approaches zero. The synchronous rectifier works under all operating conditions, including Idle Mode.
Integrator Amplifier (COMP)
An internal transconductance amplifier fine tunes the output DC accuracy. The transconductance amplifier is compensated at COMP. A capacitor from COMP to ground determines the gain-bandwidth product and the overall loop response. This integrator effectively elimi­nates any long-term error within the time constant set by the G
m
of the transconductance amplifier and the
capacitor connected to COMP.
For stability, choose COMP as follows:
where G
m
= 9.1µS.
AC LOAD
REGULATION (%)
OUTPUT
VOLTAGE (V)
IN 2 2.525
Unconnected 2 3.33
FBSEL PIN
GND 1 Adjustable
V
REF
2 Adjustable
Figure 2. Standard 3.3V/3A Application Circuit
Table 1. Output Voltage Selection
INPUT
4.5V TO 5.5V
IN
10µF
4.7µH
220µF
3.3V OUTPUT
C1
C2 330µF
LX
MAX1623
PGND
10
NOTE: HEAVY LINES DENOTE HIGH SWITCHING CURRENT PATHS.
4.7µF
SHDN
FBSEL
V
CC
FB
TOFF
COMP
REF
GND
0.1µF
110k
470pF
C
COMP
G R C
××
m LOAD OUT
4
A high capacitor value maintains a constant average output voltage but slows the loop response to changes in output voltage. A low capacitor value speeds up the loop response to changes in output voltage. Choose the capacitor value that results in optimal performance.
Current Limiting
The current-sense circuit enables when the PMOS power switch is on. This circuit’s corresponding output voltage feeds three separate comparators: the skip cur­rent comparator (1.25A), the maximum current com­parator (4.15A), and the PWM current comparator (see the Modes of Operation section).
Oscillator Frequency and
Programming the Off-Time
The MAX1623 features a programmable off-time that is set by R
TOFF
connected from TOFF to GND. Connecting
a 110kresistor from TOFF to GND achieves a 1µs (nominal) off-time. The off-time is inversely proportional to R
TOFF
according to the formula:
t
OFF
= R
TOFF
/ 110k (µs)
t
OFF
is adjustable between 0.5µs to 4µs (see the Typical Operating Characteristics). To set the switching frequency when the inductor operates in continuous­conduction mode, the off-time has to be set to:
where:
t
OFF
= the programmed off-time
VI= input voltage
VO= output voltage
f = desired switching frequency during continuous
inductor current
V
PCH
= the voltage drop across the internal P-channel
switch
V
NCH
= the voltage drop across the internal N-channel
synchronous rectifier
Switching frequency decreases as load current is decreased below the 625mA Idle Mode trip point.
Internal Reference
The 1.10V internal reference (available at REF) is accu­rate to ±1.5% over the -40°C to +85°C operating range, making it useful as a precision system reference. Bypass the reference to ground with a minimum 0.1µF ceramic capacitor. For low noise and jitter performance, use a
0.47µF ceramic capacitor. The reference can supply up to 10µA for external loads. However, if tight accuracy specifications for either reference or the main output are essential, avoid reference loads in excess of 5µA. Loading the reference reduces the main output voltage slightly, according to the reference-voltage load-regula­tion error.
Start-Up
To prevent the MAX1623 from false output regulation, the internal PMOS and NMOS switches will not switch on until all of the following conditions are true: the sup­ply voltage is above the undervoltage lockout thresh­old, SHDN is pulled high, the internal reference voltage is at 75% of its nominal (1.1V) value, and the die tem­perature is below +145°C. When the above conditions are satisfied, the MAX1623 will regulate the output volt­age to the selected level. The MAX1623 typically starts up in 1ms for full output load.
Thermal Shutdown and
Overload Conditions
Thermal overload protection limits the MAX1623’s total power dissipation. When the junction temperature reaches T
j
= +145°C, the device turns off, allowing it to cool down. Switching resumes after the IC’s junction temperature decreases by 20°C. If the thermal overload condition persists, the output pulses on and off.
Thermal overload protection is designed to protect the MAX1623 during fault conditions, such as an output short circuit.
Thermal Resistance
Junction to ambient thermal resistance (θJA) strongly depends on the amount of copper area immediately surrounding the IC’s leads. The MAX1623 evaluation kit has 0.8in2of copper area. θJAon this board was mea­sured to have 45°C/W of thermal resistance with no air
MAX1623
_______________________________________________________________________________________ 9
3A, Low-Voltage, Step-Down Regulator with
Synchronous Rectification and Internal Switches
Figure 3. Adjustable Output Voltage
LX
MAX1623
PGND
GND
FB
R1 = 10k to 500k R2 = R1(V
OUT
= 1.1V
V
REF
/ V
- 1)
REF
V
OUT
R2
R1
t
=
OFF
−−
VV V
I O PCH
fV V V
( )
I PCH NCH
+
MAX1623
3A, Low-Voltage, Step-Down Regulator with Synchronous Rectification and Internal Switches
10 _______________________________________________________________________________________
flow. A copper area of 0.4in2showed thermal resis­tance of 60°C/W.
Airflow over the IC can significantly reduce θJA.
Power Dissipation
The MAX1623’s power dissipation consists mostly of con­duction losses in the two internal power switches. Power dissipation due to supply current in the control section and average current used to charge and discharge the gate capacitance of the two power switches is less than 30mW at 300kHz. This number is reduced when switch­ing frequency is reduced as the part enters Idle Mode.
Combined conduction loss in the two power switches is calculated by:
PD= I
LOAD
2
(RON)
where RON= 100m(max). The θJArequired to deliver this amount of power is cal-
culated by:
θJA= (T
J(MAX)
– T
A(MAX)
) / P
D
where:
T
J(MAX)
= maximum allowed junction temperature
T
A(MAX)
= maximum ambient temperature expected
Applications Information
Inductor L1
The inductor value can be adjusted to optimize the design for size, cost, and efficiency. Three key inductor parameters must be specified: inductance value (L), peak current (I
PEAK
), and DC resistance (RDC). The fol­lowing equation includes a constant, denoted as LIR, which is the ratio of inductor peak-to-peak AC current to DC load current. A higher value of LIR allows smaller inductance, but results in higher losses and ripple. A good compromise between size and losses is found at a 30% ripple current to load current ratio (LIR = 0.3), which corresponds to a peak inductor current 1.15 times the DC load current:
where:
f = switching frequency
I
OUT
= maximum DC load current
LIR = ratio of AC to DC inductor current, typically
0.3
The peak inductor current at full load is 1.15 x I
OUT
if the above equation is used; otherwise, the peak current can be calculated by:
The inductor’s DC resistance is a key parameter for effi­ciency and must be minimized, preferably to less than 25mat I
OUT
= 3A. To reduce EMI, use a shielded
inductor.
Input and Output Filter
Capacitors (C1, C2)
Use a low-ESR input capacitor according to the input ripple-current requirements and voltage rating.
In addition to C1, place a 10µF ceramic bypass capacitor from the power input (pin 2, 4, 6) to power ground (pin 15, 17, 19) within 5mm of the IC.
The output filter capacitor determines the output volt­age ripple and output load-transient response, as well as the loop’s stability.
The output ripple in continuous-conduction mode is:
where f is the switching frequency.
Table 2. Suggested Values (VIN= 5V, IO= 3A, f = 300kHz)
T
OFF
(µs)
L
(µH)
3.3 1.10 4.7
2.5 1.67 4.7
V
OUT
(V)
1.8 2.16 4.7
1.5 2.38 3.9
1.1 2.68 3.3
R
TOFF
(k)
120
180
240
260
280
L
V(V V)
OUT IN(MAX) OUT
=
V f (I ) (LIR)
IN(MAX) OUT
××
V(V V)
II
=+
PEAK OUT
OUT IN(MAX) OUT
2 f L V
II
RIPPLE LOAD
=
 
V I LIR ESR
OUT(RPL) OUT(MAX) C2
=× +
×× ×
IN(MAX)
××
π
 
1
 
VVV
()
OUT IN OUT
V
IN
 
2 f C2
Loop Stability
Stable operation requires the right output filter capaci­tor. When choosing the output capacitor, ensure the fol­lowing conditions are met:
and
10mΩ≤R
ESR
Circuit Layout and Grounding
Good layout is necessary to achieve the intended out­put power level, high efficiency, and low noise. Good layout includes the use of a ground plane, appropriate component placement, and correct routing of traces using appropriate trace widths. For heatsinking purpos­es, copper area connected at the IC should be evenly distributed among the high-current pins.
1) Minimize high-current ground loops. Connect the input capacitor’s ground, output capacitor’s ground, and IC PGND together.
2) A ground plane is essential for optimum perfor­mance. In most applications, the circuit will be located on a multilayer board, and full use of the four or more copper layers is recommended. Use the top and bottom layers for interconnections and the inner layers for an uninterrupted ground plane.
3) Place the LX node components as close together as possible. This reduces resistive and switching losses and confines noise due to ground induc­tance.
4) Connect the input filter capacitor less than 10mm away from IN. The connecting copper trace carries large currents and must be at least 2mm wide, preferably 5mm.
5) Connect GND directly to PGND at only one point near the IC.
MAX1623
______________________________________________________________________________________ 11
3A, Low-Voltage, Step-Down Regulator with
Synchronous Rectification and Internal Switches
___________________Chip Information
TRANSISTOR COUNT: 1220
C80t
≥× ×
2 OFF
V V
OUT
REF
MAX1623
3A, Low-Voltage, Step-Down Regulator with Synchronous Rectification and Internal Switches
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
12 ____________________Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600
© 2002 Maxim Integrated Products Printed USA is a registered trademark of Maxim Integrated Products.
Package Information
(The package drawing(s) in this data sheet may not reflect the most current specifications. For the latest package outline information, go to www.maxim-ic.com/packages.)
SSOP.EPS
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