November 2003
ADC08060
8-Bit, 20 MSPS to 60 MSPS, 1.3 mW/MSPS A/D Converter
ADC08060 8-Bit, 60 MSPS, 1.3 mW/MSPS A/D Converter
General Description
The ADC08060 is a low-power, 8-bit, monolithic analog-todigital converter with an on-chip track-and-hold circuit. Optimized for low cost, low power, small size and ease of use,
this product operates at conversion rates of 20 MSPS to 70
MSPS with outstanding dynamic performance over its full
operating range while consuming just 1.3 mW per MHz of
clock frequency. That’s just 78 mW of power at 60 MSPS.
Raising the PD pin puts the ADC08060 into a Power Down
mode where it consumes just 1 mW.
The unique architecture achieves 7.5 Effective Bits with
25 MHz input frequency. The excellent DC and AC characteristics of this device, together with its low power consumption and single +3V supply operation, make it ideally suited
for many imaging and communications applications, including use in portable equipment. Furthermore, the ADC08060
is resistant to latch-up and the outputs are short-circuit proof.
The top and bottom of the ADC08060’s reference ladder are
available for connections, enabling a wide range of input
possibilities. The digital outputs are TTL/CMOS compatible
with a separate output power supply pin to support interfacing with 3V or 2.5V logic. The digital inputs (CLK and PD) are
TTL/CMOS compatible.
The ADC08060 is offered in a 24-lead plastic package
(TSSOP) and is specified over the industrial temperature
range of −40˚C to +85˚C. An evaluation board is available to
assist in the easy evaluation of the ADC08060.
Features
n Single-ended input
n Internal sample-and-hold function
n Low voltage (single +3V) operation
n Small package
n Power-down feature
Key Specifications
n Resolution 8 bits
n Maximum sampling frequency 60 MSPS (min)
n DNL 0.4 LSB (typ)
n ENOB 7.5 bits (typ) at f
n THD −60 dB (typ)
n No missing codes Guaranteed
n Power Consumption
— Operating 1.3 mW/MSPS (typ)
— Power Down Mode 1 mW (typ)
=25MHz
IN
Applications
n Digital imaging systems
n Communication systems
n Portable instrumentation
n Viterbi decoders
n Set-top boxes
Pin Configuration
20006201
© 2003 National Semiconductor Corporation DS200062 www.national.com
Ordering Information
ADC08060
Block Diagram
ADC08060CIMT TSSOP
ADC08060CIMTX TSSOP (tape and reel)
ADC08060EVAL Evaluation Board
Pin Descriptions and Equivalent Circuits
Pin No. Symbol Equivalent Circuit Description
6V
3V
9V
10 V
IN
RT
RM
RB
Analog signal input. Conversion range is VRBto VRT.
Analog Input that is the high (top) side of the reference
ladder of the ADC. Nominal range is 1.0V to V
and VRBinputs define the VINconversion range.
on V
RT
Bypass well. See Section 2.0 for more information.
Mid-point of the reference ladder. This pin should be
bypassed to a clean, quiet point in the analog ground
plane with a 0.1 µF capacitor.
Analog Input that is the low side (bottom) of the
reference ladder of the ADC. Nominal range is 0.0V to
– 1.0V). Voltage on VRTand VRBinputs define the
(V
RT
conversion range. Bypass well. See Section 2.0 for
V
IN
more information.
20006202
. Voltage
A
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Pin Descriptions and Equivalent Circuits (Continued)
Pin No. Symbol Equivalent Circuit Description
Power Down input. When this pin is high, the converter is
23 PD
in the Power Down mode and the data output pins hold
the last conversion result.
ADC08060
24 CLK
13 thru 16
and
D0–D7
19 thru 22
7V
IN
GND Reference ground for the single-ended analog input, VIN.
CMOS/TTL compatible digital clock Input. V
on the falling edge of CLK input.
Conversion data digital Output pins. D0 is the LSB, D7 is
the MSB. Valid data is output just after the rising edge of
the CLK input.
Positive analog supply pin. Connect to a clean, quiet
1, 4, 12 V
A
voltage source of +3V. V
µF ceramic chip capacitor for each pin, plus one
should be bypassed with a 0.1
A
10 µF capacitor. See Section 3.0 for more information.
18 DR V
D
Power supply for the output drivers. If connected to VA,
decouple well from V
.
A
17 DR GND The ground return for the output driver supply.
2, 5, 8, 11 AGND The ground return for the analog supply.
is sampled
IN
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Absolute Maximum Ratings (Notes 1,
2)
If Military/Aerospace specified devices are required,
ADC08060
Soldering Temperature, Infrared,
10 seconds (Note 6) 235˚C
Storage Temperature −65˚C to +150˚C
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
Supply Voltage (V
Driver Supply Voltage (DR V
Voltage on Any Input or Output Pin −0.3V to V
Reference Voltage (VRT,VRB)V
CLK, OE Voltage Range
Digital Output Voltage (V
Input Current at Any Pin (Note 3)
Package Input Current (Note 3)
Power Dissipation at T
) 3.8V
A
)V
D
+ 0.3V
A
to AGND
A
−0.3V to
+ 0.3V)
(V
A
) DR GND to DR V
OH,VOL
±
25 mA
±
50 mA
= 25˚C See (Note 4)
A
A
D
Operating Ratings (Notes 1, 2)
Operating Temperature Range −40˚C ≤ T
Supply Voltage (V
Driver Supply Voltage (DR V
Ground Difference |GND - DR GND| 0V to 300 mV
Upper Reference Voltage (V
Lower Reference Voltage (V
V
Voltage Range VRBto V
IN
) +2.7V to +3.6V
A
) +2.4V to V
D
) 1.0V to (VA+ 0.1V)
RT
) 0Vto(VRT− 1.0V)
RB
ESD Susceptibility (Note 5)
Human Body Model
Machine Model
2500V
250V
Converter Electrical Characteristics
The following specifications apply for VA=DRVD= +3.0VDC,VRT= +1.9V, VRB= 0.3V, CL= 10 pF, f
duty cycle. Boldface limits apply for T
J=TMIN
to T
Symbol Parameter Conditions
: all other limits TA= 25˚C (Notes 7, 8)
MAX
Typical
(Note 9)
DC ACCURACY
INL Integral Non-Linearity
DNL Differential Non-Linearity
±
0.5
±
0.4
Missing Codes 0 (max)
FSE Full Scale Error 18
ZSE Zero Scale Offset Error 26
ANALOG INPUT AND REFERENCE CHARACTERISTICS
V
IN
C
IN
R
IN
Input Voltage 1.6
VINInput Capacitance
RINInput Resistance
V
= 0.75V +0.5
IN
Vrms
(CLK LOW) 3 pF
(CLK HIGH) 4 pF
>
1MΩ
BW Full Power Bandwidth 200 MHz
V
V
V
V
R
I
RT
RB
RT
RB
REF
REF
Top Reference Voltage 1.9
Bottom Reference Voltage 0.3
Reference Delta 1.6
Reference Ladder Resistance VRTto V
RB
Reference Ladder Current 7.3
220
CLK, PD DIGITAL INPUT CHARACTERISTICS
V
IH
V
IL
I
IH
Logical High Input Voltage DR VD=VA= 3.3V 2.0 V (min)
Logical Low Input Voltage DR VD=VA= 2.7V 0.8 V (max)
Logical High Input Current VIH=DRVD=VA= 3.3V 10 nA
= 60 MHz at 50%
CLK
Limits
(Note 9)
±
1.3 LSB (max)
+1.0
−0.9
±
28 mV (max)
±
35 mV (max)
V
RB
V
RT
V
A
1.0 V (min)
− 1.0 V (max)
V
RT
0 V (min)
1.0 V (min)
2.3 V (max)
150 Ω (min)
300 Ω (max)
5.3 mA (min)
10.6 mA (max)
≤ +85˚C
A
RT
Units
(Limits)
LSB (max)
LSB (min)
V (min)
V (max)
V (max)
A
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Converter Electrical Characteristics (Continued)
The following specifications apply for VA=DRVD= +3.0VDC,VRT= +1.9V, VRB= 0.3V, CL= 10 pF, f
duty cycle. Boldface limits apply for T
J=TMIN
to T
Symbol Parameter Conditions
CLK, PD DIGITAL INPUT CHARACTERISTICS
I
IL
C
IN
Logical Low Input Current VIL= 0V, DR VD=VA= 2.7V −50 nA
Logic Input Capacitance 3 pF
DIGITAL OUTPUT CHARACTERISTICS
V
OH
V
OL
High Level Output Voltage VA=DRVD= 2.7V, IOH= −400 µA 2.6 2.4 V (min)
Low Level Output Voltage VA=DRVD= 2.7V, IOL= 1.0 mA 0.4 0.5 V (max)
DYNAMIC PERFORMANCE
f
IN
f
ENOB Effective Number of Bits
SINAD Signal-to-Noise & Distortion
SNR Signal-to-Noise Ratio
SFDR Spurious Free Dynamic Range
THD Total Harmonic Distortion
HD2 2nd Harmonic Distortion
HD3 3rd Harmonic Distortion
IMD Intermodulation Distortion
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
IN
f
1
f
2
POWER SUPPLY CHARACTERISTICS
I
A
DR I
Analog Supply Current
Output Driver Supply Current
D
DC Input 25 31 mA (max)
f
IN
DC Input 0.3 1 mA (max)
f
IN
DC Input 25.3 32 mA (max)
I
A
DRI
+
Total Operating Current
D
f
IN
PD = Low
CLK Low, PD = Hi 0.2
: all other limits TA= 25˚C (Notes 7, 8)
MAX
Typical
(Note 9)
= 4.4 MHz, VIN= FS − 0.25 dB 7.6 Bits
= 10 MHz, VIN= FS − 0.25 dB 7.6 7.1 Bits (min)
= 25 MHz, VIN= FS − 0.25 dB 7.5 Bits
= 29 MHz, VIN= FS − 0.25 dB 7.4 Bits
= 4.4 MHz, VIN= FS − 0.25 dB 47 dB
= 10 MHz, VIN= FS − 0.25 dB 47 44.5 dB (min)
= 25 MHz, VIN= FS − 0.25 dB 47 dB
= 29 MHz, VIN= FS − 0.25 dB 46 dB
= 4.4 MHz, VIN= FS − 0.25 dB 47 dB
= 10 MHz, VIN= FS − 0.25 dB 47 44.6 dB (min)
= 25 MHz, VIN= FS − 0.25 dB 47 dB
= 29 MHz, VIN= FS − 0.25 dB 46 dB
= 4.4 MHz, VIN= FS − 0.25 dB 64 dBc
= 10 MHz, VIN= FS − 0.25 dB 63 dBc
= 25 MHz, VIN= FS − 0.25 dB 60 dBc
= 29 MHz, VIN= FS − 0.25 dB 54 dBc
= 4.4 MHz, VIN= FS − 0.25 dB −64 dBc
= 10 MHz, VIN= FS − 0.25 dB −63 dBc
= 25 MHz, VIN= FS − 0.25 dB -57 dBc
= 29 MHz, VIN= FS − 0.25 dB −54 dBc
= 4.4 MHz, VIN= FS − 0.25 dB -70 dBc
= 10 MHz, VIN= FS − 0.25 dB −65 dBc
= 25 MHz, VIN= FS − 0.25 dB -64 dBc
= 29 MHz, VIN= FS − 0.25 dB −54 dBc
= 4.4 MHz, VIN= FS − 0.25 dB −72 dBc
= 10 MHz, VIN= FS − 0.25 dB −70 dBc
= 25 MHz, VIN= FS − 0.25 dB -68 dBc
= 29 MHz, VIN= FS − 0.25 dB −65 dBc
= 11 MHz, VIN= FS − 6.25 dB
= 12 MHz, VIN= FS − 6.25 dB
-55 dBc
= 10 MHz, VIN=FS−3dB 25 mA
= 10 MHz, VIN=FS−3dB 4.4 mA
= 10 MHz, VIN=FS−3dB,
29.4
= 60 MHz at 50%
CLK
Limits
(Note 9)
ADC08060
Units
(Limits)
mA (max)
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Converter Electrical Characteristics (Continued)
The following specifications apply for VA=DRVD= +3.0VDC,VRT= +1.9V, VRB= 0.3V, CL= 10 pF, f
duty cycle. Boldface limits apply for T
ADC08060
J=TMIN
to T
Symbol Parameter Conditions
: all other limits TA= 25˚C (Notes 7, 8)
MAX
Typical
(Note 9)
POWER SUPPLY CHARACTERISTICS
DC Input 76 96 mW (max)
f
= 10 MHz, VIN=FS−3dB,
PC Power Consumption
IN
PD = Low
88 mW
CLK Low, PD = Hi 0.6 mW
PSRR
PSRR
Power Supply Rejection Ratio
1
Power Supply Rejection Ratio
2
FSE change with 2.7V to 3.3V change
in V
A
SNR change with 200 mV at 200 kHz
on supply
54 dB
45 dB
AC ELECTRICAL CHARACTERISTICS
f
C1
f
C2
t
CL
t
CH
t
OH
t
OD
Maximum Conversion Rate 70 60 MHz (min)
Minimum Conversion Rate 20 MHz
Minimum Clock Low Time 6.7 ns (min)
Minimum Clock High Time 6.7 ns (min)
Output Hold Time CLK Rise to Data Invalid 4.4 ns
Output Delay CLK Rise to Data Valid 8.2 12 ns (max)
Pipeline Delay (Latency) 2.5 Clock Cycles
t
AD
t
AJ
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
functional, but do not guarantee specific performance limits. For guaranteed specifications and test conditions, see the Electrical Characteristics. The guaranteed
specifications apply only for the test conditions listed. Some performance characteristics may degrade when the device is not operated under the listed test
conditions.
Note 2: All voltages are measured with respect to GND = AGND = DR GND = 0V, unless otherwise specified.
Note 3: When the input voltage at any pin exceeds the power supplies (that is, less than AGND or DR GND, or greater than V
should be limited to 25 mA. The 50 mA maximum package input current rating limits the number of pins that can safely exceed the power supplies with an input
current of 25 mA to two.
Note 4: The absolute maximum junction temperature (T
junction-to-ambient thermal resistance (θ
TSSOP, θ
this device under normal operation will typically be about 180 mW (88 mW quiescent power +12 mW reference ladder power). The values for maximum power
dissipation listed above will be reached only when the ADC08060 is operated in a severe fault condition (e.g., when input or output pins are driven beyond the power
supply voltages, or the power supply polarity is reversed). Obviously, such conditions should always be avoided.
Note 5: Human body model is 100 pF capacitor discharged through a 1.5 kΩ resistor. Machine model is 220 pF discharged through ZERO Ohms.
Note 6: See AN-450, “Surface Mounting Methods and Their Effect on Product Reliability”, or the section entitled “Surface Mount” found in any post 1986 National
Semiconductor Linear Data Book, for other methods of soldering surface mount devices.
Note 7: The analog inputs are protected as shown below. Input voltage magnitudes up to V
However, errors in the A/D conversion can occur if the input goes above DR V
voltage must be ≤2.6V
Sampling (Aperture) Delay CLK Fall to Acquisition of Data 1.5 ns
Aperture Jitter 2 ps rms
A
max) for this device is 150˚C. The maximum allowable power dissipation is dictated by TJmax, the
), and the ambient temperature (TA), and can be calculated using the formula PDMAX=(TJmax − TA)/θJA. In the 24-pin
is 92˚C/W, so PDMAX = 1,358 mW at 25˚C and 435 mW at the maximum operating ambient temperature of 85˚C. Note that the power consumption of
JA
to ensure accurate conversions.
DC
JA
J
+ 300 mV or to 300 mV below GND will not damage this device.
or below GND by more than 100 mV. For example, if VAis 2.7VDCthe full-scale input
D
A
= 60 MHz at 50%
CLK
Limits
(Note 9)
or DR VD), the current at that pin
Units
(Limits)
20006207
Note 8: To guarantee accuracy, it is required that VAand DR VDbe well bypassed. Each supply pin must be decoupled with separate bypass capacitors.
Note 9: Typical figures are at T
Level).
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= 25˚C, and represent most likely parametric norms. Test limits are guaranteed to National’s AOQL (Average Outgoing Quality
J
ADC08060
Typical Performance Characteristics V
wise stated
INL INL vs. Temperature
20006208
INL vs. Supply Voltage INL vs. Sample Rate
=DRVD= 3V, f
A
= 60 MHz, fIN= 10 MHz, unless other-
CLK
20006214
20006215
DNL DNL vs. Temperature
20006209
20006210
20006217
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Typical Performance Characteristics V
otherwise stated (Continued)
=DRVD= 3V, f
A
= 60 MHz, fIN= 10 MHz, unless
CLK
ADC08060
DNL vs. Supply Voltage DNL vs. Sample Rate
20006218
SNR vs. Temperature SNR vs. Supply Voltage
20006211
20006220 20006221
SNR vs. Sample Rate SNR vs. Input Frequency
20006212 20006223
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ADC08060
Typical Performance Characteristics V
otherwise stated (Continued)
SNR vs. Clock Duty Cycle Distortion vs. Temperature
20006224 20006225
Distortion vs. Supply Voltage Distortion vs. Sample Rate
=DRVD= 3V, f
A
= 60 MHz, fIN= 10 MHz, unless
CLK
20006226 20006213
Distortion vs. Input Frequency Distortion vs. Clock Duty Cycle
20006228 20006229
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Typical Performance Characteristics V
otherwise stated (Continued)
=DRVD= 3V, f
A
= 60 MHz, fIN= 10 MHz, unless
CLK
ADC08060
SINAD/ENOB vs. Temperature SINAD/ENOB vs. Supply Voltage
20006230
SINAD/ENOB vs. Sample Rate SINAD/ENOB vs. Clock Duty Cycle
20006238
20006216
20006240
SINAD/ENOB vs. Input Frequency Power Consumption vs. Sample Rate
20006239
20006219
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ADC08060
Typical Performance Characteristics V
otherwise stated (Continued)
Spectral Response
Intermodulation Distortion (IMD)
@
fIN= 10.1 MHz Spectral Response@fIN=25MHz
20006244 20006245
=DRVD= 3V, f
A
= 60 MHz, fIN= 10 MHz, unless
CLK
20006242
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Specification Definitions
APERTURE (SAMPLING) DELAY is that time required after
the fall of the clock input for the sampling switch to open. The
ADC08060
Sample/Hold circuit effectively stops capturing the input signal and goes into the “hold” mode t
low.
APERTURE JITTER is the variation in aperture delay from
sample to sample. Aperture jitter shows up as noise at the
output.
CLOCK DUTY CYCLE is the ratio of the time that the clock
waveform is at a logic high to the total time of one clock
period.
DIFFERENTIAL NON-LINEARITY (DNL) is the measure of
the maximum deviation from the ideal step size of 1 LSB.
Measured at 60 MSPS with a ramp input.
EFFECTIVE NUMBER OF BITS (ENOB, or EFFECTIVE
BITS) is another method of specifying Signal-to-Noise and
Distortion Ratio, or SINAD. ENOB is defined as (SINAD –
1.76) / 6.02 and says that the converter is equivalent to a
perfect ADC of this (ENOB) number of bits.
FULL-POWER BANDWIDTH is the frequency at which the
reconstructed output fundamental drops 3 dB below its low
frequency value for a full scale input.
FULL-SCALE ERROR is a measure of how far the last code
transition is from the ideal 1
1
⁄2LSB below VRTand is defined
as:
+ 1.5 LSB – V
V
max
where V
is the voltage at which the transition to the
max
maximum (full scale) code occurs.
INTEGRAL NON-LINEARITY (INL) is a measure of the
deviation of each individual code from a line drawn from zero
1
⁄2LSB below the first code transition) through positive
scale (
full scale (
1
⁄2LSB above the last code transition). The deviation of any given code from this straight line is measured
from the center of that code value. The end point test method
is used. Measured at 60 MSPS with a ramp input.
INTERMODULATION DISTORTION (IMD) is the creation of
additional spectral components as a result of the interaction
between two sinusoidal frequencies that are applied to the
ADC input at the same time. IMD is the ratio of the power in
the second and third order intermodulation products to the
total power in the original frequencies.
MISSING CODES are those output codes that are skipped
and will never appear at the ADC outputs. These codes
cannot be reached with any input value.
POWER SUPPLY REJECTION RATIO (PSRR) is a measure of how well the ADC rejects a change in the power
supply voltage. For the ADC08060, PSRR1 is the ratio of the
change in d.c. power supply voltage to the resulting change
in Full-Scale Error, expressed in dB. PSRR2 is a measure of
after the clock goes
AD
RT
how well an a.c. signal riding upon the power supply is
rejected and is here defined as:
where SNR0 is the SNR measured with no noise or signal on
the supply lines and SNR1 is the SNR measured with a 200
kHz, 200 mV
signal riding upon the supply lines.
P-P
OUTPUT DELAY is the time delay after the rising edge of
the input clock before the data changes at the output pins.
OUTPUT HOLD TIME is the length of time that the output
data is valid after the rise of the input clock.
PIPELINE DELAY (LATENCY) is the number of clock cycles
between initiation of conversion and when that data is presented to the output driver stage. New data is available at
every clock cycle, but the data lags the conversion by the
Pipeline Delay plus the Output Delay.
SIGNAL TO NOISE RATIO (SNR) is the ratio, expressed in
dB, of the rms value of the input signal frequency at the
output to the rms value of the sum of all other spectral
components below one-half the sampling frequency, not including harmonics or d.c.
SIGNAL TO NOISE PLUS DISTORTION (S/(N+D) or
SINAD) is the ratio, expressed in dB, of the rms value of the
input signal frequency at the output to the rms value of all of
the other spectral components below half the clock frequency, including harmonics but excluding d.c.
SPURIOUS FREE DYNAMIC RANGE (SFDR) is the difference, expressed in dB, between the rms values of the input
signal frequency at the output and the peak spurious signal,
where a spurious signal is any signal present in the output
spectrum that is not present at the input.
TOTAL HARMONIC DISTORTION (THD) is the ratio, expressed in dB, of the total of the first nine harmonic levels at
the output to the level of the fundamental at the output. THD
is calculated as
where f1is the RMS power of the fundamental (input) frequency and f
through f10is the power in the first 9 harmon-
2
ics in the output spectrum.
ZERO SCALE OFFSET ERROR is the error in the input
voltage required to cause the first code transition. It is defined as
V
OFF=VZT−VRB
where VZTis the first code transition input voltage.
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Timing Diagram
ADC08060
20006231
FIGURE 1. ADC08060 Timing Diagram
Functional Description
The ADC08060 uses a new, unique architecture that
achieves over 7.4 effective bits at input frequencies up to
30 MHz.
The analog input signal that is within the voltage range set by
and VRBis digitized to eight bits. Output format is
V
RT
straight binary. Input voltages below V
output word to consist of all zeroes. Input voltages above
will cause the output word to consist of all ones.
V
RB
Incorporating a switched capacitor bandgap, the ADC08060
exhibits a power consumption that is proportional to frequency, limiting power consumption to what is needed at the
clock rate that is used. This and its excellent performance
over a wide range of clock frequencies makes it an ideal
choice as a single ADC for many 8-bit needs.
Data is acquired at the falling edge of the clock and the
digital equivalent of that data is available at the digital outputs 2.5 clock cycles plus t
later. The ADC08060 will
OD
will cause the
RB
convert as long as the clock signal is present. The device is
in the active state when the Power Down pin (PD) is low.
When the PD pin is high, the device is in the power down
mode, where the output pins hold the last conversion before
the PD pin went high and the device consumes just 1 mW.
Applications Information
1.0 REFERENCE INPUTS
The reference inputs V
the reference ladder, respectively. Input signals between
these two voltages will be digitized to 8 bits. External voltages applied to the reference input pins should be within the
range specified in the Operating Ratings table (1.0V to (V
0.1V) for V
and 0V to (VRT− 1.0V) for VRB). Any device
RT
used to drive the reference pins should be able to source
sufficient current into the V
from the V
pin.
RB
and VRBare the top and bottom of
RT
pin and sink sufficient current
RT
A
+
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Applications Information (Continued)
ADC08060
20006232
FIGURE 2. Simple, low component count reference biasing. Because of the ladder and external resistor tolerances,
the reference voltage can vary too much for some applications.
The reference bias circuit of Figure 2 is very simple and the
performance is adequate for many applications. However,
circuit tolerances will lead to a wide reference voltage range.
Superior performance can generally be achieved by driving
the reference pins with a low impedance source.
The circuit of Figure 3 will allow a more accurate setting of
the reference voltages. The lower amplifier must have bipolar supplies as its output voltage must go negative to force
to any voltage below the VBEof the PNP transistor. Of
V
RB
changed to suit your reference voltage needs, or the divider
can be replaced with potentiometers for precise settings.
The bottom of the ladder (V
) may simply be returned to
RB
ground if the minimum input signal excursion is 0V. Be sure
that the driving sources can source sufficient current into the
pin and sink enough current from the VRBpin to keep
V
RT
these pins stable.
The LMC662 amplifier shown was chosen for its low offset
voltage and low cost.
course, the divider resistors at the amplifier input could be
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Applications Information (Continued)
ADC08060
FIGURE 3. Driving the reference to force desired values requires driving with a low impedance source.
should always be at least 1.0V more positive than V
V
RT
RB
to minimize noise.
(pin 9) is the center of the reference ladder and should
V
RM
be bypassed to a clean, quiet point in the analog ground
plane with a 0.1 µF capacitor. DO NOT allow this pin to float.
2.0 THE ANALOG INPUT
The analog input of the ADC08060 is a switch followed by an
integrator. The input capacitance changes with the clock
level, appearing as 3 pF when the clock is low, and 4 pF
when the clock is high. The sampling nature of the analog
input causes current spikes that result in voltage spikes at
20006233
the analog input pin. Any circuit used to drive the analog
input must be able to drive that input and to settle within the
clock high time. The LMH6702 has been found to be a good
amplifier to drive the ADC08060.
Figure 4 shows an example of an input circuit using the
LMH6702. Any input amplifier should incorporate some gain
as operational amplifiers exhibit better phase margin and
transient response with gains above 2 or 3 than with unity
gain. If an overall gain of less than 3 is required, attenuate
the input and operate the amplifier at a higher gain, as
shown in Figure 4.
www.national.com15
Applications Information (Continued)
ADC08060
FIGURE 4. The input amplifier should incorporate some gain for best performance (see text).
The RC at the amplifier output filters the clock rate energy
that comes out of the analog input due to the input sampling
circuit. The optimum time constant for this circuit depends
not only upon the amplifier and ADC, but also on the circuit
layout and board material. A resistor value should be chosen
between 18Ω and 47Ω and the capacitor value chose according to the formula
This will provide optimum SNR performance. Best THD performance is realized when the capacitor and resistor values
are both zero. To optimize SINAD, reduce the capacitor or
resistor value until SINAD performance is optimized. That is,
until SNR = −THD. This value will usually be in the range of
40% to 65% of the value calculated with the above formula.
An accurate calculation is not possible because of the board
material and layout dependence.
The above is intended for oversampling or Nyquist applications. There should be no resistor or capacitor between the
ADC input and any amplifier for undersampling applications.
The circuit of Figure 4 has both gain and offset adjustments.
If you eliminate these adjustments normal circuit tolerances
may cause signal clipping unless care is exercised in the
worst case analysis of component tolerances and the input
signal excursion is appropriately limited to account for the
worst case conditions. Of course, this means that the designer will not be able to depend upon getting a full scale
output with maximum signal input.
20006234
3.0 POWER SUPPLY CONSIDERATIONS
A/D converters draw sufficient transient current to corrupt
their own power supplies if not adequately bypassed. A
10 µF tantalum or aluminum electrolytic capacitor should be
placed within an inch (2.5 cm) of the A/D power pins, with a
0.1 µF ceramic chip capacitor placed within one centimeter
of the converter’s power supply pins. Leadless chip capacitors are preferred because they have low lead inductance.
While a single voltage source is recommended for the V
and DR VDsupplies of the ADC08060, these supply pins
should be well isolated from each other to prevent any digital
noise from being coupled into the analog portions of the
ADC. A choke or 27Ω resistor is recommended between
these supply lines with adequate bypass capacitors close to
the supply pins.
As is the case with all high speed converters, the ADC08060
should be assumed to have little power supply rejection.
None of the supplies for the converter should be the supply
that is used for other digital circuitry in any system with a lot
of digital power being consumed. The ADC supplies should
be the same supply used for other analog circuitry.
No pin should ever have a voltage on it that is in excess of
the supply voltage or below ground by more than 300 mV,
not even on a transient basis. This can be a problem upon
application of power and power shut-down. Be sure that the
supplies to circuits driving any of the input pins, analog or
digital, do not come up any faster than does the voltage at
the ADC08060 power pins.
A
www.national.com 16
Applications Information (Continued)
4.0 THE DIGITAL INPUT PINS
The ADC08060 has two digital input pins: The PD pin and
the Clock pin.
4.1 The PD Pin
The Power Down (PD) pin, when high, puts the ADC08060
into a low power mode where power consumption is reduced
to 1 mW. Output data is valid and accurate about 1 microsecond after the PD pin is brought low.
The digital output pins retain the last conversion output code
when either the clock is stopped or the PD pin is high.
4.2 The ADC08060 Clock
Although the ADC08060 is tested and its performance is
guaranteed with a 60 MHz clock, it typically will function well
with clock frequencies from 20 MHz to 70 MHz.
Halting the clock will provide nearly as much power saving
as raising the PD pin high. Typical power consumption with a
stopped clock is 3 mW, compared to 1 mW when PD is high.
The digital outputs will remain in the same state as they were
before the clock was halted.
Once the clock is restored (or the PD pin is brought low),
there is a time of about 1 µs before the output data is valid.
However, because of the linear relationship between total
power consumption and clock frequency, the part requires
about 1 µs after the clock is restarted or substantially
changed in frequency before the part returns to its specified
accuracy.
The low and high times of the clock signal can affect the
performance of any A/D Converter. Because achieving a
precise duty cycle is difficult, the ADC08060 is designed to
maintain performance over a range of duty cycles. While it is
specified and performance is guaranteed with a 50% clock
duty cycle and 60 Msps, ADC08060 performance is typically
maintained with clock high and low times of 3.3 ns, corresponding to a clock duty cycle range of 40% to 50% with a
60 MHz clock. Note that the clock minimum high and low
times may not be used simultaneously.
The CLOCK line should be series terminated at the clock
source in the characteristic impedance of that line. If the
clock line is longer than
ADC08060 clock pin as seen from the clock source. Typical
t
is about 150 ps/inch on FR-4 board material. For FR-4
PD
board material, the value of C becomes
where L is the length of the clock line in inches.
5.0 LAYOUT AND GROUNDING
Proper grounding and proper routing of all signals are essential to ensure accurate conversion. A combined analog
and digital ground plane should be used.
Since digital switching transients are composed largely of
high frequency components, total ground plane copper
weight will have little effect upon the logic-generated noise
because of the skin effect. Total surface area is more important than is total ground plane volume. Capacitive coupling
between the typically noisy digital circuitry and the sensitive
analog circuitry can lead to poor performance that may seem
impossible to isolate and remedy. The solution is to keep the
analog circuitry well separated from the digital circuitry.
High power digital components should not be located on or
near a straight line between the ADC (or any linear component) and the power supply area as the resulting common
return current path could cause fluctuation in the analog
“ground” return of the ADC.
Generally, analog and digital lines should cross each other at
90˚ to avoid getting digital noise into the analog path. In high
frequency systems, however, avoid crossing analog and
digital lines altogether. Clock lines should be isolated from
ALL other lines, analog AND digital. Even the generally
accepted 90˚ crossing should be avoided as even a little
coupling can cause problems at high frequencies. Best performance at high frequencies is obtained with a straight
signal path.
The analog input should be isolated from noisy signal traces
to avoid coupling of spurious signals into the input. Any
external component (e.g., a filter capacitor) connected between the converter’s input and ground should be connected
to a very clean point in the analog ground plane.
ADC08060
where tris the clock rise time and tPDis the propagation rate
of the signal along the trace.
If the clock source is used to drive more than just the
ADD08060, the CLOCK pin should be a.c. terminated with a
series RC to ground such that the resistor value is equal to
the characteristic impedance of the clock line and the capacitor value is
where tPDis the signal propagation rate down the clock line,
"L" is the line length and Z
is the characteristic impedance
O
of the clock line. This termination should be located as close
as possible to, but within one centimeter of, the ADC08060
clock pin. Further, the termination should be beyond the
20006236
FIGURE 5. Layout Example
www.national.com17
Applications Information (Continued)
Figure 5 gives an example of a suitable layout. All analog
circuitry (input amplifiers, filters, reference components, etc.)
ADC08060
should be placed together away from any digital components.
6.0 DYNAMIC PERFORMANCE
The ADC08060 is a.c. tested and its dynamic performance is
guaranteed. To meet the published specifications, the clock
source driving the CLK input must exhibit less than 10 ps
(rms) of jitter. For best a.c. performance, isolating the ADC
clock from any digital circuitry should be done with adequate
buffers, as with a clock tree. See Figure 6.
It is good practice to keep the ADC clock line as short as
possible and to keep it well away from any other signals.
Other signals can introduce jitter into the clock signal. The
clock signal can also introduce noise into the analog path.
FIGURE 6. Isolating the ADC Clock from Digital
Circuitry
7.0 COMMON APPLICATION PITFALLS
Driving the inputs (analog or digital) beyond the power
supply rails. For proper operation, all inputs should not go
more than 300 mV below the ground pins or 300 mV above
the supply pins. Exceeding these limits on even a transient
20006237
basis may cause faulty or erratic operation. It is not uncommon for high speed digital circuits (e.g., 74F and 74AC
devices) to exhibit undershoot that goes more than a volt
below ground. A 51Ω resistor in series with the offending
digital input will usually eliminate the problem.
Care should be taken not to overdrive the inputs of the
ADC08060. Such practice may lead to conversion inaccuracies and even to device damage.
Attempting to drive a high capacitance digital data bus.
The more capacitance the output drivers must charge for
each conversion, the more instantaneous digital current is
required from DR V
and DR GND. These large charging
D
current spikes can couple into the analog section, degrading
dynamic performance. Buffering the digital data outputs (with
a 74F541, for example) may be necessary if the data bus
capacitance exceeds 10 pF. Dynamic performance can also
be improved by adding 100Ω series resistors at each digital
output, reducing the energy coupled back into the converter
input pins.
Using an inadequate amplifier to drive the analog input.
As explained in Section 2.0, the capacitance seen at the
input alternates between 3 pF and 4 pF with the clock. This
dynamic capacitance is more difficult to drive than is a fixed
capacitance, and should be considered when choosing a
driving device. The LMH6702 has been found to be a good
device for driving the ADC08060.
Driving the V
pin or the VRBpin with devices that can
RT
not source or sink the current required by the ladder.
As mentioned in Section 1.0, care should be taken to see
that any driving devices can source sufficient current into the
pin and sink sufficient current from the VRBpin. If these
V
RT
pins are not driven with devices than can handle the required
current, these reference pins will not be stable, resulting in a
reduction of dynamic performance.
Using a clock source with excessive jitter, using an
excessively long clock signal trace, or having other
signals coupled to the clock signal trace. This will cause
the sampling interval to vary, causing excessive output noise
and a reduction in SNR performance. The use of simple
gates with RC timing is generally inadequate as a clock
source.
www.national.com 18
Physical Dimensions inches (millimeters) unless otherwise noted
ADC08060 8-Bit, 60 MSPS, 1.3 mW/MSPS A/D Converter
NOTES: UNLESS OTHERWISE SPECIFIED
REFERENCE JEDEC REGISTRATION mo-153, VARIATION AD, DATED 7/93.
24-Lead Package TC
Order Number ADC08060CIMT
NS Package Number MTC24
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