The IF-amplifier contains 3 AC-coupled control stages with
a total gain control range which is higher than 66 dB. The
sensitivity of the circuit is comparable with that of modern
IF-IC’s.
The video signal is demodulated by means of a PLL carrier
regenerator. This circuit contains a frequency detector and
a phase detector. During acquisition the frequency
detector will tune the VCO to the right frequency. The initial
adjustment of the oscillator is realised via the I2C-bus. The
switching between SECAM L and L’ can also be realised
via the I2C-bus. After lock-in the phase detector controls
the VCO so that a stable phase relation between the VCO
and the input signal is achieved. The VCO is running at the
double IF frequency. The reference signal for the
demodulator is obtained by means of a frequency divider
circuit. To get a good performance for phase modulated
carrier signals the control speed of the PLL can be
increased by means of the FFI bit.
The AFC output is obtained by using the VCO control
voltage of the PLL and can be read via the I2C-bus. For
fast search tuning systems the window of the AFC can be
increased with a factor 3. The setting is realised with the
AFW bit.
The AGC-detector operates on top sync and top whitelevel. The demodulation polarity is switched via the
I2C-bus. The AGC detector time-constant capacitor is
connected externally. This mainly because of the flexibility
of the application. The time-constant of the AGC system
during positive modulation is rather long to avoid visible
variations of the signal amplitude. To improve the speed of
the AGC system a circuit has been included which detects
whether the AGC detector is activated every frame period.
When during 3 field periods no action is detected the
speed of the system is increased. For signals without peak
white information the system switches automatically to a
gated black level AGC. Because a black level clamp pulse
is required for this way of operation the circuit will only
switch to black level AGC in the internal mode.
The circuit contains a video identification circuit which is
independent of the synchronisation circuit. Therefore
search tuning is possible when the display section of the
receiver is used as a monitor. However, this ident circuit
cannot be made as sensitive as the slower sync ident
circuit (SL) and we recommend to use both ident outputs
to obtain a reliable search system. The ident output is
supplied to the tuning system via the I2C-bus.
TDA 9321H
The input of the identification circuit is connected to pin 14,
the “internal” CVBS input (see Fig.3). This has the
advantage that the ident circuit can also be made
operative when a scrambled signal is received
(descrambler connected between the IF video output (pin
10) and pin 14). A second advantage is that the ident
circuit can be used when the IF amplifier is not used (e.g.
with built-in satellite tuners).
The video ident circuit can also be used to identify the
selected CBVS or Y/C signal. The switching between the
2 modes can be realised with the VIM bit.
The TDA 9321H contains a group delay correction circuit
which can be switched between the BG and a flat group
delay response characteristic. This has the advantage that
in multi-standard receivers no compromise has to be made
for the choice of the SAW filter. Both the input and output
of the group delay correction circuit are externally available
so that the sound trap can be connected between the IF
video output and the group delay correction input. The
output signal of the correction circuit can be supplied to the
video processing circuit and to the SCART plug.
2
The IC has several (I
can be used to switch sound traps or other external
components.
When the IF amplifier is not used the complete IF amplifier
can be switched-off via the I2C-bus by means of the IFO
bit.
Sound circuit
The sound IF amplifier is similar to the vision IF amplifier
and has a gain control range of about 66 dB. The AGC
circuit is related to the SIF carrier levels (average level of
AM or FM carriers) and ensures a constant signal
amplitude of the AM demodulator and the QSS mixer.
The single reference QSS mixer is realised by a multiplier.
In this multiplier the SIF signal is converted to the
intercarrier frequency by mixing it with the regenerated
picture carrier from the VCO. The mixer output signal is
supplied to the output via a high-pass filter for attenuation
of the residual video signals. With this system a high
performance hi-fi stereo sound processing can be
achieved.
The AM sound demodulator is realised by a multiplier. The
modulated sound IF signal is multiplied in phase with the
limited SIF signal. The demodulator output signal is
supplied to the output via a low-pass filter for attenuation
of the carrier harmonics.
C-bus controlled) output ports which
June 30, 19988
Page 9
Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
VIM
IDENT
CVBS
EXT. 2
Y/CVBS
EXT. 3
EXT. 3
Fig.3 CVBS switch and interfacing of video ident
CVBS-INT
VIDEO
IDENT
CVBS
EXT. 1
TDA 9321H
TO LUMA/SYNC PROCESSING
TO CHROMA PROCESSING
+
+
+
C
Y/CVBS
EXT. 4CEXT. 4
COMB C-IN
COMB Y-IN
CVBS
COMB OUT
TXT
CVBSO
PIP
CVBSO
Video switches
The circuit has 3 CVBS inputs (1 internal and 2 external
inputs) and 2 Y/C inputs. The Y/C inputs can also be used as
additional CVBS inputs. The switch configuration is given in
Fig.3. The selection of the various sources is made via the
I2C-bus.
The circuit can be set in a mode in which it automatically
detects whether a CVBS or a Y/C signal is supplied to the Y/C
inputs. In this mode the TV-standard identification first takes
place on the added Y/CVBS and the C input signal. Then both
chroma input signal amplitudes are checked once and the
input signal with the highest burst signal amplitude is
selected. The result of the detection can be read via the
I2C-bus.
The IC has 2 inputs (AV-1 and AV-2) which can be used to
read the status levels of pin 8 of the SCART plug. The
information is available in the output status byte 02 in the bits
D0-D3.
The 3 outputs of the video switch (CVBSO
, CVBSO
TXT
PIP
and
COMBCVBS) can be independently switched to the various
input signals. The names are just arbitrary and it is for
instance possible to use the COMBCVBS signal to drive the
Comb-filter and the teletext decoder in parallel and to supply
the CVBSO
signal to the SCART plug (via an emitter
TXT
follower).
For comb filter interfacing the circuit has the
COMBCVBS output, a 3rd Y/C input, a reference signal
output (fsc) and 2 control pins which switch the comb
filter to the standard of the incoming signal (as detected
by the ident circuit of the colour decoder). When a signal
is recognised which can be combed and the comb filter
is enabled by the ECMB-bit the Y/C signals coming from
the comb filter are automatically selected. This is
indicated via the CMB-bit in output status byte 02
(D5).For signals which cannot be combed (like SECAM
or Black-to-White signals) the Y/C signals coming from
the comb filter are not selected.
Chroma and luminance processing
The circuits contain a chroma bandpass, the SECAM
cloche filter and chroma trap circuit. The filters are
realised by means of gyrator circuits and they are
automatically calibrated by comparing the tuning
frequency with the X-tal frequency of the decoder. The
luminance delay line is also realised by means of gyrator
circuits. The centre frequency of the chroma bandpass
filter is switchable via the I2C-bus so that the
performance can be optimised for “front-end” signals
and external CVBS signals.
The luminance output signal which is derived from the
incoming CVBS or Y/C signal can be varied in amplitude
by means of a separate gain setting control via the
I2C-bus control bits GAI1 and GAI0. The gain variation
which can be realised with these bits is -1 to +2 dB.
June 30, 19989
Page 10
Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
Colour decoder
The colour decoder can decode PAL, NTSC and SECAM
signals. The PAL/NTSC decoder contains an
alignment-free X-tal oscillator with 4 separate X-tal pins, a
killer circuit and two colour difference demodulators. The
90° phase shift for the reference signal is made internally.
Because it is possible to connect 4 different X-tals to the
colour decoder, all colour standards can be decoded
without external switching circuits. Which X-tals are
connected to the decoder must be indicated via the
I2C-bus. X-tal pins which are not used must be left open.
The horizontal oscillator is calibrated by means of the X-tal
frequency of the colour PLL. For a reliable calibration it is
very important that the X-tal indication bits (XA to XD) are
not corrupted. For this reason the X-tal bits can be read in
the output bytes so that the software can check the I2C
transmission.
The IC’s contain an Automatic Colour Limiting (ACL)
circuit which is switchable via the I2C-bus and which
prevents that oversaturation occurs when signals with a
high chroma-to-burst ratio are received. The ACL circuit is
designed such that it only reduces the chroma signal and
not the burst signal. This has the advantage that the colour
sensitivity is not affected by this function. The ACL function
is mainly intended for NTSC signals and it can also be
used for PAL signals. For SECAM signals the ACL function
should be switched-off.
The SECAM decoder contains an auto-calibrating PLL
demodulator which has two references, viz: the 4.43 MHz
sub-carrier frequency which is obtained from the X-tal
oscillator which is used to tune the PLL to the desired
free-running frequency and the bandgap reference to
obtain the correct absolute value of the output signal. The
VCO of the PLL is calibrated during each vertical blanking
period, when the IC is in search or SECAM mode.
The circuit can also decode the PAL
can insert the various reference signals, set-ups and
timing signals which are required for the PAL
IC’s.
The base-band delay line (TDA 4665 function) is
integrated.
plus
helper signal and
plus
decoder
TDA 9321H
RGB switch and matrix
The IC has 2 RGB inputs with fast switching. The switching
of the various sourcing is controlled via the I2C-bus and the
condition of the switch inputs can be read from the I2C-bus
status bytes. If the RGB signals are not synchronous with
the selected decoder input signal, an external clamp pulse
has to be supplied to the HA/CLP input. The IC must be set
in this mode via the I2C-bus. In that case the VA pulse is
suppressed by switching the VA output in a high
impedance OFF-state.
When an external RGB signal is mixed into the internal
YUV signal it is necessary to switch-off the PAL
demodulation. To detect the presence of a fast blanking a
circuit is added which forces the MACP and HD bit to zero
if a blanking pulse is detected in 2 consecutive lines. This
system is chosen to prevent switching-off at every spike
which is detected on the fast blanking input.
The IC has the possibility to use the RGB1 input as YUV
input. This function can be enabled by means of the YUV
bit in subaddress 0A (D3). When switched to the YUV input
the input signals must have the same amplitude and
polarity as the YUV output signals. The Y signal has to be
supplied to the G1 input, the U signal to the B1 input and
the V signal to the R1 input.
Synchronisation circuit
The sync separator is preceded by a controlled amplifier
which adjusts the sync pulse amplitude to a fixed level.
These pulses are fed to the slicing stage which is operating
at 50% of the amplitude. The separated sync pulses are
fed to the phase detector and to the coincidence detector.
This coincidence detector is used to detect whether the
line oscillator is synchronised and can also be used for
transmitter identification. This circuit can be made less
sensitive by means of the STM bit. This mode can be used
during search tuning to avoid that the tuning system stops
at very weak input signals. The PLL has a very high statical
steepness so that the phase of the picture is independent
of the line frequency.
For the horizontal output pulse 2 conditions are possible,
viz.:
• An HA pulse which has a phase and width which is
identical to the incoming horizontal sync pulse
• A clamp pulse (CLP) which has a phase and width which
is identical to the clamp pulse in the sandcastle pulse
plus
June 30, 199810
Page 11
Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
The HA/CLP signal is generated by means of an oscillator
which is running at a frequency of 440 x fH. Its frequency is
divided by 440 to lock the first loop to the incoming signal.
The time-constant of the loop can be forced by the I2C-bus
(fast or slow). If required the IC can select the
time-constant depending on the noise content of the
incoming video signal.
The free-running frequency of the oscillator is determined
by a digital control circuit which is locked to the reference
signal of the colour decoder. When the IC is switched-on
the HA/CLP is suppressed and the oscillator is calibrated
as soon as all sub-address bytes have been sent. When
the frequency of the oscillator is correct the HA/CLP signal
is switched-on again.
When the coincidence detector indicates an out-of-lock
situation the calibration procedure is repeated.
The VA pulse is obtained via a vertical count down circuit.
The countdown circuit has various windows depending on
the incoming signal (50 Hz or 60 Hz standard or no
standard). The countdown circuit can be forced in various
modes by means of the I2C-bus. To obtain short switching
times of the countdown circuit during a channel change the
divider can be forced in the search window by means of
the NCIN bit.
TDA 9321H
2
C-BUS SPECIFICATION
I
The slave addresses of the IC’s is given in the table below.
The circuit operates up to clock frequencies of 400 kHz.
Slave addresses
A6A5A4A3A2A1A0R/W
10001A111/0
The bit A1 is controlled via the pin 48 (AS), when the pin is
connected to ground it is a 0 and when connected to the
positive supply line it is a 1. When this pin is left open it is
connected to ground via an internal resistor.
Start-up procedure
Read the status bytes until POR = 0 and send all
subaddress bytes. It is advised to check the bus
transmission by reading the output status bits SXA to SXD.
This ensures a good operation of the calibration system of
the horizontal oscillator. The horizontal output signal is
switched-on when the oscillator is calibrated.
Each time before the data in the IC is refreshed, the status
bytes must be read. If POR = 1, the procedure mentioned
above must be carried out to restart the IC.When this
procedure is not followed the horizontal frequency may be
incorrect after power-up or after a power dip.
Valid subaddresses: 00 to 0E, subaddresses FE and FF
are reserved for test purposes. Auto-increment mode
available for subaddresses.
1. Black and helper set-up will only be present in a norm
sync condition.
Table 8 Automatic colour limiting
ACLCOLOUR LIMITING
0not active
1active
plus
/EDTV-2)
XA-XDCONDITION
0X-tal not present
1X-tal present, note1
Note
1. When a comb filter is used the various X-tals must be
connected to the IC as indicated in the pinning
diagram. This is required because the ident system
switches automatically to the comb filter when a signal
is identified which can be combed (right combination of
colour standard and X-tal frequency). For applications
without comb filter only XA is important (4.43 MHz),
the other pins can then have an arbitrary 3.5 MHz
X-tal.
1. For an equal delay of the luminance and chrominance
signal the delay must be set at a value of 280 ns
(YD3...YD0 = 1011). This is only valid for a CVBS
signal without group delay distortions.
Table 13 Forced field frequency
FORFFORSFIELD FREQUENCY
00auto (60 Hz when line not
synchronized)
01forced 60 Hz; note 1
10keep last detected field frequency
11auto (50 Hz when line not
synchronized)
Note
1. When switched to this mode the divider will directly
switch to forced 60 Hz only.
Table 14 Phase 1 (ϕ1) time constant, see also table 55
FOAFOBMODE
00normal
01slow
10slow/fast
11fast
Table 15 Video ident mode
VIMMODE
0ident coupled to internal CVBS (pin 14)
1ident coupled to selected CVBS
TDA 9321H
Table 16 Synchronization mode
POCMODE
0active
1not active
Table 17 Video ident mode
VIDVIDEO IDENT MODE
0ϕ
1not active
Table 18 Blanked sync on Y
BSYCONDITION
0unblanked sync, note1
1blanked sync
Note
1. Except for PAL
Table 19 Condition of horizontal output
HOCONDITION
0clamp pulse available at H
1HA pulse available at H
Table 20 Enable “Macrovision/subtitle” gating
EMGMODE
0disable gating
1enable gating
Table 21 Vertical divider mode
NCINVERTICAL DIVIDER MODE
0normal operation
1switched to search window
loop switched on and off
1
out
plus
with black set-up.
OUT
OUT
June 30, 199814
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Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
Table 22 Video switch control
ECMB
NOTE 2
0000-INT. CVBSINT. CVBS
00010CVBS1CVBS1
00011CVBS2CVBS2
00100CVBS3CVBS3
00101YC3Y+C3
00110CVBS4CVBS4
00111YC4Y+C4
01100AUTO YC3, note1CVBS3 or Y+C3
01110AUTO YC4, note1CVBS4 or Y+C4
1000-YC COMBINT. CVBS
10010YC COMBCVBS1
10011YC COMBCVBS2
10100YC COMBCVBS3
10110YC COMBCVBS4
11100AUTO COMB3, note1CVBS3 or Y+C3
11110AUTO COMB4, note1CVBS4 or Y+C4
DEC3DEC2DEC1DEC0SELECTED SIGNALSIGNAL TO COMB
TDA 9321H
Note
1. AUTO YC means the decoder switches between CVBS and YC depending on the presence of the burst signal on
these signals. AUTO COMB means the decoder switches to YC mode if the burst is present on the C input and to
the comb filter output if the burst is present on the CVBS signal.
2. When ECMB = 1 the subcarrier frequency is present at pin 30 (REFO). The Y/C output signals coming from the comb
filter are only switched-on when a signal is received that can be combed.
output voltage HIGH4.05.05.5V
output voltage LOW−0.20.4V
sink current2−−mA
source current2−−mA
Notes
1. The 2 supply pins must be decoupled separately but they must be derived from the same main supply to avoid too
big differences between the two.
2. On set AGC.
3. This parameter is not tested during production and is just given as application information for the designer of the
television receiver.
4. Loop bandwidth BL = 60 kHz (natural frequency fN = 15 kHz; damping factor d = 2; calculated with top sync level as
FPLL input signal level). LC-VCO circuit: Q0 = 60, C
= 30 pF.
int.
5. The optimum temperature stability of the PLL can be obtained when a Toko coil as given in Table 53 is applied.
6. This parameter is not tested during production but is guaranteed by the design and qualified by means of matrix
batches which are made in the pilot production period.
7. Measured at 10 mV (RMS) top sync input signal.
8. So called projected zero point, i.e. with switched demodulator.
9. Measured in accordance with the test line given in Fig.5. For the differential phase test the peak white setting is
reduced to 87%.
The differential gain is expressed as a percentage of the difference in peak amplitudes between the largest and
smallest value relative to the subcarrier amplitude at blanking level.
The phase difference is defined as the difference in degrees between the largest and smallest phase angle.
10. This figure is valid for the complete video signal amplitude (peak white-to-black), see Fig.6.
11. The noise inverter is only active in the “strong signal mode” (no noise detected in the incoming signal)
12. The test set-up and input conditions are given in Fig.7. The figures are measured with an input signal of 10 mV RMS.
June 30, 199834
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Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
13. Measured at an input signal of 10 mV
voltage (RMS value). B = 5 MHz. Weighted in accordance with CCIR 567.
14. The AGC response time is also dependent on the acquisition time of the PLL demodulator. The values given are valid
when the PLL is in lock.
15. The AFC control voltage is obtained from the control voltage of the VCO of the PLL demodulator. The tuning
information is supplied to the tuning system via the I2C-bus. 2 bits are reserved for this function. The AFC value is
valid only when the PL-bit is 1.
16. The weighted S/N ratio is measured under the following conditions:
a) The vision IF modulator must meet the following specifications:
Incidental phase modulation for black-to-white jumps less than 0.5 degrees.
QSS AF performance, measured with the television-demodulator AMF2 (audio output, weighted S/N ratio) better
than 60 dB (deviation 27 kHz) for 6 kHz sine wave black-to-white modulation.
Picture-to-sound carrier ratio: PC/SC1 = 13 dB (transmitter).
b) The measurements must be carried out with the Siemens SAW filters G3962 for vision IF and G9350 for sound
IF. Input level for sound IF 10 mV
c) The PC/SC ratio at the vision IF input is calculated as the addition of the TV transmitter ratio and the SAW filter
PC/SC ratio. This PC/SC ratio is necessary to achieve the S/N(W) values as indicated.
17. Signal with negative-going sync. Amplitude includes sync pulse amplitude.
18. Indicated is a signal for a colour bar with 75% saturation (chroma : burst ratio = 2.2 : 1).
19. When a signal is identified which can be combed (right combination of colour standard and reference X-tal) the comb
filter is switched to that mode via the SYS1 and SYS2 pins and then the filter is activated by switching on the
reference carrier signal and connecting the Y/C output signal of the comb filter to the video processing circuits.
20. The subcarrier output signal can be used as reference signal for external comb filter IC’s (e.g. SAA 4961). When the
ECMB bit is low the subcarrier signal is suppressed and the dc level is low. With the ECMB bit high the output level
is high and the subcarrier signal is present.
21. The outputs SYS1 and SYS2 can be used to switch the comb filter to the different colour standards like PAL-M,
PAL-N, PAL-B,G and NTSC-M and are controlled by the colour decoder identification circuit.
The setting of the outputs for the various standards is given in table 54.
22. For the detection of the status of the incoming SCART signal a voltage divider with a ratio of 2/3 has to be connected
between pin 8 of the SCART plug and the detection input. The impedance of the voltage divider should not be too
high-ohmic because of the input impedance of 100 kΩ.
23. When the decoder is forced to a fixed subcarrier frequency (via the XA-XD or the CM-bits) the chroma trap is always
switched-on, also when no colour signal is identified. When 2 X-tals are active the chroma trap is switched-off when
no colour signal is identified.
24. The typical group delay characteristic for the BG standard is given in Fig.8.
25. At a chrominance input voltage of 660 mV (p-p) (colour bar with 75% saturation i.e. burst signal amplitude
300 mV (p-p)) the dynamic range of the ACC is +6 and −20 dB.
26. The ACL function can be activated by via the ACL bit. The ACL circuit reduces the gain of the chroma amplifier for
input signals with a chroma-to-burst ratio which exceeds a value of 3.0.
. The S/N is the ratio of black-to-white amplitude to the black level noise
RMS
with 27 kHz deviation.
RMS
TDA 9321H
June 30, 199835
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Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
27. All frequency variations are referenced to 3.58 or 4.43 MHz carrier frequency.
All oscillator specifications are measured with the Philips crystal series 9922 520 with a series capacitance of 18 pF.
The oscillator circuit is rather insensitive to the spurious responses of the X-tal. As long as the resonance resistance
of the third overtone is higher than that of the fundamental frequency the oscillator will operate at the right frequency.
The typical crystal parameters for the X-tals mentioned above are:
a) Load resonance frequency f0= 4.433619, 3.579545, 3.582056 and 3.575611 MHz; CL= 20 pF.
b) Motional capacitance CM= 20.6 fF (4.43 MHz crystal) or 14.7 fF (3.58 MHz crystal).
c) Parallel capacitance C0= 5.0 pf.
The minimum detuning range can only be specified if both the IC and the X-tal tolerances are known and therefore
the figures regarding catching range are only valid for the specified X-tal series. In this figure tolerances of the X-tal
with respect to the nominal frequency, motional capacitance and ageing have been taken into account and have
been counted for by gaussic addition.
Whenever different typical X-tal parameters are used the following equation might be helpful for calculating the
impact on the tuning capabilities:
Detuning range = CM /(1 + C0/CL)
The resulting detuning range should be corrected for temperature shift and supply voltage deviation of both the IC
and the X-tal. To guarantee a catching range of ±300 Hz on 4.43 MHz the minimum motional capacitance of the X-tal
must have a value 13.2 fF or higher. For a catching range of 250 Hz with the 3.58 MHz X-tal the minimum motional
capacitance must have a value of 9 fF.
The actual series capacitance in the application should be CL = 18 pF to account for parasitic capacitances on and
off chip.
28. The hue control is active for NTSC on the demodulated colour difference signals and for PAL
helper signal.
29. This parameter indicates the bandwidth of the complete chrominance circuit including the chrominance bandpass
filter. The bandwidth of the low-pass filter of the demodulator is approximately 1 MHz.
30. This delay is partially caused by the low-pass filter at the sync separator input.
31. The “internal” luminance signal (signal which is derived from the incoming CVBS or Y/C signals) has a separate gain
control setting (controlled by the I2C bits GAI1 and GAI0 and with a gain variation between -1 dB and +2 dB) which
can be used to get an optimal input signal amplitude for the feature box.
32. The slicing level is independent of sync pulse amplitude. The given percentage is the distance between the slicing
level and the black level (back porch). When the amplitude of the sync pulse exceeds the value of 350 mV the sync
separator will slice the sync pulse at a level of 175 mV above top sync. The maximum sync pulse amplitude is 4 V
33. To obtain a good performance for both weak signal and VCR playback the time constant of the first control loop is
switched depending on the input signal condition and the condition of the I2C-bus. Therefore the circuit contains a
noise detector and the time constant is switched to ‘slow’ when too much noise is present in the signal. In the ‘fast’
mode during the vertical retrace time the phase detector current is increased 50% so that phase errors due to
head-switching of the VCR are corrected as soon as possible. Switching between the two modes can be
automatically or overruled by the I2C-bus.
The circuit contains a video identification circuit which is independent of first loop. This identification circuit can be
used to close or open the first control loop when a video signal is present or not present on the input. This enables
a stable On Screen Display (OSD) when just noise is present at the input. The coupling of the video identification
circuit with the first loop can be defeated via the I2C-bus.
To prevent that the horizontal synchronisation is disturbed by anti copy signals like Macrovision the phase detector
is gated during the vertical retrace period from line 11 to 17 (60 Hz signal) or 11 to 22 (50 Hz signal) so that pulses
during scan have no effect on the output voltage. The width of the gate pulse is about 22 µs. During weak signal
conditions (noise detector active) the gating is active during the complete scan period and the width of the gate pulse
is reduced to 5.7 µs so that the effect of noise is reduced to a minimum.
The output current of the phase detector in the various conditions are shown in Table 55.
2
TDA 9321H
plus
on the demodulated
p-p
.
June 30, 199836
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Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
34. The timing pulses for the vertical ramp generator are obtained from the horizontal oscillator via a divider circuit. This
divider circuit has 3 modes of operation:
a) Search mode ‘large window’.
This mode is switched on when the circuit is not synchronized or when a non-standard signal (number of lines
per frame outside the range between 311 and 314 (50 Hz mode) or between 261 and 264 (60 Hz mode) is
received). In the search mode the divider can be triggered between line 244 and line 361 (approximately
43.3 to 64.5 Hz).
b) Standard mode ‘narrow window’.
This mode is switched on when more than 15 succeeding vertical sync pulses are detected in the narrow window.
When the circuit is in the standard mode and a vertical sync pulse is missing the retrace of the vertical ramp
generator is started at the end of the window. Consequently, the disturbance of the picture is very small. The
circuit will switch back to the search window when, for 6 successive vertical periods, no sync pulses are found
within the window.
c) Standard TV-norm (divider ratio 525 (60 Hz) or 625 (50 Hz).
When the system is switched to the narrow window it is checked whether the incoming vertical sync pulses are
in accordance with the TV-norm. When 15 standard TV-norm pulses are counted the divider system is switched
to the standard divider ratio mode. In this mode the divider is always reset at the standard value even if the vertical
sync pulse is missing.
When 3 vertical sync pulses are missed the system switches back to the narrow window and when also in this
window no sync pulses are found (condition 3 missing pulses) the system switches over to the search window.
The vertical divider needs some waiting time during channel-switching of the tuner. When a fast reaction of the
divider is required during channel-switching the system can be forced to the search window by means of the NCIN bit
in subaddress 06.
35. The delay between the positive edge of VA and the positive edge of CLP (~ negative edge of HA) after VA is 32.0 µs
for field 1 and 0 µs for field 2. Especially for PAL
phase relation to the undisturbed V pulses of the incoming video signal. This relation must remain correct as long as
the vertical divider is in the standard mode (indirect sync mode). Therefore the coincidence window used here must
be a half line window. With a well defined phase relation of the generated VA pulses to the generated HA pulses a
correct field identification and all the required timing signals referring to a certain line in each frame can be generated
externally in the PAL
36. The general purpose outputs (pin 19 and 22) can be used to switch external circuits like sound traps etc. They are
controlled via the I2C-bus by the bits OS0 (pin 19) and OS1 (pin 22).
plus
decoder environment.
plus
signals the regenerated VA pulses must have a fixed and known
TDA 9321H
Table 53 Coil data for the IF-PLL demodulator (approximated coil values)
IF Freq.VCO Freq.CoilTOKO sample number
(MHz)(MHz)(nH)5 mm (5KM)
38.977.8150P369INAS-159HM
45.7591.5100P369INAS-160HM
58.75117.570P369INAS-161HM
Temperature coefficient30 ± 100 ppm/˚C
June 30, 199837
Page 38
Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
Table 54 Switching conditions of the SYS1 and SYS2 pins
-----------------------------------------------------------at 2.66 or 3.3 MHz
V
O
ATTENUATOR
3.6 dB+=
TEST
CIRCUIT
SPECTRUM
ANALYZER
gain setting
adjusted for blue
MBC210
Fig.7 Test set-up intermodulation.
June 30, 199840
Page 41
Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
450
400
350
300
250
200
TDA 9321H
150
GROUP DELAY (NS)
100
50
0
1.02.0
Fig.8 Group delay characteristic
FREQUENCY (MHz)
3.0
4.0
5.0
June 30, 199841
Page 42
June 30, 199842
TEST AND APPLICATION INFORMATION
Philips SemiconductorsFinal Device Specification
I
2
C-bus controlled TV Input Processor
TUNER AGC
SAW
IF
FILTER
CVBS-1
AV-1
CVBS-2
AV-2
CVBS/Y-3
C-3
CVBS/Y-4
C-4
RGB-1
RGB-2
TDA 9321H
RGB-3
Y
U
V
Y
U
V
FEATURE
TDA 9330H
RGB-4
R
G
B
BEAM CURR.
BL. CURR.
BOX
V-OUT
H
A
V
A
H
D
EW-OUT
V
D
H-OUT
CVBS(PIP)
CVBS(TXT)
CVBS
COMB FILTER
Y
TDA 9321H
C
Fig.9 Application diagram.
Page 43
Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
PACKAGE OUTLINE
handbook, full pagewidth
seating plane
6452
1
pin 1 index
0.10
18.2
17.6
S
TDA 9321H
S
B
51
1.2
(4x)
0.8
1.0
B
20.1
24.2
19.9
23.6
0.20 M
Dimensions in mm
0.50
0.35
2.90
2.65
33
3220
1.2
0.25
0.05
0.8
A
(4x)
detail X
1.0
0.6
X
1.4
1.2
0.25
0.14
0 to 7
MSA327
3.2
2.7
o
19
1.0
0.50
0.35
14.1
13.9
0.20 M A
Fig.10 Plastic quad flat package; 64 leads (lead length 1.95 mm); body 14 x 20 x 2.8
June 30, 199843
Page 44
Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
SOLDERING
Plastic quad flat-packs
BYWAVE
During placement and before soldering, the component
must be fixed with a droplet of adhesive. After curing the
adhesive, the component can be soldered. The adhesive
can be applied by screen printing, pin transfer or syringe
dispensing.
Maximum permissible solder temperature is 260 °C, and
maximum duration of package immersion in solder bath is
10 s, if allowed to cool to less than 150 °C within 6 s.
Typical dwell time is 4 s at 250 °C.
A modified wave soldering technique is recommended
using two solder waves (dual-wave), in which a turbulent
wave with high upward pressure is followed by a smooth
laminar wave. Using a mildly-activated flux eliminates the
need for removal of corrosive residues in most
applications.
BY SOLDER PASTE REFLOW
TDA 9321H
Several techniques exist for reflowing; for example,
thermal conduction by heated belt, infrared, and
vapour-phase reflow. Dwell times vary between 50 and
300 s according to method. Typical reflow temperatures
range from 215 to 250 °C.
Preheating is necessary to dry the paste and evaporate
the binding agent. Preheating duration: 45 min at 45 °C.
REPAIRING SOLDERED JOINTS (BY HAND-HELD SOLDERING
IRON OR PULSE
Fix the component by first soldering two, diagonally
opposite, end pins. Apply the heating tool to the flat part of
the pin only. Contact time must be limited to 10 s at up to
300 °C. When using proper tools, all other pins can be
soldered in one operation within 2 to 5 s at between 270
and 320 °C. (Pulse-heated soldering is not recommended
for SO packages.)
For pulse-heated solder tool (resistance) soldering of VSO
packages, solder is applied to the substrate by dipping or
by an extra thick tin/lead plating before package
placement.
-HEATED SOLDER TOOL)
Reflow soldering requires the solder paste (a suspension
of fine solder particles, flux and binding agent) to be
applied to the substrate by screen printing, stencilling or
pressure-syringe dispensing before device placement.
June 30, 199844
Page 45
Philips SemiconductorsFinal Device Specification
I2C-bus controlled TV Input Processor
DEFINITIONS
Data sheet status
Objective specificationThis data sheet contains target or goal specifications for product development.
Preliminary specificationThis data sheet contains preliminary data; supplementary data may be published later.
Product specificationThis data sheet contains final product specifications.
Limiting values
Limiting values given are in accordance with the Absolute Maximum Rating System (IEC 134). Stress above one or
more of the limiting values may cause permanent damage to the device. These are stress ratings only and operation
of the device at these or at any other conditions above those given in the Characteristics sections of the specification
is not implied. Exposure to limiting values for extended periods may affect device reliability.
Application information
Where application information is given, it is advisory and does not form part of the specification.
LIFE SUPPORT APPLICATIONS
These products are not designed for use in life support appliances, devices, or systems where malfunction of these
products can reasonably be expected to result in personal injury. Philips customers using or selling these products for
use in such applications do so at their own risk and agree to fully indemnify Philips for any damages resulting from such
improper use or sale.
TDA 9321H
PURCHASE OF PHILIPS I
Purchase of Philips I
components in the I2C system provided the system conforms to the I2C specification defined
by Philips. This specification can be ordered using the code 9398 393 40011.
2
C COMPONENTS
2
C components conveys a license under the Philips’ I2C patent to use the
June 30, 199845
Page 46
Philips Semiconductors – a worldwide company
Argentina: see South America
Australia: 34 Waterloo Road, NORTH RYDE, NSW 2113,
United States: 811 East Arques Avenue, SUNNYVALE, CA 94088-3409,
Tel. +1 800 234 7381
Uruguay: see South America
Vietnam: see Singapore
Yugoslavia: PHILIPS, Trg N. Pasica 5/v, 11000 BEOGRAD,
Tel. +381 11 625 344, Fax.+381 11 635 777
For all other countries apply to: Philips Semiconductors, Marketing & Sales Communications,
Building BE-p, P.O. Box 218, 5600 MD EINDHOVEN, The Netherlands, Fax. +31 40 27 24825
The information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed
without notice. No liability will be accepted by the publisher for any consequence of its use. Publication thereof does not convey nor imply any license
under patent- or other industrial or intellectual property rights.
Printed in The Netherlands
Internet: http://www.semiconductors.philips.com
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