ON NCP1203D100G, NCP1203D100R2G, NCP1203D40G, NCP1203D40R2G, NCP1203D60G Schematic [ru]

...
NCP1203
PWM Current--Mode Controller for Universal Off-- Line S upplies Featuring Standby and Short Circuit Protection
Housed in SOIC--8 or PDIP--8 package, the NCP1203 represents a major leap toward ultra--compact Switchmode Power Supplies and represents an excellent candidate to replace the UC384X devices. Due to its proprietary SMARTMOSVery High Voltage Technology, the circuit allows the implementation of complete off--line AC--DC adapters, battery charger and a high--power SMPS with few external components.
With an internal structure operating at a fixed 40 kHz, 60 kHz or 100 kHz switching frequency, the controller features a high--voltage startup FET which ensures a clean and loss--less startup sequence. Its current--mode control naturally provides good audio--susceptibility and inherent pulse--by--pulse control.
When the current setpoint falls below a given value, e .g. the output power demand diminishes, the IC automatically enters the so--called skip cycle mode and provides improved efficiency at light loads while offering excellent performance in standby conditions. Because this occurs at a user adjustable low peak current, no acoustic noise takes place.
The NCP1203 also includes an efficient protective circuitry which, in presence of an output over load condition, disables the output pulses while the device enters a safe burst mode, trying to restart. Once the default has gone, the device auto--recovers. Finally, a temperature shutdown with hysteresis helps building safe and robust power supplies.
Features
High--Voltage Startup Current SourceAuto--Recovery Internal Output Short--Circuit ProtectionExtremely Low No--Load Standby PowerCurrent--Mode with Adjustable Skip--Cycle CapabilityInternal Leading Edge Blanking250 mA Peak Current CapabilityInternally Fixed Frequency at 40 kHz, 60 kHz and 100 kHzDirect Optocoupler ConnectionUndervoltage Lockout at 7.8 V TypicalSPICE Models Available for TRANsient and AC AnalysisPin to Pin Compatible with NCP1200Pb--Free Packages are Available
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MARKING DIAGRAM
8
SOIC--8
8
1
8
1
D1, D2 SUFFIX
CASE 751
x = 4, 6, or 1 A = Assembly Location L = Wafer Lot Y = Year W = Work Week G = Pb--Free Package
PDIP--8 N SUFFIX CASE 626
xx = 40, 60, or 100 A = Assembly Location WL = Wafer Lot YY = Year WW = Work Week G = Pb--Free Package
PIN CONNECTIONS
Adj
1
FB
2
CS
3
GND
4
(Top View)
8
7
6
5
8
1
1
1203Pxx
YYWWG
HV
NC
V
CC
Drv
203Dx ALYW
G
AWL
Applications
AC--DC Adapters for Notebooks, etc.Offline Battery ChargersAuxiliary Power Supplies (USB, Appliances, TVs, etc.)
Semiconductor Components Industries, LLC, 2010
December, 2010-- Rev. 10
ORDERING INFORMATION
See detailed ordering and shipping information in thepackage dimensions section on page 13 of this data sheet.
1
Publication Order Number:
NCP1203/D
NCP1203
*
+
EMI
FILTER
UNIVERSAL
INPUT
*Please refer to the application information section
+
NCP1203
HV
Adj
1
FB
2
CS
3
GND
4
V
CC
Drv
8
7
6
5
Aux.
+
Figure 1. Typical Application Example
PIN FUNCTION DESCRIPTION
Pin No. Pin Name Function Pin Description
1 Adj Adjust the skipping peak current This pin lets you adjust the level at which the cycle skipping process takes
2 FB Sets the peak current setpoint By connecting an optocoupler to this pin, the peak current setpoint is
3 CS Current sense input This pin senses the primary current and routes it to the internal comparator
4 GND The IC ground --
5 Drv Driving pulses The driver’s output to an external MOSFET.
6 V
7 NC -- This unconnected pin ensures adequate creepage distance.
8 HV Ensure a clean and lossless
CC
Supplies the IC
startup s equence
place. Shorting this pin to ground, permanently disables the skip cycle feature.
adjusted accordingly to the output power demand. Skip cycle occurs when FB falls below Vpin1.
viaanL.E.B.
This pin is connected to an external bulk capacitor of typically 22 mF.
Connected to the high--voltage rail, this pin injects a constant current into the V
capacitor during the startup sequence.
CC
V
OUT
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2
NCP1203
Adj
FB
CURRENT
SENSE
GROUND
HV
1
8
HV CURRENT SOURCE
80 k
1.2 V
2
SKIP CYCLE COMPARATOR
+
--
INTERNAL V
UVLO HIGH AND LOW
INTERNAL REGULATOR
CC
NC
7
24 k
Q FLIP--FLOP DCmax = 80%
3
250 ns
L.E.B.
40--60--100 kHz
CLOCK
20 k 57 k
V
4
REF
+
25 k
1V
SET
RESET
+
--
Q
OVERLOAD
MANAGEMENT
250 mA
V
6
Drv
5
CC
--
Figure 2. Internal Circuit Architecture
MAXIMUM RATINGS
Rating Symbol Value Unit
Power Supply Voltage VCC,Drv 16 V
Power Supply Voltage on all other pins except Pin 5 (Drv), Pin 6 (VCC) and Pin 8 (HV) -- --0.3to10 V
Maximum Current into all pins except Pin 6 (VCC) and Pin 8 (HV) when 10 V ESD diodes are activated
Thermal Resistance, Junction--to--Air, PDIP--8 Version Thermal Resistance, Junction--to--Air, SOIC Version Thermal Resistance, Junction--to--Case
Maximum Junction Temperature TJ
R R R
--
θ
JA
θ
JA
θ
JC
MAX
Temperature Shutdown -- 170 C
Hysteresis in Shutdown -- 30 C
Operating Temperature Range T
Storage Temperature Range T
J
stg
ESD Capability, Human Body Model, All pins except Pin 6 (VCC) and Pin 8 (HV) -- 2.0 kV
ESD Capability, Machine Model -- 200 V
MaximumVoltageonPin8(HV)withPin6(VCC) Decoupled to Ground with 10mF
-- 500 V
Stresses exceeding Maximum Ratings may damage the device. Maximum Ratings are stress ratings only. Functional operation above the Recommended Operating Conditions is not implied. Extended exposure to stresses above the Recommended Operating Conditions may affect device reliability.
5.0 mA
100
C/W
178
57
150 C
--40 to +125 C
--60 to +150 C
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NCP1203
ELECTRICAL CHARACTERISTICS (For typical values T
= 11 V unless otherwise noted.)
V
CC
Characteristic
=25C, for min/max values TJ=0C to +125C, Max TJ= 150C,
J
Symbol Pin Min Ty p Max Unit
Supply Section (All frequency versions, otherwise noted)
Turn--on Threshold Level, V
Minimum Operating Voltage after Turn--on V
VCCDecreasing Level at which the Latchoff Phase Ends V
Going Up V
CC
CC(on)
CC(min)
CClatch
6 12.2 12.8 14 V
6 7.2 7.8 8.4 V
6 -- 4.9 -- V
Internal IC Consumption, No Output Load on Pin 5 ICC1 6 -- 750 880
(Note 1)
Internal IC Consumption, 1.0 nF Output Load on Pin 5,
F
=40kHz
SW
Internal IC Consumption, 1.0 nF Output Load on Pin 5,
F
=60kHz
SW
Internal IC Consumption, 1.0 nF Output Load on Pin 5,
= 100 kHz
F
SW
ICC2 6 -- 1.2 1.4
(Note 2)
ICC2 6 -- 1.4 1.6
(Note 2)
ICC2 6 -- 2.0 2.2
(Note 2)
Internal IC Consumption, Latch--off Phase, VCC=6.0V ICC3 6 -- 250 --
Internal Startup Current Source (Pin8biasedat50V)
High--Voltage Current Source, V
=10V IC1 8 3.5 6.0 9.0 mA
CC
High--Voltage Current Source, VCC=0 IC2 8 -- 11 -- mA
Drive Output
Output Voltage Rise--Time @ CL = 1.0 nF, 10-- 90% of
T
r
5 -- 67 -- ns
Output Signal
Output Voltage Fall--Time @ CL = 1.0 nF, 10--90% of
T
f
5 -- 28 -- ns
Output Signal
Source Resistance R
Sink Resistance R
OH
OL
5 27 40 61
5 5.0 10 20
Current Comparator (Pin 5 loaded unless otherwise noted)
Input Bias Current @ 1.0 V Input Level on Pin 3
Maximum Internal Current Setpoint (Note 3) I
Default Internal Current Setpoint for Skip Cycle Operation I
Propagation Delay from Current Detection to Gate OFF
Limit
Lskip
T
I
IB
DEL
3 -- 0.02 --
3 0.85 0.92 1.0 V
3 -- 360 -- mV
3 -- 90 160 ns
State
Leading Edge Blanking Duration (Note 3) T
LEB
3 -- 230 -- ns
Internal Oscillator (VCC= 11 V, Pin 5 loaded by 1 nF)
Oscillation Frequency, 40 kHz Version
Oscillation Frequency, 60 kHz Version f
Oscillation Frequency, 100 kHz Version f
f
OSC
OSC
OSC
-- 37 42 47 kHz
-- 57 65 73 kHz
-- 90 103 11 5 kHz
Maximum Duty--Cycle Dmax -- 74 80 87 %
Feedback Section (VCC= 11 V, Pin 5 unloaded)
Internal Pullup Resistor
Rup 2 -- 20 --
Pin 3 to Current Setpoint Division Ratio Iratio -- -- 3.3 -- --
Skip Cycle Generation
Default S kip Mode Level
Vskip 1 1.0 1.2 1.4 V
Pin 1 Internal Output Impedance Zout 1 -- 22 --
1. Max value at TJ=0C.
2. Maximum value @ T
3. Pin 5 loaded by 1 nF.
=25C, please see characterization curves.
J
mA
mA
mA
mA
mA
Ω
Ω
mA
kΩ
kΩ
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NCP1203
14.0
13.8
13.6
13.4
13.2
13.0
THRESHOLD (V)
12.8
CC(on)
12.6
V
12.4
12.2
900
860
820
780
740
700
660
620
580
, CURRENT CONSUMPTION (mA)
540
CC
I
500
8.4
8.2
8.0
LEVEL (V)
7.8
7.6
CC(min)
V
7.4
7.2
--25 --25
TEMPERATURE (C) TEMPERATURE (C)
Figure 3. V
CC(on)
50
Threshold versus
75
100
-- 5 0 0
Figure 4. V
Temperature
2.0
1.9
1.8
1.7
1.6
1.5
1.4
1.3
1.2
, 1 nF LOAD CONSUMPTION (mA)
1.1
CC
I
-- 2 5
1251007550250-- 5 0
TEMPERATURE (C)
1.0
25250 125
CC(min)
Level versus Temperature
100 kHz
60 kHz
40 kHz
TEMPERATURE (C)
50 75 100
125-- 5 0
1251007550250-- 5 0 -- 2 5
HV CURRENT SOURCE (mA)
Figure 5. ICCurrent Consumption (No Load)
versus Temperature
8.0
7.5
7.0
6.5
6.0
5.5
5.0
4.5
4.0
-- 2 5
TEMPERATURE (C)
60 kHz
40 kHz
100 kHz
Figure 7. HV Current Source at VCC=10V
versus Temperature
400
350
300
=6V(mA)
CC
250
@V
CC
I
200
1251007550250-- 5 0
150
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5
Figure 6. ICCConsumption (Loaded by 1 nF)
versus Temperature
-- 2 5
TEMPERATURE (C)
Figure 8. ICConsumption at VCC=6V
versus Temperature
1251007550250-- 5 0
NCP1203
DRIVE SOURCE RESISTANCE (Ω)
MAXIMUM CURRENT SETPOINT (V)
60
55
50
45
40
35
30
25
20
15
0.99
0.97
0.95
0.93
0.91
0.89
0.87
0.85
75
100
-- 2 5 -- 2 5
TEMPERATURE (C) TEMPERATURE (C)
50
Figure 9. Drive Source Resistance versus
Temperature
-- 5 0
-- 2 5
TEMPERATURE (C) TEMPERATURE (C)
50
75
100250 125
20
18
16
14
12
10
8
6
DRIVE SINK RESISTANCE (Ω)
4
2
-- 5 0 0
Figure 10. Drive Sink Resistance versus
120
100
80
60
40
f, FREQUENCY (kHz)
20
0
-- 2 5
25250 125
50 75 100
Temperature
100 kHz
60 kHz
40 kHz
125-- 5 0
1251007550250-- 5 0
Figure 11. Maximum Current Setpoint versus
Temperature
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Figure 12. Frequency versus Temperature
6
NCP1203
APPLICATION INFORMATION
Introduction
The NCP1203 implements a standard current mode architecture where the switch--off time is dictated by the peak current setpoint. This component represents the ideal candidate where low part--count is the key parameter, particularly in low--cost AC--DC adapters, auxiliary supplies etc. Due to its high--performance SMARTMOS High--Voltage technology, the NCP1203 incorporates all the necessary components normally needed in UC384X based supplies: timing components, feedback devices, low--pass filter and startup device. This later point emphasizes the fact that ON Semiconductor’s NCP1203 does not need an external startup resistance but supplies the startup current directly from the high--voltage rail. On the other hand, more and more applications are requiring low no--load standby power, e.g. for AC--DC adapters, VCRs etc. UC384X series have a lot of difficulty to reduce the switching losses at low power levels. NCP1203 elegantly solves this problem by
12.8 V /4.9 V
+
--
6mAor0
skipping unwanted switching cycles at a user--adjustable power level. By ensuring that skip cycles take place at low peak current, the device ensures quiet, noise free operation. Finally, an auto--recovery output short--circuit protection (OCP) prevents from any lethal thermal runaway in overload conditions.
Startup Sequence
When the power supply is first powered from the mains outlet, the internal current source (typically 6.0 mA) is biased and charges up the V on this V
capacitor reaches the V
CC
capacitor. When the voltage
CC
level (typically
CC(on)
12.8 V), the current source turns off and no longer wastes any power. At this time, the V
capacitor only supplies the
CC
controller and the auxiliary supply is supposed to take over before V
collapses below V
CC
. Figure 13 shows the
CC(min)
internal arrangement of this structure:
8
6
HV
Figure 13. The Current Source Brings VCCAbove 12.8 V and then Turns Off
Once the power supply has started, the VCCshall be constrained below 16 V, which is the maximum rating on pin 6. Figure 14 portrays a typical startup sequence with a V
regulated at 12.5 V:
CC
CV
CC
4
13.5
12.5
11. 5
10.5
9.5
Figure 14. A Typical Startup Sequence for
12.8 V
3.00 M 8.00 M 13.0 M 18.0 M 23.0 M
Aux
t, TIME (sec)
the NCP1203
REGULATION
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NCP1203
Current--Mode Operation
As the UC384X series, the NCP1203 features a well--known current mode control architecture which provides superior input audio--susceptibility compared to traditional voltage--mode controllers. Primary current pulse--by--pulse checking together with a fast over current comparator offers greater security in the event of a difficult fault condition, e.g. a saturating transformer.
Adjustable Skip Cycle Level
By offering the ability to tailor the level at which the skip cycle takes place, the designer can make sure that the skip operation only occurs at low peak current. This point guarantees a noise--free operation with cheap transformers. Skip cycle offers a proven mean to reduce the standby power in no or light loads situations.
Wide Switching--Frequency Offer
Four different options are available: 40 kHz -- 65 kHz – 100 kHz. Depending on the application, the designer can pick up the right device to help reducing magnetics or improve the EMI signature before reaching the 150 kHz starting point.
Overcurrent Protection (OCP)
When the auxiliary winding collapses below UVLOlow, the controller stops switching and reduces its consumption. It stays in this mode until Vcc reaches 4.9 V typical, where the startup source is reactivated and a new startup sequence is attempted. The power supply is thus operated in burst mode and avoids any lethal thermal runaway. When the default goes way, the power supply automatically resumes operation.
Wide Duty--Cycle Operation
Wide mains operation requires a large duty--cycle excursion. The NCP1203 can go up to 80% typically.
Low Standby Power
If SMPS naturally exhibit a good efficiency at nominal load, they begin to be less efficient when the output power demand diminishes. By skipping un--needed switching cycles, the NCP1203 drastically reduces the power wasted during light load conditions. In no--load conditions, the NCP1203 allows the total standbypower to easily reachnext International Energy Agency (IEA) recommendations.
No Acoustic Noise while Operating
Instead of skipping cycles at high peak currents, the NCP1203 waits until the peak current demand falls below a user--adjustable 1/3
rd
of the maximum limit. As a result,
cycle skipping can take place without having a singing
transformer You can thus select cheap magnetic components free of noise problems.
External MOSFET Connection
By leaving the external MOSFET external to the IC, you can select avalanche proof devices which, in certain cases (e.g. low output powers), let you work without an active clamping network. Also, by controlling the MOSFET gate signal flow, you have an option to slow down the device commutation, therefore reducing the amount of ElectroMagnetic Interference (EMI).
SPICE Model
A dedicated model to run transient cycle--by--cycle simulations is available but also an averaged version to help you closing the loop. Ready--to--use templates can be downloaded in OrCAD’sPspice and INTUSOFT’sfrom ON Semiconductor web site, NCP1203 related section.
Overload Operation
In applications where the output current is purposely not controlled (e.g. wall adapters delivering raw DC level), it is interesting to implement a true short--circuit protection. A short--circuit actually forces the output voltage to be at a low level, preventing a bias current to circulate in the optocoupler LED. As a result, the auxiliary voltage also decreases because it also operates in Flyback and thus duplicates the output voltage, providing the leakage inductance between windings is keptlow.Toaccount for this situation and properly protect the power supply, NCP1203 hosts a dedicated overload detection circuitry. Once activated, this circuitry imposes to deliver pulses in a burst manner with a low duty--cycle. The system auto--recovers when the fault condition disappears.
During the startup phase, the peak current is pushed to the maximum until the output voltage reaches its target and the feedback loop takes over. The auxiliary voltage takes place after a few switching cycles and self--supplies the IC. In presence of a short circuit on the output, the auxiliary voltage will go down until it crosses the undervoltage lockout level of typically 7.8 V. When this happens, NCP1203 immediately stops the switching pulses and unbias all unnecessary logical blocks. The overall consumption drops, while keeping the gate grounded, and the V
slowly falls down. As soon as VCCreaches typically
CC
4.8 V, the startup source turns--on again and a new startup sequence occurs, bringing V
toward 12.8 V as an attempt
CC
to restart. If the default has gone, then the power supply normally restarts. If not, a new protective burst is initiated, shielding the SMPS from any runaway. Figure 15, on the following page, portrays the typical operating signals in short circuit.
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NCP1203
12.8 V
Figure 15. Typical Waveforms in Short Circuit Conditions
Calculating the VCCCapacitor
7.8 V
4.9 V
The VCCcapacitor can be calculated knowing the IC
consumption as soon as V
reaches 12.8 V. Suppose that a
CC
NCP1203P60 is used and drives a MOSFET with a 30 nC total gate charge (Qg). The total average current is thus made of ICC1 (700 mA) plus the driver current, Fsw x Qg or
1.8 mA. The total current is therefore 2.5 mA. The ΔV available to fully startup the circuit (e.g. never reach the
7.8 V UVLO during power on) is 12.8–7.8 = 5 V. We have a capacitor who then needs to supply the NCP1203 with
2.5 mA during a given time until the auxiliary supply takes over. Suppose that this time was measured at around 15 ms.
CV
C 7.5 mF
Skipping Cycle Mode
is calculated using the equation
CC
. Select a 22 mF/16 V and this will fit.
C =
Δt·i
ΔV
The NCP1203 automatically skips switching cycles when the output power demand drops below a given level. This is accomplished by monitoring the FB pin. In normal operation, pin 2 imposes a peak current accordingly to the load value. If the load demand decreases, the internal loop asks for less peak current. When this setpoint reaches a determined level (Vpin 1), the IC prevents the current from decreasing further down and starts to blank the output pulses: the IC enters the so--called skip cycle mode, also named controlled burst operation. The power transfer now depends upon the width of the pulse bunches (Figure 17). Suppose we have the following component values:
Lp, primary inductance = 350 mH Fsw , switching frequency = 61 kHz Ip skip = 600 mA (or 333 mV/Rsense)
or
V
CC
DRIVING PULSES
The theoretical power transfer is therefore:
1
·Lp·Ip2·Fsw= 3.8 W
2
If this IC enters skip cycle mode with a bunch length of 10 ms overa recurrent period of 100 ms, then the total power transfer is:
3.8 . 0.1 = 380 mW
.
To better understand how this skipcycle mode takesplace, a look at the operation mode versus the FB level immediately gives the necessary insight:
FB
4.2 V, FB Pin Open
3.2 V, Upper NORMAL CURRENT MODE OPERATION
SKIP CYCLE OPERATION I
= 333 mV/R
P(min)
SENSE
Figure 16.
Dynamic Range
1V
When FB is above the skip cycle threshold (1.0 V by default), the peak current cannot exceed 1.0 V/Rsense. When the IC enters the skip cycle mode, the peak current cannot go below Vpin1/3.3/Rsense. The user still has the flexibility to alter this 1.0 V by either shunting pin 1 to ground through a resistor or raising it through a resistor up to the desired level. Grounding pin 1 permanently invalidates the skip cycle operation. However, given the extremely low standby power the controller can reach, the PWM in no--load conditions can quickly enter the minimum t
and still transfer too much power. An instability can take
on
place. We recommend in that case to leave a little bit of skip level to always allow 0% duty cycle.
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NCP1203
Figure 17. Output Pulses at Various Power Levels (X = 5.0 ms/div) P1 < P2 < P3
Power P1
Power P2
Power P3
300 M
200 M
100 M
0
315.40 882.70 1.450 M 2.017 M 2.585 M
Figure 18. The Skip Cycle Takes Place at Low Peak Currents which Guaranties Noise--Free Operation
MAX PEAK
CURRENT
We recommend a pin 1 operation between 400 mV and
1.3 V that will fix the skip peak current level between 120 mV/Rsense and 390 mV/Rsense.
Non--Latching Shutdown
In some cases, it might be desirable to shut off the part
temporarily and authorize its restart once the default has
SKIP CYCLE
CURRENT LIMIT
disappeared. This option can easily be accomplished through a single NPN bipolar transistor wired between FB and ground. By pulling FB below the Adj pin 1 level, the output pulses are disabled as long as FB is pulled below pin 1. As soon as FB is relaxed, the IC resumes its operation. Figure 19 depicts the application example.
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NCP1203
ON/OFF
Figure 19. Another Way of Shutting Down the IC without a Definitive Latch--Off State
Full Latching Shutdown
Other applications require a full latching shutdown, e.g. when an abnormal situation is detected (overtemperature or overvoltage). This feature can easily be implemented through two external transistors wired as a discrete SCR.
OVP
10 k
0.1 mF
10 k
8
7
6
5
Q1
When the V
1
2
3
4
level exceeds the zener breakdown voltage,
CC
the NPN biases the PNP and fires the equivalent SCR, permanently bringing down the FB pin. The switching pulses are disabled until the user unplugs the power supply.
Rhold
12 k
NCP1203
1
2
3
4
8
7
6
5
CV
CC
LAux
Figure 20. Two Bipolars Ensure a Total Latch--Off of the SMPS in Presence of an OVP
Rhold ensures that the SCR stays on when fired. The bias current flowing through Rhold should be small enough to let the V
ramp up (12.8 V) and down (4.9 V) when the SCR
CC
is fired. The NPN base can also receive a signal from a temperature sensor. Typical bipolars can be MMBT2222 and MMBT2907 for the discrete latch. The MMBT3946 features two bipolars NPN+PNP in the same package and could also be used.
Protecting the Controller Against Negative Spikes
As with any controller built upon a CMOS technology, it is the designer’s duty to avoid the presence of negative spikes on sensitive pins. Negative signals have the bad habit to forward bias the controller substrate and induce erratic behaviors. Sometimes, the injection can be so strong that internal parasitic SCRs are triggered, engendering irremediable damages to the IC if they are a low impedance path is offered between V
and GND. If the current sense
CC
pin is often the seat of such spurious signals, the high--voltage pin can also be the source of problems in certain circumstances. During the turn--off sequence, e.g. when the user un--plugs the power supply, the controller is still fed by its V
capacitor and keeps activating the
CC
MOSFET ON and OFF with a peak current limited by Rsense. Unfortunately, if the quality coefficient Q of the resonating network formed by Lp and Cbulk is low (e.g. the MOSFET Rdson + Rsense are small), conditions are met to make the circuit resonate and thus negatively bias the controller. Since we are talking about ms pulses, the amount of injected charge (Q = I x t) immediately latches the controller which brutally dischargesits V V
capacitor is of sufficient value, its stored energy
CC
capacitor.If this
CC
damages the controller. Figure 21 depicts a typical negative shot occurring on the HV pinwhere the brutal V
discharge
CC
testifies for latchup.
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NCP1203
Figure 21. A negative spike takes place on the Bulk capacitor at the switch--off sequence
Simple and inexpensive cures exist to prevent from internal parasitic SCR activation. One of them consists in inserting a resistor in series with the high--voltage pin to keep the negative current to the lowest when the bulk becomes negative (Figure 22). Please note that the negative spike is clamped to –2 x Vf due to the diode bridge. Also, the power dissipation of this resistor is extremely small since it only heats up during the startup sequence.
Rbulk >4.7k
+
Cbulk
1
2
3
4
Figure 22. A simple resistor in series avoids any
latchup in the controller
8
7
6
5
+
CV
CC
Another option (Figure 23) consists in wiring a diodefrom
V
to the bulk capacitor to force VCCto reach UVLOlow
CC
sooner and thus stops the switching activity before the bulk capacitor gets deeply discharged. For security reasons, two diodes can be connected in series.
+
Cbulk
1
2
3
4
Figure 23. or a diode forces VCCto reach
UVLOlow sooner
8
7
6
5
D3 1N4007
+
CV
CC
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NCP1203
ORDERING INFORMATION
Device Package Shipping
NCP1203P40G PDIP--8
(Pb--Free)
NCP1203D40R2G SOIC--8
(Pb--Free)
NCP1203P60G PDIP--8
(Pb--Free)
NCP1203D60R2 SOIC--8 2500 Units / Tape & Reel
NCP1203D60R2G SOIC--8
(Pb--Free)
NCP1203P100G PDIP --8
(Pb--Free)
NCP1203D100R2G SOIC--8
(Pb--Free)
†For information on tape and reel specifications, including part orientation and tape sizes, please refer to our Tape and Reel Packaging
Specifications Brochure, BRD8011/D.
50 Units / Rail
2500 Units / Tape & Reel
50 Units / Rail
2500 Units / Tape & Reel
50 Units / Rail
2500 Units / Tape & Reel
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-- Z --
-- Y --
NCP1203
PACKAGE DIMENSIONS
SOIC--8 NB
CASE 751--07
ISSUE AJ
-- X --
B
H
A
58
1
4
G
D
0.25 (0.010) Z
M
S
Y
0.25 (0.010)
C
SEATING PLANE
SXS
M
M
Y
N
X45
_
0.10 (0.004)
M
SOLDERING FOOTPRINT*
K
J
NOTES:
1. DIMENSIONING AND TOLERANCING PER ANSI Y14.5M, 1982.
2. CONTROLLING DIMENSION: MILLIMETER.
3. DIMENSION A AND B DO NOT INCLUDE MOLD PROTRUSION.
4. MAXIMUM MOLD PROTRUSION 0.15 (0.006) PER SIDE.
5. DIMENSION D DOES NOT INCLUDE DAMBAR PROTRUSION. ALLOWABLE DAMBAR PROTRUSION SHALL BE 0.127 (0.005) TOTAL IN EXCESS OF THE D DIMENSION AT MAXIMUM MATERIAL CONDITION .
6. 751--01 THRU 751-- 06 ARE OBSOLETE. NEW STANDARD IS 751 --07.
MILLIMETERS
DIMAMIN MAX MIN MAX
4.80 5.00 0.189 0.197
B 3.80 4.00 0.150 0.157 C 1.35 1.75 0.053 0.069 D 0.33 0.51 0.013 0.020 G 1.27 BSC 0.050 BSC H 0.10 0.25 0.004 0.010 J 0.19 0.25 0.007 0.010 K 0.40 1.27 0.016 0.050 M 0808
____
N 0.25 0.50 0.010 0.020 S 5.80 6.20 0.228 0.244
INCHES
1.52
0.060
7.0
0.275
0.6
0.024
4.0
0.155
1.270
0.050
SCALE 6:1
inches
mm
*For additional information on our Pb--Free strategy and soldering
details, please download the ON Semiconductor Soldering and Mounting Techniques Reference Manual, SOLDERRM/D.
http://onsemi.com
14
NOTE 5
l
D
D1
14
TOP VIEW
e/2
NCP1203
PACKAGE DIMENSIONS
8LEADPDIP
CASE 626--05
ISSUE M
NOTES:
A
58
E
E1
F
c
E2
END VIEW
NOTE 3
A
L
1. DIMENSIONING AND TOLERANCING PER ASME Y14.5M, 1994.
2. CONTROLLING DIMENSION: INCHES.
3. DIMENSION E IS MEASURED WITH THE LEADS RE­STRAINED PARALLEL AT WIDTH E2.
4. DIMENSION E1 DOES NOT INCLUDE MOLD FLASH.
5. ROUNDED CORNERS OPTIONAL.
DIM MIN NOM MAX
A -- -- -- -- -- -- -- -- 0 . 2 1 0
A1 0.015 -------- --------
b 0.014 0.018 0.022 C 0.008 0.010 0.014 D 0.355 0.365 0.400
D1 0.005 -------- --------
E 0.300 0.310 0.325 E1 0.240 0.250 0.280 6.10 6.35 7.11 E2 E3 -- -- -- -- -- -- -- -- 0 . 4 3 0 -- -- -- -- -- -- -- -- 1 0 . 9 2
e 0.100 BSC L 0.115 0.130 0.150
INCHES
0.300 BSC 7.62 BSC
MILLIMETERS
MIN NOM MAX
-- -- -- -- -- -- -- -- 5 . 3 3 0 . 3 8 -- -- -- -- -- -- -- --
0.35 0.46 0.56
0.20 0.25 0.36
9.02 9.27 10.02 0 . 1 3 -- -- -- -- -- -- -- --
7.62 7.87 8.26
2.54 BSC
2.92 3.30 3.81
A1
e
8X
SIDE VIEW
SEATING
C
PLANE
b
M
0.010 CA
E3
END VIEW
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NCP1203/D
15
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