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LM7341
Datasheet (National Semiconductor)
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Datasheet LM7341 Datasheet (National Semiconductor)

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October 13, 2008
LM7341 Rail-to-Rail Input/Output ±15V, 4.6 MHz GBW, Operational Amplifier in SOT-23 Package
LM7341 Rail-to-Rail Input/Output, ±15V, 4.6 MHz GBW, Operational Amplifier in SOT-23 Package

General Description

The LM7341 is a rail-to-rail input and output amplifier in a small SOT-23 package with a wide supply voltage and tem­perature range. The LM7341 has a 4.6 MHz gain bandwidth and a 1.9 volt per microsecond slew rate, and draws 0.75 mA of supply current at no load.
The LM7341 is tested at −40°C, 125°C and 25°C with modern automatic test equipment. Detailed performance specifica­tions at 2.7V, ±5V, and ±15V and over a wide temperature range make the LM7341 a good choice for automotive, in­dustrial, and other demanding applications.
Greater than rail-to-rail input common mode range with a minimum 76 dB of common mode rejection at ±15V makes the LM7341 a good choice for both high and low side sensing applications.
LM7341 performance is consistent over a wide voltage range, making the part useful for applications where the supply volt­age can change, such as automotive electrical systems and battery powered electronics.
The LM7341 uses a small SOT23-5 package, which takes up little board space, and can be placed near signal sources to reduce noise pickup.

Features

(VS = ±15V, TA = 25°C, typical values.)
Tiny 5-pin SOT-23 package saves space
■
Greater than rail-to-rail input CMVR −15.3V to 15.3V
■
Rail-to-rail output swing −14.84V to 14.86V
■
Supply current 0.7 mA
■
Gain bandwidth 4.6 MHz
■
Slew Rate 1.9 V/µs
■
Wide supply range 2.7V to 32V
■
High power supply rejection ratio 106 dB
■
High common mode rejection ratio 115 dB
■
Excellent gain 106 dB
■
Temperature range −40°C to 125°C
■
Tested at −40°C, 125°C and 25°C at 2.7V, ±5V and ±15V
■

Applications

Automotive
■
Industrial robotics
■
Sensor output buffers
■
Multiple voltage power supplies
■
Reverse biasing of photodiodes
■
Low current optocouplers
■
High side sensing
■
Comparator
■
Battery chargers
■
Test point output buffers
■
Below ground current sensing
■

Typical Performance Characteristics

Open Loop Frequency Response
20206046
© 2008 National Semiconductor Corporation 202060 www.national.com
Open Loop Frequency Response
20206047

Absolute Maximum Ratings (Note 1)

If Military/Aerospace specified devices are required,
LM7341
please contact the National Semiconductor Sales Office/ Distributors for availability and specifications.
ESD Tolerance (Note 2) Human Body Model 2000V Machine Model 200V Charge-Device Model 1000V VIN Differential
Voltage at Input/Output Pin (V+) + 0.3V, (V−) −0.3V
Supply Voltage (VS = V+ − V−)
Input Current ±10 mA Output Current(Note 3) ±20 mA
±15V
35V
Power Supply Current 25 mA Soldering Information Infrared or Convection (20 sec) 235°C Wave Soldering Lead Temp.
(10 sec.) 260°C Storage Temperature Range −65°C to 150°C Junction Temperature (Note 4) 150°C

Operating Ratings (Note 1)

Supply Voltage (VS = V+ − V−)
Temperature Range (Note 4) −40°C to 125°C
Package Thermal Resistance (θJA)
5-Pin SOT-23 325°C/W

2.7V Electrical Characteristics

Unless otherwise specified, all limits guaranteed for TA = 25°C, V+ = 2.7V, V− = 0V, VCM = 0.5V, V
1.35V. Boldface limits apply at the temperature extremes
Symbol Parameter Conditions Min
(Note 6)
V
OS
Input Offset Voltage VCM = 0.5V and VCM = 2.2V −4
−5
TCV
I
B
Input Offset Voltage Temperature Drift ±2
OS
Input Bias Current VCM = 0.5V −180
−200
VCM = 2.2V 30 60
I
OS
CMRR Common Mode Rejection Ratio
Input Offset Current VCM = 0.5V and VCM = 2.2V 1 40
0V ≤ VCM ≤ 1.0V
82
80
0V ≤ VCM ≤ 2.7V
62
60
PSRR Power Supply Rejection Ratio
2.7V ≤ VS ≤ 30V VCM = 0.5V
86
84
CMVR Common Mode Voltage Range CMRR > 60 dB −0.3 0.0
2.7 3.0
A
VOL
V
OUT
Open Loop Voltage Gain
Output Voltage Swing High
0.5V ≤ VO ≤ 2.2V
RL = 10 kΩ to 1.35V
RL = 10 kΩ to 1.35V VID = 100 mV
RL = 2 kΩ to 1.35V
12
8
50 120
95 150
VID = 100 mV
Output Voltage Swing Low
RL = 10 kΩ to 1.35V VID = −100 mV
RL = 2 kΩ to 1.35V
55 120
100 150
VID = −100 mV
I
OUT
I
S
Output Current Sourcing, V
VID = 200 mV
Sinking, V VID = −200 mV
OUT
OUT
= 0V
= 0V
6
4
5
3
Supply Current VCM = 0.5V and VCM = 2.2V 0.6 0.9
SR Slew Rate ±1V Step 1.5
= 1.35V and RL > 1 MΩ to
OUT
Typ
(Note 5)
±0.2 +4
−90
106
80
106 dB
65
12
10
Max
(Note 6)
+5
70
50
150
200
150
200
1.0
2.5V to 32V
Units
mV
μV/°C
nA
nA
dB
V
V/mV
mV from
either rail
mA
mA
V/μs
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LM7341
Symbol Parameter Conditions Min
(Note 6)
GBW Gain Bandwidth
e
n
i
n
Input Referred Voltage Noise Density f = 1 kHz 35
Input Referred Voltage Noise Density f = 1 kHz 0.28
f = 100 kHz, RL = 100 kΩ
3.6 MHz
Typ
(Note 5)
Max
(Note 6)
Units
nV/
pA/
THD+N Total Harmonic Distortion + Noise f = 10 kHz −66 dB
t
PD
t
r
t
f
Propagation Delay Overdrive = 50 mV (Note 7) 4
Overdrive = 1V (Note 7) 3
µs
Rise Time 20% to 80% (Note 7) 1 µs
Fall Time 80% to 20% (Note 7) 1 µs

±5V Electrical Characteristics

Unless otherwise specified, all limits guaranteed for TA = 25°C, V+ = +5V, V− = −5V, VCM = V
Boldface limits apply at the temperature extremes.
Symbol Parameter Conditions Min
(Note 6)
V
OS
TCV
I
B
Input Offset Voltage VCM = −4.5V and VCM = 4.5V −4
Input Offset Voltage Temperature Drift ±2
OS
Input Bias Current VCM = −4.5V −200
−250
VCM = 4.5V 35 70
I
OS
CMRR Common Mode Rejection Ratio
Input Offset Current VCM = −4.5V and VCM = 4.5V 1 40
−5V ≤ VCM ≤ 3V
−5V ≤ VCM ≤ 5V
PSRR Power Supply Rejection Ratio
CMVR Common Mode Voltage Range
A
VOL
Open Loop Voltage Gain
2.7V ≤ VS ≤ 30V, VCM = −4.5V
CMRR ≥ 65 dB
−4V ≤ VO ≤ 4V
RL = 10 kΩ to 0V
V
OUT
Output Voltage Swing High
RL = 10 kΩ to 0V, VID = 100 mV
RL = 2 kΩ to 0V, VID = 100 mV
Output Voltage Swing Low
RL = 10 kΩ to 0V VID = −100 mV
RL = 2 kΩ to 0V VID = −100 mV
I
OUT
Output Current Sourcing, V
OUT
= −5V
VID = 200 mV
Sinking, V
OUT
= 5V
VID = −200 mV
I
S
Supply Current VCM = −4.5V and VCM = 4.5V 0.65 1.0
SR Slew Rate ±4V Step 1.7
GBW Gain Bandwidth
f = 100 kHz, RL = 100 kΩ
= 0V and RL > 1 MΩ to 0V.
OUT
Typ
(Note 5)
Max
(Note 6)
Units
±0.2 +4
−5
+5
μV/°C
−95
80
50
84
112
82
72
92
70
86
106
84
−5.3 −5.0
5.0 5.3
20
12
110
V/mV
80 150
200
170 300
400
90 150
mV from
either rail
200
210 300
400
6
11
4
6
12
4
1.1
4.0 MHz
mV
nA
nA
dB
dB
mA
mA
V/μs
V
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Symbol Parameter Conditions Min
LM7341
e
n
i
n
Input Referred Voltage Noise Density f = 1 kHz 33
Input Referred Voltage Noise Density f = 1 kHz 0.26
(Note 6)
Typ
(Note 5)
Max
(Note 6)
THD+N Total Harmonic Distortion + Noise f = 10 kHz −66 dB
t
PD
Propagation Delay Overdrive = 50 mV (Note 7) 8
Overdrive = 1V (Note 7) 6
t
r
t
f
Rise Time 20% to 80% (Note 7) 5 µs
Fall Time 80% to 20% (Note 7) 5 µs

±15V Electrical Characteristics

Unless otherwise specified, all limits guaranteed for TA = 25°C, V+ = 15V, V− = −15V, VCM = V
Boldface limits apply at the temperature extremes
Symbol Parameter Conditions Min
(Note 6)
V
OS
Input Offset Voltage V
= −14.5V and VCM = 14.5V −4
CM
−5
TCV
I
B
Input Offset Voltage Temperature Drift ±2
OS
Input Bias Current VCM = −14.5V −250
−300
VCM = 14.5V 40 80
I
OS
CMRR Common Mode Rejection Ratio
Input Offset Current VCM = −14.5V and VCM = 14.5V 1 40
−15V ≤ VCM ≤12V
84
82
−15V ≤ VCM ≤ 15V
78
76
PSRR Power Supply Rejection Ratio
2.7V ≤ VS ≤ 30V, VCM = −14.5V
86
84
CMVR Common Mode Voltage Range CMRR > 80 dB −15.3 −15.0
15.0 15.3
A
V
I
OUT
I
S
VOL
OUT
Open Loop Voltage Gain
Output Voltage Swing High
Output Voltage Swing Low
Output Current (Note 4)
−13V ≤ VO ≤ 13V
RL = 10 kΩ to 0V
RL = 10 kΩ to 0V VID = 100 mV
RL = 10 kΩ to 0V VID = −100 mV
Sourcing, V
OUT
= −15V
VID = 200 mV
Sinking, V
OUT
= 15V
VID = −200 mV
25
15
5
3
8
5
Supply Current VCM = −14.5V and VCM = 14.5V 0.7 1.2
SR Slew Rate ±12V Step 1.9
GBW Gain Bandwidth
e
n
i
n
Input Referred Voltage Noise Density f = 1 kHz 31
Input Referred Voltage Noise Density f = 1 kHz 0.27
f = 100 kHz, RL = 100 kΩ
THD+N Total Harmonic Distortion + Noise f = 10 kHz −65 dB
t
PD
Propagation Delay Overdrive = 50 mV (Note 7) 17
Overdrive = 1V (Note 7) 12
= 0V and RL > 1 MΩ to 0V.
OUT
Typ
(Note 5)
Max
(Note 6)
±0.2 +4
+5
−110
90
50
115
100
106
200
135 300
400
160 300
400
10
13
1.3
4.6 MHz
Units
nV/
pA/
µs
Units
mV
μV/°C
nA
nA
dB
dB
V
V/mV
mV from
either rail
mA
mA
V/μs
nV/
pA/
µs
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LM7341
Symbol Parameter Conditions Min
(Note 6)
t
r
t
f
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics.
Note 2: Human Body Model, applicable std. MIL-STD-883, Method 3015.7. Machine Model, applicable std. JESD22-A115-A (ESD MM std. of JEDEC)
Field-Induced Charge-Device Model, applicable std. JESD22-C101-C (ESD FICDM std. of JEDEC).
Note 3: Applies to both single-supply and split-supply operation. Continuous short circuit operation at elevated ambient temperature can result in exceeding the maximum allowed junction temperature of 150°C.
Note 4: The maximum power dissipation is a function of T PD = (T
Note 5: Typical values represent the most likely parametric norm as determined at the time of characterization. Actual typical values may vary over time and will also depend on the application and configuration. The typical values are not tested and are not guaranteed on shipped production material.
Note 6: All limits are guaranteed by testing or statistical analysis.
Note 7: The maximum differential voltage between the input pins is VIN Differential = ±15V.
Rise Time 20% to 80% (Note 7) 13 µs
Fall Time 80% to 20% (Note 7) 13 µs
, θJA. The maximum allowable power dissipation at any ambient temperature is
− TA)/θJA. All numbers apply for packages soldered directly unto a PC board.
J(MAX)
J(MAX)
Typ
(Note 5)
Max
(Note 6)

Connection Diagram

5-Pin SOT-23
Units
Top View
20206002

Ordering Information

Package Part Number Package Marking Transport Media NSC Drawing
5-Pin SOT-23
LM7341MF
AV4A
LM7341MFX 3k Units Tape and Reel
1k Units Tape and Reel
MF05ALM7341MFE 250 Units Tape and Reel
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Typical Performance Characteristics

LM7341
Output Swing vs. Sourcing Current
Output Swing vs. Sourcing Current
20206030
Output Swing vs. Sinking Current
20206033
Output Swing vs. Sinking Current
20206031
Output Swing vs. Sourcing Current
20206032
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20206034
Output Swing vs. Sinking Current
20206035
LM7341
VOS Distribution
VOS vs. VCM (Unit 2)
20206040
VOS vs. VCM (Unit 1)
20206003
VOS vs. VCM (Unit 3)
VOS vs. VCM (Unit 1)
20206004
20206006
20206008
VOS vs. VCM (Unit 2)
20206007
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LM7341
VOS vs. VCM (Unit 3)
VOS vs. VCM (Unit 1)
VOS vs. VCM (Unit 2)
VOS vs. VS (Unit 1)
20206011
20206009
20206010
VOS vs. VCM (Unit 3)
20206005
VOS vs. VS (Unit 2)
20206012
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20206013
LM7341
VOS vs. VS (Unit 3)
VOS vs. VS (Unit 2)
20206014
VOS vs. VS (Unit 1)
20206015
VOS vs. VS (Unit 3)
I
BIAS
vs. V
CM
20206016
20206018
I
BIAS
vs. V
20206017
CM
20206019
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LM7341
I
BIAS
vs. V
CM
I
BIAS
vs. V
S
I
vs. V
BIAS
IS vs. V
CM
20206020
S
20206024
IS vs. V
IS vs. V
CM
CM
20206021
20206025
20206026
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20206027
LM7341
IS vs. V
CM
20206028
Positive Output Swing vs. Supply Voltage
IS vs. V
CM
20206029
Positive Output Swing vs. Supply Voltage
20206036
Negative Output Swing vs. Supply Voltage
20206038
20206037
Negative Output Swing vs. Supply Voltage
20206039
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LM7341
Open Loop Frequency with Various Capacitive Load
Open Loop Frequency with Various Resistive Load
20206044
Open Loop Frequency with Various Supply Voltage
20206046
CMRR vs. Frequency
20206045
Open Loop Frequency Response with Various Temperatures
20206047
+PSRR vs. Frequency
20206043
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20206041
LM7341
-PSRR vs. Frequency
Large Signal Step Response
Small Signal Step Response
20206051
20206042
Input Referred Noise Density vs. Frequency
20206052
Input Referred Noise Density vs. Frequency
20206049
20206048
Input Referred Noise Density vs. Frequency
20206050
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THD+N vs. Frequency
LM7341

Application Information

GENERAL INFORMATION

Low supply current and wide bandwidth, greater than rail-to­rail input range, full rail-to-rail output, good capacitive load driving ability, wide supply voltage and low distortion all make the LM7341 ideal for many diverse applications.
The high common-mode rejection ratio and full rail-to-rail in­put range provides precision performance when operated in non-inverting applications where the common-mode error is added directly to the other system errors.

CAPACITIVE LOAD DRIVING

The LM7341 has the ability to drive large capacitive loads. For example, 1000 pF only reduces the phase margin to about 30 degrees.

POWER DISSIPATION

Although the LM7341 has internal output current limiting, shorting the output to ground when operating on a +30V pow­er supply will cause the op amp to dissipate about 350 mW. This is a worst-case example. In the 5-pin SOT-23 package, the higher thermal resistance will cause a calculated rise of 113°C. This can raise the junction temperature to above the absolute maximum temperature of 150°C.
Operating from split supplies greatly reduces the power dis­sipated when the output is shorted. Operating on ±15V sup­plies can only cause a temperature rise of 57°C in the 5-pin SOT-23 package, assuming the short is to ground.

WIDE SUPPLY RANGE

The high power-supply rejection ratio (PSRR) and common mode rejection ratio (CMRR) provide precision performance when operated on battery or other unregulated supplies. This advantage is further enhanced by the very wide supply range (2.5V–32V) offered by the LM7341. In situations where highly variable or unregulated supplies are present, the excellent PSRR and wide supply range of the LM7341 benefit the sys­tem designer with continued precision performance, even in such adverse supply conditions.
20206053

SPECIFIC ADVANTAGES OF 5-Pin SOT-23 (TinyPak)

The obvious advantage of the 5-pin SOT-23, TinyPak, is that it can save board space, a critical aspect of any portable or miniaturized system design. The need to decrease overall system size is inherent in any handheld, portable, or lightweight system application.
Furthermore, the low profile can help in height limited designs, such as consumer hand-held remote controls, sub-notebook computers, and PCMCIA cards.
An additional advantage of the tiny package is that it allows better system performance due to ease of package place­ment. Because the tiny package is so small, it can fit on the board right where the op amp needs to be placed for optimal performance, unconstrained by the usual space limitations. This optimal placement of the tiny package allows for many system enhancements, not easily achieved with the con­straints of a larger package. For example, problems such as system noise due to undesired pickup of digital signals can be easily reduced or mitigated. This pick-up problem is often caused by long wires in the board layout going to or from an op amp. By placing the tiny package closer to the signal source and allowing the LM7341 output to drive the long wire, the signal becomes less sensitive to such pick-up. An overall reduction of system noise results.
Additional space savings parts are available in tiny packages from National Semiconductor, including low power amplifiers, precision voltage references, and voltage regulators.

LOW DISTORTION, HIGH OUTPUT DRIVE CAPABILITY

The LM7341 offers superior low-distortion performance, with a total-harmonic-distortion-plus-noise of −66 dB at f = 10 kHz. The advantage offered by the LM7341 is its low distortion levels, even at high output current and low load resistance.
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Typical Applications

HANDHELD REMOTE CONTROLS

The LM7341 offers outstanding specifications for applications requiring good speed/power trade-off. In applications such as remote control operation, where high bandwidth and low pow­er consumption are needed. The LM7341 performance can easily meet these requirements.

OPTICAL LINE ISOLATION FOR MODEMS

The combination of the low distortion and good load driving capabilities of the LM7341 make it an excellent choice for driving opto-coupler circuits to achieve line isolation for modems. This technique prevents telephone line noise from coupling onto the modem signal. Superior isolation is achieved by coupling the signal optically from the computer modem to the telephone lines; however, this also requires a low distortion at relatively high currents. Due to its low distor­tion at high output drive currents, the LM7341 fulfills this need, in this and in other telecom applications.

REMOTE MICROPHONE IN PERSONAL COMPUTERS

Remote microphones in Personal Computers often utilize a microphone at the top of the monitor which must drive a long cable in a high noise environment. One method often used to reduce the nose is to lower the signal impedance, which re­duces the noise pickup. In this configuration, the amplifier usually requires 30 dB–40 dB of gain, at bandwidths higher than most low-power CMOS parts can achieve. The LM7341 offers the tiny package, higher bandwidths, and greater out­put drive capability than other rail-to-rail input/output parts can provide for this application.

LM7341 AS A COMPARATOR

The LM7341 can also be used as a comparator and provides quite reasonable performance. Note however that unlike a typical comparator an op amp has a maximum allowed dif­ferential voltage between the input pins. For the LM7341, as stated in the Absolute Maximum Ratings section, this maxi­mum voltage is VIN Differential = ±15V. Beyond this limit, even for a short time, damage to the device may occur.
As an inverting comparator at VS = 30V and 1V of overdrive there is typically 12 μs of propagation delay. At VS = 30V and 50 mV of overdrive there is typically 17 µs of propagation de­lay.
LM7341
20206054

FIGURE 1. Inverting Comparator

Similarly a non-inverting comparator at VS = 30V and 1V of overdrive there is typically 12 µs of propagation delay. At VS = 30V and 50 mV of overdrive there is typically 17 μs of propagation delay.
20206055

FIGURE 2. Non-Inverting Comparator

COMPARATOR WITH HYSTERESIS

The basic comparator configuration may oscillate or produce a noisy output if the applied differential input voltage is near the comparator's offset voltage. This usually happens when the input signal is moving very slowly across the comparator's switching threshold. This problem can be prevented by the addition of hysteresis or positive feedback.
15 www.national.com

INVERTING COMPARATOR WITH HYSTERESIS

The inverting comparator with hysteresis requires a three re-
LM7341
sistor network that is referenced to the supply voltage VCC of the comparator, as shown in Figure 3. When VIN at the in­verting input is less than VA, the voltage at the non-inverting node of the comparator (VIN < VA), the output voltage is high (for simplicity assume V three network resistors can be represented as R1||R3 in series
switches as high as VCC). The
OUT
with R2. The lower input trip voltage VA1 is defined as
VA1 = VCCR2 / ((R1||R3) + R2)
When VIN is greater than VA (VIN > VA), the output voltage is low, very close to ground. In this case the three network re-
sistors can be presented as R2||R3 in series with R1. The upper trip voltage VA2 is defined as
VA2 = VCC (R2||R3) / ((R1+ (R2||R3)
The total hysteresis provided by the network is defined as
Delta VA = VA1- V
A2
For example to achieve 50 mV of hysteresis when VCC = 30V set R1 = 4.02 kΩ, R2 = 4.02 kΩ, and R3 = 1.21 MΩ. With these resistors selected the error due to input bias current is ap­proximately 1 mV. To minimize this error it is best to use low resistor values on the inputs.

FIGURE 3. Inverting Comparator with Hysteresis

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20206056

NON-INVERTING COMPARATOR WITH HYSTERESIS

A non-inverting comparator with hysteresis requires a two re­sistor network, and a voltage reference (V input. When VIN is low, the output is also low. For the output to switch from low to high, VIN must rise up to V V
is calculated by
IN1
V
= R1*(V
IN1
REF/R2
) + V
) at the inverting
REF
REF
IN1
where
When VIN is high, the output is also high, to make the com­parator switch back to it's low state, VIN must equal V before VA will again equal V
. VIN can be calculated by
REF
REF
V
= (V
IN2
The hysteresis of this circuit is the difference between V and V
IN2
.
(R1+ R2) - VCCR1)/R
REF
Delta VIN = VCCR1/R
2
IN1
2
For example to achieve 50 mV of hysteresis when VCC = 30V set R1 = 20Ω and R2 = 12.1 kΩ.
20206057
LM7341

FIGURE 4. Non-Inverting Comparator with Hysteresis

OTHER SOT-23 AMPLIFIERS

The LM7321 is a rail-to-rail input and output amplifier that can tolerate unlimited capacitive load. It works from 2.7V to ±15V and across the −40°C to 125°C temperature range. It has 20 MHz gain-bandwidth, and is available in both 5-Pin SOT-23 and 8-Pin SOIC packages.
The LM6211 is a 20 MHz part with CMOS input, which runs on 5V to 24V single supplies. It has rail-to-rail output and low noise.
The LMP7701 is a rail-to-rail input and output precision part with an input voltage offset under 220 microvolts and low noise. It has 2.5 MHz bandwidth and works on 2.7V to 12V supplies.
20206058

SMALLER SC70 AMPLIFIERS

The LMV641 is a 10 MHz amplifier which uses only 140 micro amps of supply current. The input voltage offset is less than
0.5 mV. The LMV851 is an 8 MHz amplifier which uses only 0.4 mA
supply current, and is available in the smaller SC70 package. The LMV851 also resists Electro Magnetic Interference (EMI) from mobile phones and similar high frequency sources. It works on 2.7V to 5.5 V supplies.
Detailed information on these and a wide range of other parts can be found at www.national.com.
17 www.national.com

Physical Dimensions inches (millimeters) unless otherwise noted

LM7341
5-Pin SOT-23
NS Package Number MF05A
www.national.com 18
Notes
LM7341
19 www.national.com
Notes
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