February 2003
LM6171
High Speed Low Power Low Distortion Voltage Feedback
Amplifier
LM6171 High Speed Low Power Low Distortion Voltage Feedback Amplifier
General Description
The LM6171 is a high speed unity-gain stable voltage feedback amplifier. It offers a high slew rate of 3600V/µs and a
unity-gain bandwidth of 100 MHz while consuming only 2.5
mA of supply current. The LM6171 has very impressive AC
and DC performance which is a great benefit for high speed
signal processing and video applications.
±
15V power supplies allow for large signal swings and
The
give greater dynamic range and signal-to-noise ratio. The
LM6171 has high output current drive, low SFDR and THD,
ideal for ADC/DAC systems. The LM6171 is specified for
±
5V operation for portable applications.
™
The LM6171 is built on National’s advanced VIP
cally Integrated PNP) complementary bipolar process.
III (Verti-
Typical Performance Characteristics
Closed Loop Frequency Responsevs. Supply Voltage
= +1)
(A
V
Features
(Typical Unless Otherwise Noted)
n Easy-To-Use Voltage Feedback Topology
n Very High Slew Rate: 3600V/µs
n Wide Unity-Gain-Bandwidth Product: 100 MHz
n −3dB Frequency
n Low Supply Current: 2.5 mA
n High CMRR: 110 dB
n High Open Loop Gain: 90 dB
n Specified for
@
AV= +2: 62 MHz
±
15V and±5V Operation
Applications
n Multimedia Broadcast Systems
n Line Drivers, Switchers
n Video Amplifiers
n NTSC, PAL
n ADC/DAC Buffers
n HDTV Amplifiers
n Pulse Amplifiers and Peak Detectors
n Instrumentation Amplifier
n Active Filters
®
and SECAM Systems
Large Signal Pulse Response
AV= +1, VS=±15
01233609
01233605
VIP™is a trademark of National Semiconductor Corporation.
®
PAL
is a registered trademark of and used under licence from Advanced Micro Devices, Inc.
© 2003 National Semiconductor Corporation DS012336 www.national.com
Connection Diagram
LM6171
8-Pin DIP/SO
Top View
01233601
Ordering Information
Package Temperature Range Transport Media NSC Drawing
Industrial
−40˚C to +85˚C
8-Pin LM6171AIN Rails N08E
Molded DIP LM6171BIN
8-Pin LM6171AIM, LM6171BIM Rails M08A
Small Outline LM6171AIMX, LM6171BIMX 2.5k Units Tape and Reel
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LM6171
Absolute Maximum Ratings (Note 1)
If Military/Aerospace specified devices are required,
please contact the National Semiconductor Sales Office/
Distributors for availability and specifications.
ESD Tolerance (Note 2) 2.5 kV
Supply Voltage (V
Differential Input Voltage
Common-Mode Voltage Range V
Input Current
Output Short Circuit to Ground
(Note 3) Continuous
Storage Temperature Range −65˚C to +150˚C
Maximum Junction Temperature
(Note 4) 150˚C
±
15V DC Electrical Characteristics
+–V−
) 36V
+
+0.3V to V−−0.3V
±
±
10mA
10V
Soldering Information
Infrared or Convection Reflow
(20 sec.) 235˚C
Wave Soldering Lead Temp
(10 sec.) 260˚C
Operating Ratings (Note 1)
Supply Voltage 5.5V ≤ V
Operating Temperature Range
LM6171AI, LM6171BI −40˚C to +85˚C
Thermal Resistance (θ
)
JA
N Package, 8-Pin Molded DIP 108˚C/W
M Package, 8-Pin Surface Mount 172˚C/W
S
≤ 34V
Unless otherwise specified, all limits guaranteed for TJ= 25˚C, V+= +15V, V−= −15V, VCM= 0V, and RL=1kΩ. Boldface
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
V
OS
Input Offset Voltage 1.5 3 6 mV
58max
TC V
I
B
Input Offset Voltage Average Drift 6 µV/˚C
OS
Input Bias Current 1 3 3 µA
44max
I
OS
Input Offset Current 0.03 2 2 µA
33max
R
IN
Input Resistance Common Mode 40 MΩ
Differential Mode 4.9
R
O
Open Loop 14 Ω
Output Resistance
CMRR Common Mode V
=±10V 110 80 75 dB
CM
Rejection Ratio 75 70 min
PSRR Power Supply V
=±15V to±5V 95 85 80 dB
S
Rejection Ratio 80 75 min
V
CM
Input Common-Mode CMRR ≥ 60 dB
±
13.5 V
Voltage Range
A
V
Large Signal Voltage RL=1kΩ 90 80 80 dB
Gain (Note 7) 70 70 min
R
= 100Ω 83 70 70 dB
L
60 60 min
V
O
Output Swing RL=1kΩ 13.3 12.5 12.5 V
12 12 min
−13.3 −12.5 −12.5 V
−12 −12 max
R
= 100Ω 11.6 9 9 V
L
8.5 8.5 min
−10.5 −9 −9 V
−8.5 −8.5 max
Continuous Output Current Sourcing, R
= 100Ω 116 90 90 mA
L
(Open Loop) (Note 8) 85 85 min
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±
15V DC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for TJ= 25˚C, V+= +15V, V−= −15V, VCM= 0V, and RL=1kΩ. Boldface
LM6171
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
Sinking, R
= 100Ω 105 90 90 mA
L
85 85 max
Continuous Output Current Sourcing, R
(in Linear Region) Sinking, R
I
SC
Output Short Sourcing 135 mA
=10Ω 100 mA
L
=10Ω 80 mA
L
Circuit Current Sinking 135 mA
I
S
Supply Current 2.5 4 4 mA
4.5 4.5 max
±
15V AC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for TJ= 25˚C, V+= +15V, V−= −15V, VCM= 0V, and RL=1kΩ. Boldface
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
SR Slew Rate (Note 9) A
= +2, VIN=13V
V
A
= +2, VIN=10V
V
PP
PP
3600 V/µs
3000
GBW Unity Gain-Bandwidth Product 100 MHz
−3 dB Frequency A
= +1 160 MHz
V
A
= +2 62 MHz
V
φm Phase Margin 40 deg
t
s
A
D
φ
D
e
n
Settling Time (0.1%) AV= −1, V
R
= 500Ω
L
Propagation Delay V
=±5V, RL= 500Ω,6 ns
IN
A
=−2
V
=±5V 48 ns
OUT
Differential Gain (Note 10) 0.03 %
Differential Phase (Note 10) 0.5 deg
Input-Referred f = 1 kHz
12
Voltage Noise
i
n
Input-Referred f = 1 kHz
1
Current Noise
±
5V DC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for TJ= 25˚C, V+= +5V, V−= −5V, VCM= 0V, and RL=1kΩ. Boldface lim-
its apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
V
OS
Input Offset Voltage 1.2 3 6 mV
58max
TC V
Input Offset Voltage 4 µV/˚C
OS
Average Drift
I
B
Input Bias Current 1 2.5 2.5 µA
3.5 3.5 max
I
OS
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Input Offset Current 0.03 1.5 1.5 µA
±
5V DC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for TJ= 25˚C, V+= +5V, V−= −5V, VCM= 0V, and RL=1kΩ. Boldface lim-
its apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
2.2 2.2 max
R
IN
Input Resistance Common Mode 40 MΩ
Differential Mode 4.9
R
O
Open Loop 14 Ω
Output Resistance
CMRR Common Mode V
=±2.5V 105 80 75 dB
CM
Rejection Ratio 75 70 min
PSRR Power Supply V
=±15V to±5V 95 85 80 dB
S
Rejection Ratio 80 75 min
V
CM
Input Common-Mode CMRR ≥ 60 dB
±
3.7 V
Voltage Range
A
V
Large Signal Voltage RL=1kΩ 84 75 75 dB
Gain (Note 7) 65 65 min
R
= 100Ω 80 70 70 dB
L
60 60 min
V
O
Output Swing RL=1kΩ 3.5 3.2 3.2 V
33min
−3.4 −3.2 −3.2 V
−3 −3 max
R
= 100Ω 3.2 2.8 2.8 V
L
2.5 2.5 min
−3.0 −2.8 −2.8 V
−2.5 −2.5 max
Continuous Output Current Sourcing, R
= 100Ω 32 28 28 mA
L
(Open Loop) (Note 8) 25 25 min
Sinking, R
= 100Ω 30 28 28 mA
L
25 25 max
I
SC
Output Short Sourcing 130 mA
Circuit Current Sinking 100 mA
I
S
Supply Current 2.3 3 3 mA
3.5 3.5 max
LM6171
±
5V AC Electrical Characteristics
Unless otherwise specified, all limits guaranteed for TJ= 25˚C, V+= +5V, V−= −5V, VCM= 0V, and RL=1kΩ. Boldface
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
SR Slew Rate (Note 9) A
= +2, VIN= 3.5 V
V
PP
750 V/µs
GBW Unity Gain-Bandwidth 70 MHz
Product
−3 dB Frequency A
= +1 130 MHz
V
A
=+2 45
V
φm Phase Margin 57 deg
t
s
Settling Time (0.1%) AV= −1, V
R
= 500Ω
L
= +1V, 60 ns
OUT
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±
5V AC Electrical Characteristics (Continued)
Unless otherwise specified, all limits guaranteed for TJ= 25˚C, V+= +5V, V−= −5V, VCM= 0V, and RL=1kΩ. Boldface
LM6171
limits apply at the temperature extremes
Typ LM6171AI LM6171BI
Symbol Parameter Conditions (Note 5) Limit Limit Units
(Note 6) (Note 6)
Propagation Delay V
A
D
φ
D
e
n
Differential Gain (Note 10) 0.04 %
Differential Phase (Note 10) 0.7 deg
Input-Referred f = 1 kHz
=±1V, RL= 500Ω,8 ns
IN
A
=−2
V
11
Voltage Noise
i
n
Input-Referred f = 1 kHz
1
Current Noise
Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is
intended to be functional, but specific performance is not guaranteed. For guaranteed specifications and the test conditions, see the Electrical Characteristics.
Note 2: Human body model, 1.5 kΩ in series with 100 pF.
Note 3: Continuous short circuit operation at elevated ambient temperature can result in exceeding the maximum allowed junction temperature of 150˚C.
Note 4: The maximum power dissipation is a function of T
(T
J(max)−TA
Note 5: Typical Values represent the most likely parametric norm.
Note 6: All limits are guaranteed by testing or statistical analysis.
Note 7: Large signal voltage gain is the total output swing divided by the input signal required to produce that swing. For V
V
OUT
Note 8: The open loop output current is the output swing with the 100Ω load resistor divided by that resistor.
Note 9: Slew rate is the average of the rising and falling slew rates.
Note 10: Differential gain and phase are measured with A
)/θJA. All numbers apply for packages soldered directly into a PC board.
=±1V.
, θJA, and TA. The maximum allowable power dissipation at any ambient temperature is PD=
J(max)
=±15V, V
S
= +2, VIN=1VPPat 3.58 MHz and both input and output 75Ω terminated.
V
=±5V. For VS= +5V,
OUT
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LM6171
Typical Performance Characteristics Unless otherwise noted, T
Supply Current vs. Supply Voltage Supply Current vs. Temperature
01233620
Input Offset Voltage vs. Temperature Input Bias Current vs. Temperature
= 25˚C
A
01233621
01233622
01233623
Input Offset Voltage vs. Common Mode Voltage Short Circuit Current vs. Temperature (Sourcing)
01233624
01233625
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Typical Performance Characteristics Unless otherwise noted, T
LM6171
Short Circuit Current vs. Temperature (Sinking) Output Voltage vs. Output Current
= 25˚C (Continued)
A
01233626
Output Voltage vs. Output Current CMRR vs. Frequency
01233628
PSRR vs. Frequency PSRR vs. Frequency
01233627
01233629
01233630
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01233631
LM6171
Typical Performance Characteristics Unless otherwise noted, T
= 25˚C (Continued)
A
Open Loop Frequency Response Open Loop Frequency Response
01233632
Gain Bandwidth Product vs. Supply Voltage Gain Bandwidth Product vs. Load Capacitance
01233633
01233634
01233635
Large Signal Voltage Gain vs. Load Large Signal Voltage Gain vs. Load
01233636 01233637
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Typical Performance Characteristics Unless otherwise noted, T
LM6171
Input Voltage Noise vs. Frequency Input Voltage Noise vs. Frequency
01233638 01233639
Input Current Noise vs. Frequency Input Current Noise vs. Frequency
= 25˚C (Continued)
A
01233640 01233641
Slew Rate vs. Supply Voltage Slew Rate vs. Input Voltage
01233642
01233643
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LM6171
Typical Performance Characteristics Unless otherwise noted, T
Slew Rate vs. Load Capacitance Open Loop Output Impedance vs. Frequency
01233644
Large Signal Pulse Response
Open Loop Output Impedance vs. Frequency
AV= −1, VS=±15V
= 25˚C (Continued)
A
01233645
Large Signal Pulse Response
= −1, VS=±5V
A
V
01233647
01233646
Large Signal Pulse Response
AV= +1, VS=±15V
01233648 01233649
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Typical Performance Characteristics Unless otherwise noted, T
LM6171
Large Signal Pulse Response
A
= +1, VS=±5V
V
Large Signal Pulse Response
= +2, VS=±5V
A
V
01233650 01233651
= 25˚C (Continued)
A
Large Signal Pulse Response
AV= +2, VS=±15V
Small Signal Pulse Response
AV= −1, VS=±15V
Small Signal Pulse Response
= −1, VS=±5V
A
V
01233652 01233653
Small Signal Pulse Response
AV= +1, VS=±15V
01233654 01233655
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LM6171
Typical Performance Characteristics Unless otherwise noted, T
Small Signal Pulse Response
A
= +1, VS=±5V
V
Small Signal Pulse Response
= +2, VS=±5V
A
V
01233656 01233657
Closed Loop Frequency Response vs. SupplyVoltage
Small Signal Pulse Response
AV= +2, VS=±15V
= 25˚C (Continued)
A
(AV= +1)
01233658
Closed Loop Frequency Response vs. Supply Voltage
= +2)
(A
V
01233660 01233661
01233659
Closed Loop Frequency Response vs. Capacitive Load
(AV= +1)
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Typical Performance Characteristics Unless otherwise noted, T
LM6171
Closed Loop Frequency Response vs. Capacitive Load
(A
= +1)
V
Closed Loop Frequency Response vs. Capacitive Load
= 25˚C (Continued)
A
(AV= +2)
01233662
Closed Loop Frequency Response vs. Capacitive Load
= +2) Total Harmonic Distortion vs. Frequency
(A
V
01233664
Total Harmonic Distortion vs. Frequency Total Harmonic Distortion vs. Frequency
01233663
01233665
01233666 01233667
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LM6171
Typical Performance Characteristics Unless otherwise noted, T
Total Harmonic Distortion vs. Frequency Undistorted Output Swing vs. Frequency
01233668
Undistorted Output Swing vs. Frequency Undistorted Output Swing vs. Frequency
= 25˚C (Continued)
A
01233669
01233670 01233671
Undistorted Output Swing vs. Frequency Total Power Dissipation vs. Ambient Temperature
01233672
01233673
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LM6171 Simplified Schematic
LM6171
01233610
Application Information
LM6171 PERFORMANCE DISCUSSION
The LM6171 is a high speed, unity-gain stable voltage feedback amplifier. It consumes only 2.5 mA supply current while
providing a gain-bandwidth product of 100 MHz and a slew
rate of 3600V/µs. It also has other great features such as low
differential gain and phase and high output current. The
LM6171 is a good choice in high speed circuits.
The LM6171 is a true voltage feedback amplifier. Unlike
current feedback amplifiers (CFAs) with a low inverting input
impedance and a high non-inverting input impedance, both
inputs of voltage feedback amplifiers (VFAs) have high impedance nodes. The low impedance inverting input in CFAs
will couple with feedback capacitor and cause oscillation. As
a result, CFAs cannot be used in traditional op amp circuits
such as photodiode amplifiers, I-to-V converters and integrators.
LM6171 CIRCUIT OPERATION
The class AB input stage in LM6171 is fully symmetrical and
has a similar slewing characteristic to the current feedback
amplifiers. In the LM6171 Simplfied Schematic, Q1 through
Q4 form the equivalent of the current feedback input buffer,
the equivalent of the feedback resistor, and stage A
R
E
buffers the inverting input. The triple-buffered output stage
isolates the gain stage from the load to provide low output
impedance.
LM6171 SLEW RATE CHARACTERISTIC
The slew rate of LM6171 is determined by the current available to charge and discharge an internal high impedance
node capacitor. The current is the differential input voltage
divided by the total degeneration resistor R
slew rate is proportional to the input voltage level, and the
higher slew rates are achievable in the lower gain configurations.
. Therefore, the
E
When a very fast large signal pulse is applied to the input of
an amplifier, some overshoot or undershoot occurs. By placing an external series resistor such as 1 kΩ to the input of
LM6171, the bandwidth is reduced to help lower the overshoot.
LAYOUT CONSIDERATION
Printed Circuit Boards and High Speed Op Amps
There are many things to consider when designing PC
boards for high speed op amps. Without proper caution, it is
very easy and frustrating to have excessive ringing, oscillation and other degraded AC performance in high speed
circuits. As a rule, the signal traces should be short and wide
to provide low inductance and low impedance paths. Any
unused board space needs to be grounded to reduce stray
signal pickup. Critical components should also be grounded
at a common point to eliminate voltage drop. Sockets add
capacitance to the board and can affect frequency performance. It is better to solder the amplifier directly into the PC
board without using any socket.
Using Probes
Active (FET) probes are ideal for taking high frequency
measurements because they have wide bandwidth, high
input impedance and low input capacitance. However, the
probe ground leads provide a long ground loop that will
produce errors in measurement. Instead, the probes can be
grounded directly by removing the ground leads and probe
jackets and using scope probe jacks.
Components Selection And Feedback Resistor
It is important in high speed applications to keep all component leads short because wires are inductive at high frequency. For discrete components, choose carbon
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LM6171
Application Information (Continued)
composition-type resistors and mica-type capacitors. Surface mount components are preferred over discrete components for minimum inductive effect.
Large values of feedback resistors can couple with parasitic
capacitance and cause undesirable effects such as ringing
or oscillation in high speed amplifiers. For LM6171, a feedback resistor of 510Ω gives optimal performance.
COMPENSATION FOR INPUT CAPACITANCE
The combination of an amplifier’s input capacitance with the
gain setting resistors adds a pole that can cause peaking or
oscillation. To solve this problem, a feedback capacitor with
a value
>
(RGxCIN)/R
C
F
can be used to cancel that pole. For LM6171, a feedback
capacitor of 2 pF is recommended. Figure 1 illustrates the
compensation circuit.
F
TERMINATION
In high frequency applications, reflections occur if signals
are not properly terminated. Figure 3 shows a properly terminated signal while Figure 4 shows an improperly terminated signal.
01233614
FIGURE 3. Properly Terminated Signal
01233611
FIGURE 1. Compensating for Input Capacitance
POWER SUPPLY BYPASSING
Bypassing the power supply is necessary to maintain low
power supply impedance across frequency. Both positive
and negative power supplies should be bypassed individually by placing 0.01 µF ceramic capacitors directly to power
supply pins and 2.2 µF tantalum capacitors close to the
power supply pins.
01233612
01233615
FIGURE 4. Improperly Terminated Signal
FIGURE 2. Power Supply Bypassing
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Application Information (Continued)
To minimize reflection, coaxial cable with matching charac-
LM6171
teristic impedance to the signal source should be used. The
other end of the cable should be terminated with the same
value terminator or resistor. For the commonly used cables,
RG59 has 75Ω characteristic impedance, and RG58 has
50Ω characteristic impedance.
DRIVING CAPACITIVE LOADS
Amplifiers driving capacitive loads can oscillate or have ringing at the output. To eliminate oscillation or reduce ringing,
an isolation resistor can be placed as shown below in Figure
5. The combination of the isolation resistor and the load
capacitor forms a pole to increase stablility by adding more
phase margin to the overall system. The desired performance depends on the value of the isolation resistor; the
bigger the isolation resistor, the more damped the pulse
response becomes. For LM6171, a 50Ω isolation resistor is
recommended for initial evaluation. Figure 6 shows the
LM6171 driving a 200 pF load with the 50Ω isolation resistor.
FIGURE 5. Isolation Resistor Used
to Drive Capacitive Load
01233613
For example, for the LM6171 in a SO-8 package, the maximum power dissipation at 25˚C ambient temperature is
730 mW.
Thermal resistance, θ
, depends on parameters such as
JA
die size, package size and package material. The smaller
the die size and package, the higher θ
becomes. The 8-pin
JA
DIP package has a lower thermal resistance (108˚C/W) than
that of 8-pin SO (172˚C/W). Therefore, for higher dissipation
capability, use an 8-pin DIP package.
The total power dissipated in a device can be calculated as:
P
D=PQ+PL
PQis the quiescent power dissipated in a device with no load
connected at the output. P
is the power dissipated in the
L
device with a load connected at the output; it is not the power
dissipated by the load.
Furthermore,
= supply current x total supply voltage with no load
P
Q
= output current x (voltage difference between
P
L
supply voltage and output voltage of the same
supply)
For example, the total power dissipated by the LM6171 with
=±15V and output voltage of 10V into 1 kΩ load resistor
V
S
(one end tied to ground) is
P
=PQ+P
D
L
= (2.5 mA) x (30V) + (10 mA) x (15V − 10V)
=75mW+50mW
= 125 mW
APPLICATION CIRCUITS
Fast Instrumentation Amplifier
01233616
FIGURE 6. The LM6171 Driving a 200 pF Load
with a 50Ω Isolation Resistor
POWER DISSIPATION
The maximum power allowed to dissipate in a device is
defined as:
P
D
=(T
J(max)−TA
)/θ
JA
Where PDis the power dissipation in a device
T
is the maximum junction temperature
J(max)
is the ambient temperature
T
A
is the thermal resistance of a particular package
θ
JA
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01233617
LM6171
Application Information (Continued)
Multivibrator
01233618
DESIGN KIT
A design kit is available for the LM6171. The design kit
contains:
High Speed Evaluation Board
•
LM6171 in 8-pin DIP Package
•
LM6171 Datasheet
•
Pspice Macromodel Diskette With the LM6171 Macro-
•
model
An Amplifier Selection Guide
•
Pulse Width Modulator
01233619
LM6171 in 8-pin DIP Package
•
LM6171 Datasheet
•
Pspice Macromodel Diskette With the LM6171 Macro-
•
model
Contact your local National Semiconductor sales office to
obtain a pitch pack.
PITCH PACK
A pitch pack is available for the LM6171. The pitch pack
contains:
High Speed Evaluation Board
•
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Physical Dimensions inches (millimeters) unless otherwise noted
LM6171
8-Pin Small Outline Package
NS Package Number M08A
8-Pin Molded DIP Package
NS Package Number N08E
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Notes
LM6171 High Speed Low Power Low Distortion Voltage Feedback Amplifier
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DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT AND GENERAL
COUNSEL OF NATIONAL SEMICONDUCTOR CORPORATION. As used herein:
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systems which, (a) are intended for surgical implant
into the body, or (b) support or sustain life, and
whose failure to perform when properly used in
accordance with instructions for use provided in the
2. A critical component is any component of a life
support device or system whose failure to perform
can be reasonably expected to cause the failure of
the life support device or system, or to affect its
safety or effectiveness.
labeling, can be reasonably expected to result in a
significant injury to the user.
National Semiconductor
Americas Customer
Support Center
Email: new.feedback@nsc.com
Tel: 1-800-272-9959
www.national.com
National does not assume any responsibility for use of any circuitry described, no circuit patent licenses are implied and National reserves the right at any time without notice to change said circuitry and specifications.
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