Datasheet LM26480 Datasheet (National Semiconductor)

January 15, 2008

LM26480 Externally Programmable Dual High-Current Step-Down DC/DC and Dual Linear Regulators

General Description

The LM26480 is a multi-functional Power Management Unit, optimized for low-power digital applications. This device integrates two highly efficient 1.5A step-down DC/DC converters and two 300 mA linear regulators. The LM26480 is offered in a tiny 4 x 4 x 0.8mm LLP-24 pin package.

Key Specifications

Step-Down DC/DC Converter (Buck)

1.5A output current

■

from:

OUT

Buck1 : 0.8V–2.0V @ 1.5A

—

Buck2 : 1.0V–3.3V @ 1.5A

—

Up to 96% efficiency ±3% FB voltage accuracy 2 MHz PWM switching frequency PWM - PFM automatic mode change under low loads Automatic soft start

Linear Regulators (LDO)

■

of 1.0V–3.5V

OUT

±3% FB voltage accuracy

300 mA output current 25 mV (typ) dropout

Features

Compatible with advanced applications processors and

■

FPGAs 2 LDOs for powering Internal processor functions and I/Os

■

Precision internal reference

■

Thermal overload protection

■

Current overload protection

■

24-lead 4 × 4 × 0.8mm LLP package

■

External Power-On-Reset function for Buck1 and Buck2

■

Undervoltage lock-out detector to monitor input supply

■

voltage

Applications

Core digital power

■

Applications processors

■

Peripheral I/O power

■

LM26480Externally Programmable Dual High-Current Step-Down DC/DC and Dual Linear

Regulators

Typical Application Circuit

30040401

LM26480

FIGURE 1. Application Circuit

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30040402

Connection Diagrams and Package Mark Information

30040403

FIGURE 2. 24-Lead LLP Package (top view)

LM26480

Note:

The physical placement of the package marking will vary from part to part.

(*) UZXYTT format: ‘U’ – wafer fab code; ‘Z’ – assembly code; ’XY’ 2 digit date code; ‘TT” – die run code. See http://www.national.com/quality/ marking_conventions.html for more information on marking information.

Part Number Spec Quantity

LM26480SQ-AA NOPB 1000 tape and reel

LM26480SQX-AA NOPB 4500 tape and reel

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Pin Descriptions

LM26480

LLP Pin No. Name I/O Type Description

1 VINLDO12 I PWR Analog Power for Internal Functions (VREF, BIAS, I2C, Logic)

2 SYNC I G/(D) Frequency Synchronization pin which allows the user to connect an

external clock signal to synchronize the PMIC internal oscillator. Default OFF and must be grounded when not used. Contact National Sales office to enable.

3 NPOR O D nPOR Power on reset pin for both Buck1 and Buck 2. Open drain logic

output 100K pullup resistor. nPOR is pulled to ground when the voltages on these supplies are not good. See nPOR section for more info.

4 GND_SW1 G G Buck1 NMOS Power Ground

5 SW1 O PWR Buck1 switcher output pin

6 VIN1 I PWR Power in from either DC source or Battery to Buck1

7 ENSW1 I D Enable Pin for Buck1 switcher, a logic HIGH enables Buck1. Pin cannot

be left floating.

8 FB1 I A Buck1 input feedback terminal

9 GND_C G G Non-switching core ground pin

10 AVDD I PWR Analog Power for Buck converters

11 FB2 I A Buck2 input feedback terminal

12 ENSW2 I D Enable Pin for Buck2 switcher, a logic HIGH enables Buck2. Pin cannot

be left floating.

13 VIN2 I PWR Power in from either DC source or Battery to Buck2

14 SW2 O PWR Buck2 switcher output pin

15 GND_SW2 G G Buck2 NMOS

16 ENLDO2 I D LDO2 enable pin, a logic HIGH enables LDO2. Pin cannot be left

floating.

17 ENLDO1 I D LDO1 enable pin, a logic HIGH enables LDO1. Pin cannot be left

floating.

18 GND_L G G LDO ground

19 VINLDO1 I PWR Power in from either DC source or battery to LDO1

20 LDO1 O PWR LDO1 Output

21 FBL1 I A LDO1 Feedback Terminal

22 FBL2 I A LDO2 Feedback Terminal

23 LDO2 O PWR LDO Output

24 VINLDO2 I PWR Power in from either DC source or battery to LDO2.

A: Analog Pin D: Digital Pin G: Ground Pin PWR: Power Pin I: Input Pin I/O: Input/Output Pin O: Output Pin

Power Block Operation Note

Power Block Input Enabled Disabled

VINLDO12 VIN+ VIN+ Always Powered

AVDD VIN+ VIN+ Always Powered

VIN1 VIN+ VIN+ or 0V

VIN2 VIN+ VIN+ or 0V VINLDO1 ≤ VIN+ ≤ VIN+ If Enabled, Min VIN is 1.74V VINLDO2 ≤ VIN+ ≤ VIN+ If Enabled, Min VIN is 1.74V

VIN+ is the largest potential voltage on the device.

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LM26480

Absolute Maximum Ratings (Notes 1, 2)

If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications.

VINLDO12, VIN1, AVDD, VIN2, VINLDO1, VINLDO2, ENSW1, FB1, FB2, ENSW2, ENLDO1,

Operating Ratings: Bucks (Notes 1, 2, 7)

Junction Temperature (TJ) Range –40°C to +125°C

Ambient Temperature (TA) Range (Note 6)

2.8V to 5.5V

0 to (VIN + 0.3V)

−40°C to +85°C

ENLDO2, SYNC, FBL1, FBL2 −0.3V to +6V GND to GND SLUG ±0.3V Power Dissipation (P

(TA=85°C, T

=125°C ) (Note 5)

MAX

Junction Temperature (T

D_MAX

)

J-MAX

1.17W

)

150°C

Thermal Properties (Notes 3, 5, 6)

Junction-to-Ambient Thermal Resistance (θJA) SQA024AG

34.1°C/W

Storage Temperature Range −65°C to +150°C Maximum Lead Temperature (Soldering) 260°C

ESD Ratings

Human Body Model (Note 4) 2 kV

General Electrical Characteristics (Notes 1, 2, 7, 13, 16)

Unless otherwise noted, VIN = 3.6V. Typical values and limits appearing in normal type apply for TJ = 25°C. Limits appearing in

boldface type apply over the entire junction temperature range for operation, −40°C to +125°C.

Symbol Parameter Conditions Min Typ Max Units

POR

SDH

UVLO Under Voltage Lock Out Rising 2.9 V

VINLDO12 Shutdown Current VIN = 3.6V

Power-On Reset Threshold VDD Falling Edge(Note 16)

Thermal Shutdown Threshold (Note 13)

Themal Shutdown Hysteresis (Note 13)

Failing 2.7 V

0.5 µA

1.9 V

160 °C

20 °C

Low Drop Out Regulators, LDO1 and LDO2

Unless otherwise noted, VIN = 3.6V, CIN = 1.0 µF, C TJ = 25°C. Limits appearing in boldface type apply over the entire junction temperature range for operation, −40°C to +125°C. (Notes 2, 7, 8, 9)

Symbol Parameter Conditions Min Typ Max Units

ΔV

OUT

Operational Voltage Range VINLDO1 and VINLDO2 PMOS

FB Voltage Accuracy

Line Regulation VIN = (V

Load Regulation VIN = 3.6V,

VIN – V

OUT

Short Circuit Current Limit LDO1-2, V

Dropout Voltage Load Current = 50 mA

PSRR Power Supply Ripple Rejection F = 10 kHz, Load Current = I

θn

Supply Output Noise 10 Hz < F < 100 kHz

Quiescent Current “On” I

Quiescent Current “Off” EN is de-asserted 0.03 1 µA

Turn On Time Start up from shut-down

= 0.47 µF. Typical values and limits appearing in normal type apply for

OUT

pins (Note 15)

1.74 5.5 V

−3 3 %

+ 0.3V) to 5.0V

OUT

(Note 12) Load Current = 1 mA

Load Current = 1 mA to I

= 0V

OUT

MAX

(Note 10)

MAX

0.15 %/V

0.011 %/mA

500 mA

25 200 mV

45 dB

150 µVrms

OUT

= 0 mA

= 200

40 150 µA

60 200 µA

300 µsec

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Symbol Parameter Conditions Min Typ Max Units

OUT

LM26480

Output Capacitor Capacitance for stability

0°C ≤ TJ ≤ 125°C

−40°C ≤ TJ ≤ 125°C

ESR (Equivalent Series Resistance)

0.33 0.47 µF

0.68 1.0 µF

5 500

Buck Converters SW1, SW2

Unless otherwise noted, VIN = 3.6V, CIN = 10 µF, C apply for TJ = 25°C. Limits appearing in boldface type apply over the entire junction temperature range for operation, −40°C to +125°C. ((Notes 2, 7, 8, 9, 11, 14)

Symbol Parameter Conditions Min Typ Max Units

VFB (Note 14) Feedback Voltage −3 +3 %

OUT

Line Regulation 2.8 < VIN < 5.5

Load Regulation 100 mA < IO < I

Eff Efficiency Load Current = 250 mA 96 %

SHDN

OSC

PEAK

Shutdown Supply Current EN is de-asserted 0.01 1 µA

Internal Oscillator Frequency 2.0 2.4 MHz

Buck1 Peak Switching Current Limit 2.0 2.4

Buck2 Peak Switching Current Limit 2.0 2.4

(P) Pin-Pin Resistance PFET 200 400

DSON

(N) Pin-Pin Resistance NFET 180 400

DSON

Quiescent Current “On” No load PFM Mode 33 µA

Turn On Time Start up from shut-down 500 µsec

Input Capacitor Capacitance for stability 10 µF

Output Capacitor Capacitance for stability 10 µF

= 10 µF, L

OUT

IO =10 mA

= 2.2 µH. Typical values and limits appearing in normal type

OUT

0.089 %/V

MAX

0.0013 %/mA

mΩ

I/O Electrical Characteristics

Unless otherwise noted: Typical values and limits appearing in normal type apply for TJ = 25°C. Limits appearing in boldface type apply over the entire junction temperature range for operation, TJ = 0°C to +125°C.

Symbol Parameter Conditions

Input Low Level

Input High Level

0.7*VDD V

Limit

Min Max

0.4 V

Units

Power On Reset Threshold/Function (POR)

Symbol Parameter Conditions Min Typ Max Units

nPOR nPOR = Power on reset for Buck1 and

Buck2

nPOR Threshold

Percentage of Target voltage Buck1 or Buck2

Output Level Low Load = IOL = 500 µA 0.23 0.5 V

Default 60 msec

BUCK1

AND V

OR V

BUCK2

rising

falling

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Note 1: Absolute Maximum Ratings indicate limits beyond which damage to the component may occur. Operating Ratings are conditions under which operation of the device is guaranteed. Operating Ratings do not imply guaranteed performance limits. For guaranteed performance limits and associated test conditions, see the Electrical Characteristics.

Note 2: All voltages are with respect to the potential at the GND pin.

Note 3: Internal thermal shutdown circuitry protects the device from permanent damage. Thermal shutdown engages at TJ = 160°C (typ.) and disengages at T

= 140°C (typ.)

Note 4: The Human body model is a 100 pF capacitor discharged through a 1.5 kΩ resistor into each pin. (MILSTD - 883 3015.7)

Note 5: In applications where high power dissipation and/or poor package thermal resistance is present, the maximum ambient temperature may have to be

derated. Maximum ambient temperature (T dissipation of the device in the application (P following equation: T

A-MAX

= T

J-MAX-OP

− (θJA × P

) is dependent on the maximum operating junction temperature (T

A-MAX

), and the junction-to-ambient thermal resistance of the part/package in the application (θJA), as given by the

D-MAX

). See Applications section.

D-MAX

= 125°C), the maximum power

J-MAX-OP

Note 6: Junction-to-ambient thermal resistance is highly application and board-layout dependent. In applications where high maximum power dissipation exists, special care must be paid to thermal dissipation issues in board design.

Note 7: Min and Max limits are guaranteed by design, test, or statistical analysis. Typical numbers are not guaranteed, but do represent the most likely norm.

Note 8: CIN, C

: Low-ESR Surface-Mount Ceramic Capacitors (MLCCs) used in setting electrical characteristics.

OUT

Note 9: The device maintains a stable, regulated output voltage without a load.

Note 10: Dropout voltage is the voltage difference between the input and the output at which the output voltage drops to 100 mV below its nominal value.

Note 11: Quiescent current is defined here as the difference in current between the input voltage source and the load at V

OUT

Note 12: VIN minimum for line regulation values is 1.8V.

Note 13: This specification is guaranteed by design.

Note 14: VIN ≥ V

OUT

+ R

DSON

(P) (I

OUT

+ 1/2 I

). If these conditions are not met, voltage regulation will degrade as load increases.

RIPPLE

Note 15: Pins 24, 19 can operate from VIN min of 1.74V to a VIN max of 5.5V. This rating is only for the series pass PMOS power FET. It allows the system design to use a lower voltage rating if the input voltage comes from a buck output.

Note 16: VPOR is voltage at which the EPROM resets. This is different from the UVLO on VINLDO12, which is the voltage at which the regulators shut off; and is also different from the nPOR function, which signals if the regulators are in a specified range.

LM26480

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Typical Performance Characteristics — LDO

LM26480

Output Voltage Change vs Temperature (LDO1)

VIN = 3.6V, V

= 2.5V, 100 mA load

OUT

30040466

Load Transient

3.6 VIN, 2.5V

, 0 – 150 mA load

OUT

Output Voltage Change vs Temperature (LDO2)

VIN = 3.6V, V

= 1.8V, 100 mA load

OUT

30040455

Load Transient

3.6 VIN, 2.5V

, 150–300 mA load

OUT

30040437

Line Transient (LDO1)

3.6 - 4.2 VIN, 2.5 V

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, 100 mA load

OUT

30040439

Line Transient (LDO2)

3.6 – 4.2 VIN, 1.8V

, 150 mA load

OUT

30040438

30040440

LM26480

Enable Start-up time (LDO1)

0-3.6 VIN, 2.5 V

, 1 mA load

OUT

30040441

Enable Start-up time (LDO2)

0 – 3.6 VIN, 1.8V

, 1 mA load

OUT

30040442

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Typical Performance Characteristics — Buck V

= 2.8V to 5.5V, TA = 25°C

LM26480

Shutdown Current vs. Temp

Output Voltage vs. Supply Voltage

= 2.0V)

OUT

30040443

Output Voltage vs. Supply Voltage

= 1.2V)

OUT

Output Voltage vs. Supply Voltage

= 3.0V)

OUT

30040444

30040445

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30040446

Typical Performance Characteristics — Buck Output Current transitions from PFM mode to PWM

mode for Buck 1

LM26480

Efficiency vs. Output Current

= 1.2V, L = 2.2 µH)

OUT

30040447

Output Current transitions from PWM mode to PFM mode

for Buck 2

Efficiency vs. Output Current

= 3.0V, L = 2.2 µH)

OUT

Efficiency vs. Output Current

= 2.0V, L = 2.2 µH)

OUT

Efficiency vs. Output Current

= 3.5V, L = 2.2 µH)

OUT

30040448

30040449

30040450

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Typical Performance Characteristics — Buck

LM26480

VIN= 3.6V, TA = 25°C, V

= 1.2V unless otherwise noted

OUT

Load Transient Response

= 1.2V (PWM Mode)

OUT

Line Transient Response

VIN = 3.6 – 4.2V, V

= 1.2V, 250 mA load

OUT

30040456

Mode Change by Load Transients

= 1.2V (PWM to PFM)

OUT

Line Transient Response

VIN = 3.0 – 3.6V, V

= 3.0V, 250 mA load

OUT

30040457

30040458

Start up into PWM Mode

= 1.2V, 1.5A load

OUT

30040460

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Start up into PWM Mode

= 3.0 V, 1.5A load

OUT

30040459

30040461

LM26480

Start up into PFM Mode

= 1.2V, 30 mA load

OUT

30040462

Start up into PFM Mode

= 3.0V, 30 mA load

OUT

30040470

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DC/DC Converters

OVERVIEW

LM26480

The LM26480 provides the DC/DC converters that supply the various power needs of the application by means of two linear low dropout regulators, LDO1 and LDO2, and two buck converters, SW1 and SW2. The table here under lists the output characteristics of the various regulators.

Supply Specification

Output

Supply Load

LDO1 analog 1.0 to 3.5 300

LDO2 analog 1.0 to 3.5 300

SW1 digital 0.8 to 2.0 1500

SW2 digital 1.0 to 3.3 1500

LINEAR LOW DROPOUT REGULATORS (LDOs)

LDO1 and LDO2 are identical linear regulators targeting analog loads characterized by low noise requirements. LDO1 and LDO2 are enabled through the ENLDO pin.

OUT

Range (V)

Maximum Output

Current (mA)

MAX

turns off the device, offering the lowest current consumption. PWM or PFM mode is selected automatically or PWM mode can be forced through the setting of the buck control register.

Both SW1 and SW2 can operate up to a 100% duty cycle (PMOS switch always on) for low drop out control of the output voltage. In this way the output voltage will be controlled down to the lowest possible input voltage.

Additional features include soft-start, under-voltage lock-out, current overload protection, and thermal overload protection.

CIRCUIT OPERATION DESCRIPTION

A buck converter contains a control block, a switching PFET connected between input and output, a synchronous rectifying NFET connected between the output and ground (BCKGND pin) and a feedback path. During the first portion of each switching cycle, the control block turns on the internal PFET switch. This allows current to flow from the input through the inductor to the output filter capacitor and load. The inductor limits the current to a ramp with a slope of

by storing energy in a magnetic field. During the second portion of each cycle, the control block turns the PFET switch off, blocking current flow from the input, and then turns the NFET synchronous rectifier on. The inductor draws current from ground through the NFET to the output filter capacitor and load, which ramps the inductor current down with a slope of

30040404

NO-LOAD STABILITY

The LDOs will remain stable and in regulation with no external load. This is an important consideration in some circuits, for example, CMOS RAM keep-alive applications.

SW1, SW2: Synchronous StepDown Magnetic DC/DC Converters

FUNCTIONAL DESCRIPTION

The LM26480 incorporates two high-efficiency synchronous switching buck regulators, SW1 and SW2, that deliver a constant voltage from a single Li-Ion battery to the portable system processors. Using a voltage mode architecture with synchronous rectification, both bucks have the ability to deliver up to 1500 mA depending on the input voltage and output voltage (voltage head room), and the inductor chosen (maximum current capability).

There are three modes of operation depending on the current required - PWM, PFM, and shutdown. PWM mode handles current loads of approximately 70 mA or higher, delivering voltage precision of +/-3% with 90% efficiency or better. Lighter output current loads cause the device to automatically switch into PFM for reduced current consumption (IQ = 15 µA typ.) and a longer battery life. The Standby operating mode

The output filter stores charge when the inductor current is high, and releases it when low, smoothing the voltage across the load.

PWM OPERATION

During PWM operation the converter operates as a voltagemode controller with input voltage feed forward. This allows the converter to achieve excellent load and line regulation. The DC gain of the power stage is proportional to the input voltage. To eliminate this dependence, feed forward voltage inversely proportional to the input voltage is introduced.

INTERNAL SYNCHRONOUS RECTIFICATION

While in PWM mode, the buck uses an internal NFET as a synchronous rectifier to reduce rectifier forward voltage drop and associated power loss. Synchronous rectification provides a significant improvement in efficiency whenever the output voltage is relatively low compared to the voltage drop across an ordinary rectifier diode.

CURRENT LIMITING

A current limit feature allows the converter to protect itself and external components during overload conditions. PWM mode implements current limiting using an internal comparator that trips at 2.0A for both bucks (typ). If the output is shorted to ground the device enters a timed current limit mode where the NFET is turned on for a longer duration until the inductor current falls below a low threshold, ensuring inductor current has more time to decay, thereby preventing runaway.

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LM26480

PFM OPERATION

At very light loads, the converter enters PFM mode and operates with reduced switching frequency and supply current to maintain high efficiency.

The part will automatically transition into PFM mode when either of two conditions occurs for a duration of 32 or more clock cycles:

A. The inductor current becomes discontinuous or B. The peak PMOS switch current drops below the I

level

MODE

During PFM operation, the converter positions the output voltage slightly higher than the nominal output voltage during PWM operation, allowing additional headroom for voltage drop during a load transient from light to heavy load. The PFM comparators sense the output voltage via the feedback pin and control the switching of the output FETs such that the output voltage ramps between 0.8% and 1.6% (typical) above the nominal PWM output voltage. If the output voltage is below the ‘high’ PFM comparator threshold, the PMOS power switch is turned on. It remains on until the output voltage exceeds the ‘high’ PFM threshold or the peak current exceeds the I

level set for PFM mode. The typical peak current in

PFM

PFM mode is:

Once the PMOS power switch is turned off, the NMOS power switch is turned on until the inductor current ramps to zero. When the NMOS zero-current condition is detected, the NMOS power switch is turned off. If the output voltage is below the ‘high’ PFM comparator threshold (see following figure), the PMOS switch is again turned on and the cycle is repeated until the output reaches the desired level. Once the output reaches the ‘high’ PFM threshold, the NMOS switch is turned on briefly to ramp the inductor current to zero and then both output switches are turned off and the part enters an extremely low power mode. Quiescent supply current during this ‘sleep’ mode is less than 30 µA, which allows the part to achieve high efficiencies under extremely light load conditions. When the output drops below the ‘low’ PFM threshold, the cycle repeats to restore the output voltage to ~1.6% above the nominal PWM output voltage.

If the load current should increase during PFM mode (see figure below) causing the output voltage to fall below the ‘low2’ PFM threshold, the part will automatically transition into fixed-frequency PWM mode.

SW1, SW2 CONTROL

SW1 and SW2 are enabled/disabled through the external enable pins.

The Modulation mode PWM/PFM is by default automatic and depends on the load as described above in the functional description. The modulation mode can be factory trimmed, forcing the buck to operate in PWM mode regardless of the load condition.

30040405

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SHUTDOWN MODE

During shutdown the PFET switch, reference, control and bias circuitry of the converters are turned off. The NFET

LM26480

switch will be on in shutdown to discharge the output. When the converter is enabled, soft start is activated. It is recommended to disable the converter during the system power up and under voltage conditions when the supply is less than

2.8V.

SOFT START

The soft-start feature allows the power converter to gradually reach the initial steady state operating point, thus reducing start-up stresses and surges. The two LM26480 buck converters have a soft-start circuit that limits in-rush current during start-up. During start-up the switch current limit is increased in steps. Soft start is activated only if EN goes from logic low to logic high after VIN reaches 2.8V. Soft start is implemented by increasing switch current limit in steps of 250 mA, 500 mA, 950 mA and 2A for both bucks (typ. switch current limit). The start-up time thereby depends on the output capacitor and load current demanded at start-up.

LOW DROPOUT OPERATION

The LM26480 can operate at 100% duty cycle (no switching; PMOS switch completely on) for low dropout support of the

output voltage. In this way the output voltage will be controlled down to the lowest possible input voltage. When the device operates near 100% duty cycle, output voltage ripple is approximately 25 mV. The minimum input voltage needed to support the output voltage is

IN,

—

MIN = I

LOAD

DSON, PFET

LOAD

* (R

DSON, PFET

+ R

Load current

Drain to source resistance of

INDUCTOR

) + V

OUT

PFET switch in the triode region

—

INDUCTOR

Inductor resistance

FLEXIBLE POWER-ON RESET (i.e., POWER GOOD WITH DELAY)

The LM26480 is equipped with an internal Power-On-Reset (“POR”) circuit which monitors the output voltage levels on bucks 1 and 2. The nPOR is an open drain logic output which is logic LOW when either of the buck outputs are below 91% of the rising value , or when one or both outputs fall below 82% of the desired value. The time delay between output voltage level and nPOR is enabled is (50 µs, 50 ms, 100 ms, 200 ms) 50 ms by default. The system designer can choose the external pull-up resistor (i.e. 100 kΩ ) for the nPOR pin.

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NPOR with Counter Delay

LM26480

The above diagram shows the simplest application of the Power-On Reset, where both switcher enables are tied together. In Case 1, EN1 causes nPOR to transition LOW and triggers the nPOR delay counter. If the power supply for Buck2 does not come on within that period, nPOR will stay LOW, indicating a power fail mode. Case 2 indicates the vice

versa scenario if Buck1 supply did not come on. In both cases

30040406

the nPOR remains LOW. Case 3 shows a typical application of the Power-On Reset, where both switcher enables are tied together. Even if RDY1 ramps up slightly faster than RDY2 (or vice versa), the nPOR signal will trigger a programmable delay before going HIGH, as explained below.

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LM26480

Faults Occurring in Counter Delay After Startup

The above timing diagram details the Power Good with delay with respect to the enable signals EN1, and EN2. The RDY1, RDY2 are internal signals derived from the output of two comparators. Each comparator has been trimmed as follows:

Comparator Level Buck Supply Level

HIGH Greater than 91%

LOW Less than 82%

The circuits for EN1 and RDY1 are symmetrical to EN2 and RDY2, so each reference to EN1 and RDY1 will also work for EN2 and RDY2 and vice versa.

If EN1 and RDY1 signals are High at time t1, then the RDY1

30040407

signal rising edge triggers the programmable delay counter (50 μs, 50 ms, 100 ms, 200 ms). This delay forces nPOR LOW between time interval t1 and t2. NPOR is then pulled high after the programmable delay is completed. Now if EN2 and RDY2 are initiated during this interval the nPOR signal ignores this event.

If either RDY1or RDY2 were to go LOW at t3 then the programmable delay is triggered again.

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NPOR Mask Window

LM26480

In Case 1, we see that case where EN2 and RDY2 are initiated after triggered programmable delay. To prevent the nPOR being asserted again, a masked window (5 ms) counter delay is triggered off the EN2 rising edge. NPOR is still held HIGH for the duration of the mask, whereupon the nPOR status afterwards will depend on the status of both RDY1 and RDY2 lines.

In Case 2, we see the case where EN2 is initiated after the RDY1 triggered programmable delay, but RDY2 never goes

HIGH (Buck2 never turns on). Normal operation operation of

30040408

nPOR occurs wilth respect to EN1 and RDY1, and the nPOR signal is held HIGH for the duration of the mask window. We see that nPOR goes LOW after the masking window has timed out because it is now dependent on RDY1 and RDY2, where RDY2 is LOW.

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LM26480

Design Implementation of the Flexible Power-On Reset

Design implementation of the flexible power-on reset. An internal power-on reset of the IC is used with EN1 and EN2 to produce a reset signal (LOW) to the delay timer nPOR. EN1 and RDY1 or EN2 and RDY2 are used to generate the set signal (HIGH) to the delay timer. S=R=1 never occurs. The mask timers are triggered off EN1 and EN2 which are gated with RDY1, and RDY2 to generate outputs to the final AND gate to generate the nPOR.

UNDER VOLTAGE LOCK OUT

The LM26480 features an “under voltage lock out circuit”. The function of this circuit is to continuously monitor the raw input

supply voltage (VINLDO12) and automatically disables the

30040409

four voltage regulators whenever this supply voltage is less than 2.8 VDC.

The circuit incorporates a bandgap based circuit that establishes the reference used to determine the 2.8 VDC trip point for a VIN OK – Not OK detector. This VIN OK signal is then used to gate the enable signals to the four regulators of the LM26480. When VINLDO12 is greater than 2.8 VDC the four enables control the four regulators, when VINLDO12 is less than 2.8 VDC the four regulators are disabled by the VIN detector being in the “Not OK” state. The circuit has built in hysteresis to prevent chattering occurring.

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Application Notes

EXTERNAL COMPONENT SELECTION

LM26480

30040410

Ideal Resistor Values Common R Values Feedback Capacitors

Target Vout (V)

R1 (KΩ) R2 (KΩ) R1 (KΩ) R2 (KΩ)

Actual V

Com/R (V)

OUT

Actual

Delta from

OUT

Target (V)

C1(pF) C2(pF)

0.8 120 200 121 200 0.803 0.002 15 none Buck1

0.9 160 200 162 200 0.905 0.005 15 none Only

1 200 200 200 200 1 0 15 none ^

1.1 240 200 240 200 1.1 0 15 none |

1.2 280 200 280 200 1.2 0 12 none |

1.3 320 200 324 200 1.31 0.01 12 none Buck1

1.4 360 200 357 200 1.393 -0.008 10 none And

1.5 400 200 402 200 1.505 0.005 10 none Buck2

1.6 440 200 442 200 1.605 0.005 8.2 none |

1.7 427 178 432 178 1.713 0.013 8.2 none |

1.8 463 178 464 178 1.803 0.003 8.2 none |

1.9 498 178 499 178 1.902 0.002 8.2 none |

2 450 150 453 150 2.01 0.01 8.2 none >

2.1 480 150 475 150 2.083 -0.017 8.2 none ^

2.2 422 124 422 124 2.202 0.002 8.2 none |

2.3 446 124 442 124 2.282 -0.018 8.2 none |

2.4 471 124 475 124 2.415 0.015 8.2 none |

2.5 400 100 402 100 2.51 0.01 8.2 none |

2.6 420 100 422 100 2.61 0.01 8.2 none |

2.7 440 100 442 100 2.71 0.01 8.2 33 Buck2

2.8 460 100 464 100 2.82 0.02 8.2 33 Only

2.9 480 100 475 100 2.875 -0.025 8.2 33 |

3 500 100 499 100 2.995 -0.005 6.8 33 |

3.1 520 100 523 100 3.115 0.015 6.8 33 |

3.2 540 100 536 100 3.18 -0.02 6.8 33 |

3.3 560 100 562 100 3.31 0.01 6.8 33 |

The output voltages of the bucks of the LM26480 are established by the feed back resistor divider R1 shown on the application circuit above. The equation for determining V is: V

= VFB (R1+R2)/R2 where VFB is the voltage on the Buck

OUT

FBx pin. The Buck control loop will force the voltage on VFB to be 0.50

V +/- 3%. The above table shows ideal resistor values to establish buck

voltages from 0.8V to 3.3 V along with common resistor val-

ues to establish these voltages. Common resistors do not always produce the target value, error is given in the delta column.

In addition to the resistor feedback, capacitor feedback C1 is always required, and depending on the output voltage capacitor C2 is also required. See the application diagram below and the above table for these requirements.

21 www.national.com

Inductor Value Unit Description Notes

LSW1,2 2.2 µH SW1,2 inductor

LM26480

OUTPUT INDUCTORS & CAPACITORS FOR SW1 AND SW2

There are several design considerations related to the selection of output inductors and capacitors:

•

Load transient response;

•

Stability;

•

Efficiency;

•

Output ripple voltage; and

•

Over-current ruggedness.

The LM26480 has been optimized for use with nominal values

2.2 µH and 10 µF. If other values are needed for the design, please contact National Semiconductor sales with any concerns.

INDUCTOR SELECTION FOR SW1 AND SW2

A nominal inductor value of 2.2 µH is recommended. It is important to guarantee the inductor core does not saturate during any foreseeable operational situation.

Care should be taken when reviewing the different saturation current ratings that are specified by different manufacturers. Saturation current ratings are typically specified at 25ºC, so ratings at maximum ambient temperature of the application should be requested from the manufacturer.

There are two methods to choose the inductor saturation current rating:

Recommended method:

The best way to guarantee the inductor does not saturate is to choose an inductor that has saturation current rating greater than the maximum LM26480 current limit of 2.4A. In this case the device will prevent inductor saturation.

Alternate method:

If the recommended approach cannot be used, care must be taken to guarantee that the saturation current is greater than the peak inductor current:

D.C.R. 70 mΩ

may not be exceeded during any operation, including

SAT

transients, startup, high temperature, worst case conditions, etc.

SUGGESTED INDUCTORS AND THEIR SUPPLIERS

Model Vendor Dimension

s (mm)

DO3314-22

Coilcraft 3.3 x 3.3 x

2MX

LPO3310-2

Coilcraft 3.3 x 3.3 x 1

1.4

DCR

(max)

200 mΩ

150 mΩ

SATURATION

≈1.8A

≈1.3A

22MX

ELL6PG2R2NPanaso

nic

ELC6GN2R2NPanaso

nic

CDRH2D14

Sumida 3.2 x 3.2 x

NP-2R2NC

Note: Inductor Current Saturation values are estimates; inductor manufacturer should be contacted for guaranteed values.

6.0 x 6.0 x

2.0

6.0 x 6.0 x

1.5

37mΩ

53 mΩ

94 mΩ

≈2.2A

≈1.9A

≈1.5A

OUTPUT CAPACITOR SELECTION FOR SW1 AND SW2

A ceramic output capacitor of 10 µF, 6.3V is recommended with an ESR of about 2 mΩ or less.

Output ripple can be estimated from the vector sum of the reactive (Capacitor) voltage component and the real (ESR) voltage component of the output capacitor.

SAT

LPEAK

OUTMAX

RIPPLE

OUT

VIN: L: F: D: EFF:

www.national.com 22

Inductor saturation current at operating temperature

Peak inductor current during worst case conditions

Maximum average inductor current

Peak-to-Peak inductor current

Output voltage Input voltage Inductor value in Henries at I Switching frequency, Hertz Estimated duty factor Estimated power supply efficiency

30040471

OUTMAX

COUT

ROUT

PPOUT

Estimated reactive output ripple

Estimated real output ripple

Estimated peak-to-peak output ripple

The output capacitor needs to be mounted as close as possible to the output pin of the device. For better temperature performance, X7R or X5R types are recommended. DC bias characteristics of ceramic capacitors must be considered when selecting case sizes like 0805 and 0603.

DC bias characteristics vary from manufacturer to manufacturer and by case size. DC bias curves should be requested from them as part of the capacitor selection process. ESR is typically higher for smaller packages.

The output filter capacitor smooths out current flow from the inductor to the load, helps maintain a steady output voltage during transient load changes and reduces output voltage ripple. These capacitors must be selected with sufficient capacitance and sufficiently low ESR to perform these functions.

Note that the output voltage ripple is dependent on the inductor current ripple and the equivalent series resistance of the output capacitor (ESR dent as well as temperature dependent. The R calculated with the applicable switching frequency and ambi-

COUT

). ESR

is frequency depen-

COUT

ESR

should be

ent temperature.

INPUT CAPACITOR SELECTION FOR SW1 AND SW2

It is required to use a ceramic input capacitor of at least 4.7 μF and 6.3V with an ESR of under 10 mΩ.

The input power source supplies average current continuously. During the PFET switch on-time, however, the demanded di/dt is higher than can be typically supplied by the input power source. This delta is supplied by the input capacitor.

A simplified “worst case” assumption is that all of the PFET current is supplied by the input capacitor. This will result in conservative estimates of input ripple voltage and capacitor RMS current. Input ripple voltage is estimated as follows:

PPIN

OUT

IN:

ESR

Estimated peak-to-peak input ripple voltage

Output current, Amps Input capacitor value, Farads Input capacitor ESR, Ohms

IN:

This capacitor is exposed to significant RMS current, so it is important to select a capacitor with an adequate RMS current rating. Capacitor RMS current estimated as follows:

LM26480

RSCIN

Estimated input capacitor RMS current

Model Type Vendor Voltage Rating Case Size

4.7 µF for CIN

C2012X5R0J475K Ceramic, X5R TDK 6.3V 0805, (2012)

JMK212BJ475K Ceramic, X5R Taiyo-Yuden 6.3V 0805, (2012)

GRM21BR60J475K Ceramic, X5R Murata 6.3V 0805, (2012)

C1608X5R0J475K Ceramic, X5R TDK 6.3V 0603, (1608)

10 µF for COUT

GRM21BR60J106K Ceramic, X5R Murata 6.3V 0805, (2012)

JMK212BJ106K Ceramic, X5R Taiyo-Yuden 6.3V 0805, (2012)

C2012X5R0J106K Ceramic, X5R TDK 6.3V 0805, (2012)

C1608X5R0J106K Ceramic, X5R TDK 6.3V 0603, (1608)

23 www.national.com

FEEDBACK RESISTORS FOR LDOs

LM26480

30040410

Target V

(V) Ideal Resistor Values Common R Values Actual V

OUT

R1 (KΩ) R2 (KΩ) R1 (KΩ) R2 (KΩ)

1 200 200 200 200 1

1.1 240 200 240 200 1.1

1.2 280 200 280 200 1.2

1.3 320 200 324 200 1.31

1.4 360 200 357 200 1.393

1.5 400 200 402 200 1.505

1.6 440 200 442 200 1.605

1.7 480 200 562 232 1.711

1.8 520 200 604 232 1.802

1.9 560 200 562 200 1.905

2 600 200 604 200 2.01

2.1 640 200 715 221 2.118

2.2 680 200 681 200 2.203

2.3 720 200 806 226 2.283

2.4 760 200 845 221 2.412

2.5 800 200 750 187 2.505

2.6 840 200 909 215 2.614

2.7 880 200 1100 249 2.709

2.8 920 200 1150 249 2.809

2.9 960 200 1210 255 2.873

3 1000 200 1000 200 3

3.1 1040 200 1000 191 3.118

3.2 1080 200 1000 187 3.174

3.3 1120 200 1210 215 3.314

3.4 1160 200 1210 210 3.381

3.5 1200 200 1210 200 3.525

OUT

Com/R (V)

The output Voltages of the LDOs of the LM26480 are established by the feed back resistor divider R1 shown on the application circuit above. The equation for determining V is: V

= VFB(R1+R2)/R2, where Vfb is the voltage on the

OUT

LDOX_FB pin.

OUT

The LDO control loop will force the voltage on VFBo be 0.50 V +/- 3%. The above table shows ideal resistor values to es-

www.national.com 24

tablish LDO voltages from 1.0 V to 3.5 V along with common resistor values to establish these voltages. Common resistors do not always produce the target value, error is given in the final column.

To keep the power consumed by the feedback network low it is recommended that R2 be established as about 200 KΩ. Lesser values of R2 are OK at the users discretion..

LM26480

LDO CAPACITOR SELECTION Input Capacitor

An input capacitor is required for stability. It is recommended that a 1.0 μF capacitor be connected between the LDO input pin and ground (this capacitance value may be increased without limit). This capacitor must be located a distance of not more than 1 cm from the input pin and returned to a clean analog ground. Any good quality ceramic, tantalum, or film capacitor may be used at the input.

Important: Tantalum capacitors can suffer catastrophic failures due to surge currents when connected to a low impedance source of power (like a battery or a very large capacitor). If a tantalum capacitor is used at the input, it must be guaranteed by the manufacturer to have a surge current rating sufficient for the application.

There are no requirements for the ESR on the input capacitor, but tolerance and temperature coefficient must be considered when selecting the capacitor to ensure the capacitance will remain approximately 1.0 μF over the entire operating temperature range.

Output Capacitor

The LDOs on the LM26480 are designed specifically to work with very small ceramic output capacitors. A 1.0 μF ceramic capacitor (temperature types Z5U, Y5V or X7R) with ESR between 5 mΩ to 500 mΩ, are suitable in the application circuit. It is also possible to use tantalum or film capacitors at the device output COUT (or VOUT), but these are not as attractive for reasons of size and cost. The output capacitor must meet the requirement for the minimum value of capacitance and also have an ESR value that is within the range 5 mΩ to 500 mΩ for stability.

Capacitor Characteristics

The LDOs are designed to work with ceramic capacitors on the output to take advantage of the benefits they offer. For capacitance values in the range of 0.47 μF to 4.7 μF, ceramic capacitors are the smallest, least expensive and have the lowest ESR values, thus making them best for eliminating high frequency noise. The ESR of a typical 1.0 μF ceramic capacitor is in the range of 20 mΩ to 40 mΩ, which easily meets the ESR requirement for stability for the LDOs.

For both input and output capacitors, careful interpretation of the capacitor specification is required to ensure correct device operation. The capacitor value can change greatly, depending on the operating conditions and capacitor type.

In particular, the output capacitor selection should take account of all the capacitor parameters, to ensure that the specification is met within the application. The capacitance can vary with DC bias conditions as well as temperature and frequency of operation. Capacitor values will also show some decrease over time due to aging. The capacitor parameters are also dependent on the particular case size, with smaller sizes giving poorer performance figures in general. As an example, the graph below shows a typical graph comparing

different capacitor case sizes in a capacitance vs. DC bias plot.

30040416

As shown in the graph, increasing the DC bias condition can result in the capacitance value that falls below the minimum value given in the recommended capacitor specifications table. Note that the graph shows the capacitance out of spec for the 0402 case size capacitor at higher bias voltages. It is therefore recommended that the capacitor manufacturers’ specifications for the nominal value capacitor are consulted for all conditions, as some capacitor sizes (e.g. 0402) may not be suitable in the actual application.

The ceramic capacitor’s capacitance can vary with temperature. The capacitor type X7R, which operates over a temperature range of −55°C to +125°C, will only vary the capacitance to within ±15%. The capacitor type X5R has a similar tolerance over a reduced temperature range of −55°C to +85°C. Many large value ceramic capacitors, larger than 1 μF are manufactured with Z5U or Y5V temperature characteristics. Their capacitance can drop by more than 50% as the temperature varies from 25°C to 85°C. Therefore X7R is recommended over Z5U and Y5V in applications where the ambient temperature will change significantly above or below 25°C.

Tantalum capacitors are less desirable than ceramic for use as output capacitors because they are more expensive when comparing equivalent capacitance and voltage ratings in the

0.47 μF to 4.7 μF range. Another important consideration is that tantalum capacitors have higher ESR values than equivalent size ceramics. This means that while it may be possible to find a tantalum capacitor with an ESR value within the stable range, it would have to be larger in capacitance (which means bigger and more costly) than a ceramic capacitor with the same ESR value. It should also be noted that the ESR of a typical tantalum will increase about 2:1 as the temperature goes from 25°C down to −40°C, so some guard band must be allowed.

Capacitor Min Value Unit Description Recommended Type

CLDO1 0.47 µF LDO1 output capacitor Ceramic, 6.3V, X5R

CLDO2 0.47 µF LDO2 output capacitor Ceramic, 6.3V, X5R

CSW1 10 µF SW1 output capacitor Ceramic, 6.3V, X5R

CSW2 10 µF SW2 output capacitor Ceramic, 6.3V, X5R

25 www.national.com

Analog Power Signal Routing

All power inputs should be tied to the main VDD source (i.e.

LM26480

battery), unless the user wishes to power it from another source. (i.e. powering LDO from Buck output).

The analog VDD inputs power the internal bias and error amplifiers, so they should be tied to the main VDD. The analog VDD inputs must have an input voltage between 2.8 and 5.5 V, as specified in the Electrical Characteristics section of this datasheet.

The other Vins (VINLDO1, VINLDO2, VIN1, VIN2) can actually have inputs lower than 2.8V, as long as it's higher than

the programmed output (+0.3V, to be safe). The analog and digital grounds should be tied together outside of the chip to reduce noise coupling.

For more information on board layout techniques, refer to Application Note AN–1187 “Leadless Lead frame Package (LLP).” on http://www.national.com This application note also discusses package handling, solder stencil and the assembly process.

www.national.com 26

LM26480

Board Layout Considerations

PC board layout is an important part of DC-DC converter design. Poor board layout can disrupt the performance of a DCDC converter and surrounding circuitry by contributing to EMI, ground bounce, and resistive voltage loss ii the traces. These can send erroneous signals to the DC-DC converter IC, re-

sulting in poor regulation or instability. Poor layout can also result in re-flow problems leading to poor solder joints, which can result in erratic or degraded performance.

Good layout for the LM26480 bucks can be implemented by following a few simple design rules, as illustrated in Figure 6.

FIGURE 3. Board Layout Design Rules for the LM26480

Place the buck inductor and filter capacitors close together and make the trace short. The traces between these components carry relatively high switching currents and act as antennas. Following this rule reduces radiated noise. Place the capacitors and inductor close to the buck.

Arrange the components so that the switching current loops curl in the same direction. During the first halt of each cycle, current flows from the input filter capacitor, through the buck and inductor to the output filter capacitor and back through ground, forming a current loop. In the second half of each cycle, current is pulled up from ground, through the buck by the inductor, to the output filter capacitor and then back through ground, forming a second current loop. Routing these loops so the current curls in the same direction prevents magnetic field reversal between the two half-cycles and reduces radiated noise.

Connect the ground pins of the buck, and filter capacitors together using generous component-side copper fill as a pseudo-ground plane. Then connect this to the groundplane (if one is used) with several vias. This reduces ground—plane noise by preventing the switching currents from circulating through the ground plane. it also

30040468

reduces ground bounce at the buck by giving it a lowimpedance ground connection.

Use wide traces between the power components and for power connections to the DC-DC converter circuit. This reduces voltage errors caused by resistive losses across the traces

Rout noise sensitive traces, such as the voltage feedback path, away from noisy traces between the power components. The voltage feedback trace must remain close to the buck circuit and should be routed directly from FB to VOUT at the output capacitor and should be routed opposite to noise components. This reduces EMI radiated onto the DC-DC converter’s own voltage feedback trace.

In mobile phones, for example, a common practice is to place the DC-DC converter on one corner of the board, arrange the CMOS digital circuitry around it (since this also generates noise), and then place sensitive preamplifiers and IF stages on the diagonally opposing corner. Often, the sensitive circuitry is shielded with a metal pan and power to it is postregulated to reduce conducted noise, using low-dropout linear regulators.

27 www.national.com

High VIN-High Load Operation

Additional inforamtion is provided when the IC is operated at

LM26480

extremes of VIN and regulator loads. These are described in terms of the junction temperature and buck output ripple management.

Junction Temperature

The maximum junction temperature T IC package.

The following equations demonstrate junction temperature determination, ambient temperature T power ust be controlled to keep TJ below this maximum:

T Total IC power dissipation P

power dissipation of the four regulators plus a minor amount

J-MAX-OP

= T

+ (θJA) [°C/Watt] * (P

A-MAX

is the sum of the individual

D-MAX

for chip overhead. Chip overhead is bias, TSD and LDO analog.

= PLOD1 + PLDO2 +PBUCK1 + PBUCK2 + (0.0001A

D-MAX

* VIN) [Watts].

J-MAX-OP

A-MAX

D-MAX

of 125°C of the

and total chip

) [Watts]

Power dissipation of LDO1 (PLDO1) = (VINLDO1 − VOUTLDO1) * IOUTLDO1 [V*A]

Power dissipation of LDO2 (PLDO2) = (VINLDO2 − VOUTLDO2) * IOUTLDO2 [V*A]

Power dissipation of Buck1 (PBuck1) = POUT − PIN = VOUTBUCK1 − IOUTBUCK1 * (1 − η2)/ η2 [V*A]

η1 = efficiency of Buck1 Power dissipation of Buck2 (PBuck2) = POUT − PIN = VOUT-

BUCK2 − IOUTBUCK2 * (1 − η2)/ η2 [V*A]

η2 = efficiency of Buck2 Where η is the efficiency for the specific condition is taken

from efficiency graphs. If VIN and ILOADincrease, the output ripple associated with

the Buck Regulators also increases. This mainly occurs with VIN > 5.2V and a load current greater than 1.20A. To ensure operation in this area of operation, it is recommended that the system designer circumvents the output ripple issues by installing Schottky diodes on the bucks(s) that are expected to perform under these extreme conditions.

www.national.com 28

Physical Dimensions inches (millimeters) unless otherwise noted

LM26480

4 X 4 X 0.8 mm 24-Pin LLP Package

For ordering, refer to Ordering Information table

NS Package SQA24A

29 www.national.com

Notes

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Datasheet LM26480 Datasheet (National Semiconductor)

Specifications and Main Features

Frequently Asked Questions

User Manual

General Description

Key Specifications

Features

Applications

Typical Application Circuit

FIGURE 1. Application Circuit

Connection Diagrams and Package Mark Information

FIGURE 2. 24-Lead LLP Package (top view)

Pin Descriptions

Absolute Maximum Ratings (Notes 1, 2)

Operating Ratings: Bucks (Notes 1, 2, 7)

Thermal Properties (Notes 3, 5, 6)

General Electrical Characteristics (Notes 1, 2, 7, 13, 16)

Low Drop Out Regulators, LDO1 and LDO2

Buck Converters SW1, SW2

I/O Electrical Characteristics

Power On Reset Threshold/Function (POR)

Typical Performance Characteristics — LDO

Typical Performance Characteristics — Buck V

Typical Performance Characteristics — Buck Output Current transitions from PFM mode to PWM

Typical Performance Characteristics — Buck

DC/DC Converters

OVERVIEW

Supply Specification

LINEAR LOW DROPOUT REGULATORS (LDOs)

CIRCUIT OPERATION DESCRIPTION

NO-LOAD STABILITY

FUNCTIONAL DESCRIPTION

PWM OPERATION

INTERNAL SYNCHRONOUS RECTIFICATION

CURRENT LIMITING

PFM OPERATION

SW1, SW2 CONTROL

SHUTDOWN MODE

SOFT START

LOW DROPOUT OPERATION

FLEXIBLE POWER-ON RESET (i.e., POWER GOOD WITH DELAY)

UNDER VOLTAGE LOCK OUT

Application Notes

EXTERNAL COMPONENT SELECTION

OUTPUT INDUCTORS & CAPACITORS FOR SW1 AND SW2

INDUCTOR SELECTION FOR SW1 AND SW2

SUGGESTED INDUCTORS AND THEIR SUPPLIERS

OUTPUT CAPACITOR SELECTION FOR SW1 AND SW2

INPUT CAPACITOR SELECTION FOR SW1 AND SW2

FEEDBACK RESISTORS FOR LDOs

Analog Power Signal Routing

Board Layout Considerations

FIGURE 3. Board Layout Design Rules for the LM26480

High VIN-High Load Operation

Physical Dimensions inches (millimeters) unless otherwise noted